JP4129271B2 - Transmission method, reception method, transmission method, and reception apparatus - Google Patents

Description

  The present invention relates to an orthogonal frequency multiplex signal transmission method and a receiving apparatus thereof, and more specifically, an orthogonal frequency division multiplex signal for each symbol of a predetermined length from a transmission side to a reception side via a predetermined transmission path. The present invention relates to a method for transmitting data and a receiving apparatus thereof.

  In recent years, communication using orthogonal frequency division multiplexing (hereinafter referred to as OFDM) signals has been attracting attention in digital audio broadcasting for mobile units, terrestrial digital television broadcasting, and the like. This is because the OFDM signal has good frequency utilization efficiency, enables high-speed transmission of a large amount of data, and has little characteristic deterioration due to a reflected wave even without a waveform equalizer. Moreover, since the signal waveform has a form close to random noise, it is difficult to interfere with other services. A transmission method using an OFDM signal having such characteristics is disclosed in Japanese Patent Laid-Open No. 5-167633 (hereinafter referred to as the first prior art), Nikkei Electronics (no. 574) issued on February 15, 1993. Nos. 1-15 of the EIAJ Technical Seminar document dated September 14, 1994 and “Home Next Generation Services Beyond Television” (hereinafter referred to as the second prior art) This is disclosed in “OFDM System and Its Development Trend” (hereinafter referred to as “third prior art”) written by Masanori Saito of NHK Broadcasting Technology Research Laboratories.

  FIG. 11 is a diagram showing a configuration of a conventional OFDM signal. In particular, FIG. 11 (a) shows each symbol of the OFDM signal along the time axis, and FIG. 11 (b) is a part of FIG. 11 (a). α is shown enlarged. As shown in FIG. 11A, the OFDM signal S is configured by arranging symbols Sm (m = 1, 2,...) Along the time axis. Each symbol Sm is digitally modulated (for example, QPSK modulation, 16QAM, etc.) with a plurality of (several tens to thousands, for example, 512) carriers having different frequencies (which are orthogonal to each other at the symbol time ts). The modulated carriers are multiplexed on the frequency axis by inverse FFT (fast inverse Fourier transform) calculation. Therefore, each symbol Sm shows a random amplitude distribution as shown in FIG. Note that such an OFDM signal S takes the form of a complex signal in which a real part and an imaginary part are superimposed on each symbol Sm on the transmission path.

  By the way, such an OFDM signal is transmitted from the transmission side to the reception side via a wired or wireless transmission path. In a wired transmission path, the occupied frequency band is regulated by the transmission characteristics of the transmission path. In addition, in the wireless transmission path, the occupied frequency band is regulated by legal regulations. For this reason, the transmission side converts the OFDM signal from the intermediate frequency band to the occupied frequency band of the transmission path. On the other hand, when demodulating data, the receiving side converts the received OFDM signal from an occupied frequency band of the transmission path to an intermediate frequency band for demodulation work.

  In the first prior art described above, a band-pass filter, a frequency converter and a low-pass filter for converting an OFDM signal transmitted from the transmission side into a baseband OFDM signal, and a baseband OFDM signal are sampled. A / D converter that converts to digital signal, FFT demodulator that obtains data on frequency axis for each carrier by Fourier transform of time axis data, and amplitude and phase on complex plane for each carrier A signal point coordinate determination circuit for obtaining complex data, a reception data combining circuit for converting the complex data into digital data, combining the data according to the number of bits transmitted in each carrier wave, and generating a bit stream, and a bit Deinterleave matrix and error correction to obtain received data by performing deinterleaving and error correction on stream Receiving apparatus is disclosed that includes a No. circuit.

  In the third prior art described above, a band-pass filter, a quadrature detector and a low-pass filter for converting an OFDM signal transmitted from the transmission side into a baseband OFDM signal, and a baseband OFDM signal are sampled. A / D converter for converting to digital signal, FFT demodulator for Fourier transform of time axis data to obtain data on frequency axis for each carrier wave, and received data by converting parallel data on frequency axis to serial A receiving device including a parallel-to-serial converter circuit that obtains the above is disclosed.

  FIG. 12 is a block diagram showing a configuration of an OFDM signal receiving apparatus that can be easily inferred from the first and third prior arts. In FIG. 12, this receiving apparatus includes an input terminal I to which a received OFDM signal is input, a frequency converter 100, a quadrature detector 300, a Fourier transformer 400, and a demodulated data detector 500. The quadrature detector 300 includes a duplexer 301, detectors 302 and 303, and a carrier regenerator 304.

  The OFDM signal in the occupied frequency band (center frequency fr) of the transmission path shown in FIG. 11 received by the receiving apparatus is input to the frequency converter 100 via the input terminal I. The frequency converter 100 shifts the OFDM signal in the occupied frequency band of the transmission path to the OFDM signal in the intermediate frequency band (center frequency fc) by shifting by a predetermined fixed frequency.

  The demultiplexer 301 of the quadrature detector 300 demultiplexes the OFDM signal output from the frequency converter 100 into two signals, and outputs the demultiplexed OFDM signals to the detectors 302 and 303, respectively. The carrier regenerator 304 outputs an in-phase carrier having a center frequency fc to the detector 302 and outputs a quadrature carrier having a center frequency fc to the detector 303. The detector 302 multiplies the OFDM signal output from the demultiplexer 301 by the in-phase carrier to output the real part of the OFDM signal. The detector 303 outputs the imaginary part of the OFDM signal by multiplying the OFDM signal output from the duplexer 301 by the orthogonal carrier. That is, the quadrature detector 300 converts the intermediate frequency band OFDM signal into a baseband OFDM signal.

The Fourier transformer 400 performs multiplexing on the frequency axis by collectively performing a Fourier transform operation on the real part of the OFDM signal output from the detector 302 and the imaginary part of the OFDM signal output from the detector 303. The real part and the imaginary part of each digital modulated wave are separated. The demodulated data detector 500 maps the real part and imaginary part of each digital modulated wave to the complex plane, demodulates the data obtained by modulating each carrier from the mapping position according to the threshold value set therein, and outputs it. The demodulated data is output from terminal O.
JP-A-5-167633 “Home Next-Generation Services Beyond Television” Nikkei Electronics (no. 574), February 15, 1993, pages 101-124 Masanori Saito “OFDM system and its development trend” NHK Science and Technology Research Laboratories, September 14, 1994, EIAJ Technical Seminar, pages 1-15

  The OFDM signal as described above is transmitted from the transmission apparatus to the reception apparatus via a wireless or wired transmission path, and the OFDM signal is attenuated in any transmission path. The attenuation amount of the OFDM signal changes according to the change of the distance in the wireless transmission path, and changes according to the number of branches of the transmission path in the wired transmission path. When the attenuation amount of the OFDM signal changes, the reception apparatus varies in the reception level of the OFDM signal. However, the receiving apparatus in FIG. 12 performs data demodulation processing without any correction even if the reception level of the OFDM signal varies. For this reason, there has been a problem that erroneous determination of demodulated data frequently occurs in the demodulated data detector 500.

  By the way, an FM receiver or the like is provided with an automatic gain control amplifier that corrects the fluctuation of the reception level based on the fluctuation of the envelope of the received signal. Although it is conceivable to apply such a correction method to the receiving apparatus of FIG. 12, unlike the single carrier FM signal, in the OFDM signal, a large number of modulation carriers are multiplexed on the frequency axis. The amplitude and phase patterns in the symbol interval change randomly. For this reason, the envelope waveform of the OFDM signal also changes frequently on the time axis, and if the automatic gain control amplifier is controlled based on such an envelope waveform, the gain of the automatic gain control amplifier becomes unstable and stable control is achieved. I can't. In addition, in the OFDM signal, since the modulation data of each carrier is different from each other, fluctuations in the envelope waveform and fluctuations in the reception level are not necessarily correlated. Therefore, even if the level correction method in the FM receiver is applied to the OFDM signal receiver, the fluctuation of the reception level cannot be corrected with high accuracy.

  In the receiving apparatus of FIG. 12, since the frequency shift amount in the frequency converter 100 is fixedly set, even if a frequency band shift, that is, a frequency band fluctuation occurs, the frequency band fluctuation cannot be corrected. . Therefore, there has been a problem that erroneous determination of demodulated data frequently occurs.

  By the way, an AM receiver or the like is provided with a frequency converter that corrects the fluctuation of the frequency band based on the frequency discrimination fluctuation of the received signal. Although it is conceivable to apply such a correction method to the receiving apparatus of FIG. 12, unlike an AM signal having a single carrier, in an OFDM signal, a large number of modulated carriers are multiplexed on the frequency axis. The amplitude and phase patterns in the symbol interval change randomly. For this reason, the frequency discrimination waveform of the OFDM signal also changes frequently on the frequency axis, and when the frequency converter is controlled based on such a frequency discrimination waveform, the frequency shift amount of the frequency converter becomes unstable and stable. Control is not possible. In addition, in the OFDM signal, since the modulation data of each carrier is different from each other, the fluctuation of the frequency discrimination waveform and the fluctuation of the frequency shift amount are not necessarily correlated. Therefore, even if the method of correcting the frequency shift amount in the AM receiver is applied to the OFDM signal receiving apparatus, the fluctuation of the frequency band cannot be corrected with high accuracy.

  SUMMARY OF THE INVENTION Therefore, an object of the present invention is to provide an orthogonal frequency multiplex signal transmission method and a receiving apparatus thereof that can accurately correct fluctuations in reception level and do not cause erroneous determination of demodulated data.

  Another object of the present invention is to provide a method of transmitting an orthogonal frequency multiplex signal and a receiving apparatus thereof that can accurately correct fluctuations in the frequency band and consequently do not cause erroneous determination of demodulated data.

In order to achieve the above object, a first aspect of the present invention is directed to a method of transmitting an orthogonal frequency division multiplexed signal for each symbol including a plurality of carriers having a frequency relationship orthogonal to each other. The transmission method transmits a first symbol and further transmits a second symbol. Here, the first symbol includes an integer number of known pseudo-random information in the time axis component, further, the second symbol, Ruki Yaria included in the symbols are modulated Ri by the transmission data ing.

The second aspect of the present invention is directed to a method of receiving an orthogonal frequency division multiplex signal transmitted for each symbol including a plurality of carriers having a frequency relationship orthogonal to each other. The reception method receives a first symbol and further receives a second symbol. Here, the first symbol includes an integer number of known pseudo-random information in the time axis component, further, the second symbol, Ruki Yaria included in the symbols are modulated Ri by the transmission data ing. The reception method further demodulates the second symbol based on the synchronization information obtained from the received first symbol to obtain transmission data.

  Further, the reception method further corrects the fluctuation of the frequency band based on the received first symbol.

  Further, the reception method further corrects fluctuations in the reception level based on the received first symbol.

Further, the third aspect of the present invention provides an orthogonal frequency division multiplex signal for each symbol including a plurality of carriers in a frequency relationship orthogonal to each other from a transmission side to a reception side via a wired or wireless transmission path. Is directed to a method of transmission. The transmitting side transmits a first symbol and further transmits a second symbol. Here, the first symbol includes an integer number of known pseudo-random information in the time axis component, further, the second symbol, Ruki Yaria included in the symbols are modulated Ri by the transmission data ing. The receiving side receives the second symbol, and further receives the first symbol. Here, the receiving side further demodulates the second symbol based on the synchronization information obtained from the received first symbol to obtain transmission data.

  Further, the reception side further corrects the fluctuation of the frequency band based on the received first symbol.

  Further, the reception side further corrects the fluctuation of the reception level based on the received first symbol.

The fourth aspect of the present invention is directed to a receiving apparatus that receives an orthogonal frequency division multiplex signal transmitted for each symbol including a plurality of carriers having a frequency relationship orthogonal to each other. The receiving device includes receiving means for receiving an orthogonal frequency division multiplexed signal. Here, orthogonal frequency division multiplexed signal includes a first symbol includes a second symbol, the first symbol includes an integer number of known pseudo-random information in the time axis component, further, the 2 symbols, Ruki Yaria included in the symbol has been modulated Ri by the transmission data. The receiving device further includes demodulation means for demodulating the second symbol to obtain transmission data based on the synchronization information obtained from the received first symbol.

In addition, the receiving device corrects the fluctuation of the frequency band based on the received first symbol.
In addition, the reception device corrects the fluctuation of the reception level based on the received first symbol.

The fifth aspect of the present invention is directed to a method of generating an orthogonal frequency division multiplexed signal transmitted for each symbol including a plurality of carriers having a frequency relationship orthogonal to each other. The generation method generates a first symbol, and further generates a second symbol. Here, the first symbol includes an integer number of known pseudo-random information in the time axis component, and in the second symbol, the carrier included in the symbol is modulated by transmission data.
The sixth aspect of the present invention is directed to a method of demodulating an orthogonal frequency division multiplex signal transmitted for each symbol including a plurality of carriers having a frequency relationship orthogonal to each other. Here, the orthogonal frequency division multiplexing signal includes a first symbol and a second symbol, and the first symbol includes an integer number of known pseudo-random information in the time axis component, and In the second symbol, the carrier included in the symbol is modulated by transmission data. In the demodulation method, the second symbol is demodulated based on the synchronization information obtained from the received first symbol to obtain transmission data.
The seventh aspect of the present invention is directed to a demodulator that demodulates an orthogonal frequency division multiplexed signal transmitted for each symbol including a plurality of carriers having a frequency relationship orthogonal to each other. Here, the orthogonal frequency division multiplexing signal includes a first symbol and a second symbol, and the first symbol includes an integer number of known pseudo-random information in the time axis component, and In the second symbol, the carrier included in the symbol is modulated by transmission data. The demodulator includes a demodulator that demodulates the second symbol and obtains transmission data based on the synchronization information obtained from the received first symbol.

As described above the first-seventh aspect, the first symbol including integer number of known pseudo-random information in the time axis component, a plurality of the carriers are modulated Ri by the transmission data included in one symbol By transmitting the second symbol, the correlation on the receiving side can be easily obtained.

  Hereinafter, embodiments of the present invention will be described with reference to the drawings. FIG. 1 is a diagram illustrating an example of a configuration of an OFDM signal transmitted from a transmission side to a reception side in the present invention. In particular, FIG. 1 (a) shows each symbol of the OFDM signal along the time axis, and FIG. 1 (b) shows an enlarged portion α of FIG. 1 (a).

  As shown in FIG. 1 (a), an OFDM signal S includes a specific symbol S0 for automatic gain control indicated by hatching and a demodulation symbol Sm (m = 1, 2) indicated without hatching. ,...) Along the time axis. The symbol S0 is inserted every predetermined symbol interval (for example, every 15 symbol intervals). Note that such an OFDM signal S takes the form of an analog complex signal in which a real part and an imaginary part are superimposed on each of the symbols S0 and Sm on the transmission line.

  Each symbol Sm is formed by multiplexing (high-speed inverse Fourier calculation) a plurality of carriers (several tens to thousands, for example, 512) having different frequencies (which are orthogonal to each other at the symbol time ts) on the frequency axis. ing. Each carrier is digitally modulated (for example, QPSK modulation, 16QAM, etc.) with data to be demodulated on the receiving side. For this reason, each symbol Sm shows a random amplitude distribution as shown in FIG.

  Each symbol S0 is formed, for example, by performing a fast inverse Fourier operation on one of the plurality of carriers (for example, frequency fc) which is left as an unmodulated single tone signal and the other carriers are suppressed. Yes. For this reason, each symbol S0 indicates an amplitude distribution of a specific pattern as shown in FIG. Such a symbol S0 has a known time axis component and a known frequency axis component.

  By the way, the OFDM signal S is transmitted from the transmission side to the reception side via a wired or wireless transmission path (not shown). For this reason, the OFDM signal S is attenuated on the transmission path. Therefore, on the receiving side, when demodulating data, it is necessary to correct the level of the received OFDM signal S in order to compensate for the attenuation occurring on the transmission path. Such an operation of correcting the reception level of the OFDM signal S is performed using the symbol S0. This is because the symbol S0 always includes a signal having the same pattern, so that the change in the reception level can be accurately measured from the waveform of the symbol S0.

  FIG. 2 is a block diagram showing the configuration of the receiving apparatus according to the first embodiment of the present invention. In FIG. 2, this receiving apparatus includes an input terminal I to which a received OFDM signal is input, a band-pass filter 1, an automatic gain control amplifier 2, a quadrature detector 3, A / D converters 7 and 8, , A Fourier transformer 4, a demodulated data detector 5, a control signal output device 6, and an output terminal O are provided. The quadrature detector 3 includes a duplexer 31, detectors 32 and 33, and a carrier regenerator 34. The control signal output unit 6 includes an envelope detector 61, a reference timing generator 62, a symbol timing synchronization circuit 63, a symbol energy detector 64, a control signal switch 65, a sample hold unit 66, and a low pass filter 67. Including.

  FIG. 3 is a waveform diagram showing signals at various parts of the receiving apparatus shown in FIG. Hereinafter, the operation of the receiving apparatus of FIG. 2 will be described with reference to FIG.

  An OFDM signal (see FIG. 1) received by the receiving apparatus is converted from an occupied frequency band of the transmission path to an intermediate frequency band (center frequency fc) by a frequency converter (not shown), and then passed through an input terminal I to a band pass filter. 1 is input. The band pass filter 1 removes an unnecessary band signal component from the intermediate frequency band OFDM signal and extracts only the necessary band OFDM signal. The OFDM signal output from the band pass filter 1 is provided to the quadrature detector 3 via the automatic gain control amplifier 2.

  The duplexer 31 of the quadrature detector 3 demultiplexes the OFDM signal output from the automatic gain control amplifier 2 into two, and outputs the demultiplexed OFDM signals to the detectors 32 and 33, respectively. The carrier regenerator 34 outputs an in-phase carrier having the center frequency fc to the detector 32 and outputs a quadrature carrier having the center frequency fc to the detector 33. The detector 32 outputs the real part of the OFDM signal by multiplying the OFDM signal output from the duplexer 31 by the in-phase carrier. The detector 33 outputs the imaginary part of the OFDM signal by multiplying the OFDM signal output from the duplexer 31 by the orthogonal carrier. That is, the quadrature detector 3 converts the intermediate frequency band OFDM signal into a baseband OFDM signal. The A / D converter 7 converts the real part of the OFDM signal output from the detector 32 from an analog signal to a digital signal. The A / D converter 8 converts the imaginary part of the OFDM signal output from the detector 33 from an analog signal to a digital signal.

  The Fourier transformer 4 collectively performs a Fourier transform on the real part of the digital OFDM signal output from the A / D converter 7 and the imaginary part of the digital OFDM signal output from the A / D converter 8. By performing the calculation, the real part and the imaginary part of each digital modulated wave are separated on the frequency axis. Note that the Fourier transformer 4 has a clock terminal 4c and starts adjusting the time axis of the time window used for the Fourier transform based on the symbol synchronization signal output from the symbol timing synchronization circuit 63. Start Fourier transform. The demodulated data detector 5 maps the real part and imaginary part of each digital modulated wave on the complex plane, and demodulates the data obtained by modulating each carrier from the mapping position according to the threshold value set therein.

  The operation mode of the control signal output unit 6 includes a first mode in which the control signal of the automatic gain control amplifier 2 is generated based on the envelope waveform of the output signal of the quadrature detector 3, and the symbol energy of the output signal of the Fourier transformer 4. And a second mode for generating a control signal for the automatic gain control amplifier 2 based on The control signal output unit 6 operates in the first mode when the reception of the OFDM signal is started, and operates in the second mode after the operation of the Fourier transformer 4 is stabilized (that is, after synchronization with the received signal). Hereinafter, the operation of the control signal output unit 6 will be described in more detail.

  The envelope detector 61 outputs an envelope signal representing an envelope of each symbol by performing envelope detection on each symbol of the OFDM signal output from the detectors 32 and 33. The envelope signal output from the envelope detector 61 is supplied to the reference timing generator 62 and also to the control signal input terminal 65a of the control signal switch 65 via the low-pass filter 67 that smoothes the fluctuation.

  The reference timing generator 62 previously stores therein single tone data corresponding to a specific pattern of the symbol S0. Then, for each symbol, the reference timing generator 62 obtains the correlation between the envelope signal output from the envelope detector 61 and the stored single tone data along the time axis, thereby obtaining the symbol S0. A reference timing signal indicating whether or not is detected is output. That is, as shown in FIGS. 3A and 3B, the reference timing generator 62 outputs a high level (voltage Vhigh) reference timing signal when the symbol S0 is detected, and does not include a specific pattern. When Sm is detected, a low level (voltage Vlow) reference timing signal is output. Note that the reference timing generator 62 is in a low level (even during the asynchronous period) until the detection operation is stabilized (synchronized) with respect to the received signal even if the symbol S0 is received. A reference timing signal of voltage Vlow) is output. The reference timing signal output from the reference timing generator 62 is input to the symbol timing synchronization circuit 63 and the clock terminal 66c of the sample hold unit 66, respectively.

  The symbol timing synchronization circuit 63 outputs a symbol synchronization signal (see FIG. 3C) synchronized with each symbol based on the reference timing signal supplied from the reference timing generator 62. That is, the symbol timing synchronization circuit 63 includes a clock circuit therein, and each time a rising edge of the reference timing signal is detected, a clock pulse (symbol time ts is synchronized with the head of each symbol from the clock circuit for one cycle. Clock pulse), that is, a symbol synchronization signal is output. The symbol synchronization signal is input to the clock terminal 4c of the Fourier transformer 4 and the clock terminal 64c of the symbol energy detector 64, respectively.

  The symbol timing synchronization circuit 63 outputs a lock / unlock signal (see FIG. 3D) based on the reference timing signal provided from the reference timing generator 62. This lock / unlock signal indicates an unlocked state at a low level and indicates a locked state at a high level. At the beginning of reception, the lock / unlock signal is in the unlocked state. The symbol timing synchronization circuit 63 includes a counter that counts the clock pulses therein, and resets the counter every time the rising of the reference timing signal is detected. The symbol timing synchronization circuit 63 repeats a reset state a predetermined number of times when the internal counter reaches a predetermined count value (the symbol interval at which the symbol S0 is inserted, here 15) (that is, the symbol S0 is displayed). If the input is stable a predetermined number of times), it is determined that the adjustment of the time window in the Fourier transform circuit 4 has been completed, and the lock / unlock signal is switched from the unlocked state to the locked state. This lock / unlock signal is input to the clock terminal 65 c of the control signal switch 65.

  The symbol energy detector 64 includes a D / A converter (not shown) therein. The symbol energy detector 64 synchronizes the signal component of each carrier on the frequency axis of each symbol output from the Fourier transformer 4 in synchronism with the symbol synchronization signal provided from the symbol timing synchronization circuit 63 by a symbol calculation by a digital operation. The energy of each symbol is temporarily obtained as a digital value by square integration within ts (integration of the squared one). The obtained digital energy value is converted into an analog value by the D / A converter, thereby outputting an analog symbol energy signal representing the energy of each symbol. This energy is directly proportional to the average level of each symbol. The reason for squaring is to take the absolute value of each carrier because the amplitude of each carrier fluctuates positive and negative along the time axis. Also, the reason for integrating is to obtain the average. The symbol energy signal output from the symbol energy detector 64 is input to the control signal input terminal 65 b of the control signal switch 65.

Control signal switching device 65, lock / unlock signal inputted to the clock terminal 65c selects the envelope signal outputted from the envelope detector 61 when the unlocked state, Lock when the click state symbol energy detection The symbol energy signals output from the detector 64 are selected and output as control signals for the automatic gain control amplifier 2 respectively.

  The sample and hold unit 66 controls the clock terminal 66c when the reference timing signal of the voltage Vhigh is input from the reference timing generator 62, that is, when the specific symbol S0 is output from the automatic gain control amplifier 2. The control signal selected by the signal switcher 65 is sampled and held. The control signal held in the sample hold device 66 is given to the control terminal 2c of the automatic gain control amplifier 2. The gain A of the automatic gain control amplifier 2 changes according to the voltage level of the control signal supplied from the sample hold device 66.

  As the reception level of the OFDM signal increases, the level of the envelope signal or symbol energy signal of the symbol S0 increases in direct proportion to this, so that the voltage level of the control signal applied to the automatic gain control amplifier 2 increases. At this time, the automatic gain control amplifier 2 reduces the gain A so as to reduce the level of the received OFDM signal. On the other hand, if the reception level of the OFDM signal is reduced, the level of the envelope signal or symbol energy signal of the symbol S0 is also reduced in proportion to this, so that the voltage level of the control signal applied to the automatic gain control amplifier 2 is reduced. At this time, the automatic gain control amplifier 2 increases the gain A so as to increase the level of the received OFDM signal. As a result, the automatic gain control amplifier 2 can correct the variation in the reception level of the OFDM signal to an appropriate level.

  By the way, the symbol energy signal is the energy of each symbol S0, and since it is obtained by digital calculation, it contains almost no error. On the other hand, since the envelope signal is an envelope connecting the vertices of the waveform of each symbol S0, it includes a difference between the waveform of each symbol S0 and the envelope as an error. In addition, the envelope signal requires a filtering process (performed by the low-pass filter 67) to be used as a control signal for the automatic gain control amplifier 2, and an error also occurs in this filtering process. For this reason, the control accuracy of the gain of the automatic gain control amplifier 2 can be improved by using the symbol energy signal rather than the envelope signal.

  However, when the symbol synchronization signal is output from the symbol timing synchronization circuit 63, the Fourier transformer 4 starts adjusting the time axis of the time window used for the Fourier transform. Since it takes time, there is a possibility that a state in which the time window is not synchronized with the received symbol (that is, a state in which the time window is set across a plurality of adjacent symbols) may occur at the start of OFDM signal reception. . In such a state, normal operations of the Fourier transformer 4 and the symbol energy detector 64 are not guaranteed.

  Therefore, the control signal output unit 6 is in the first operation mode for a while after starting the reception of the OFDM signal (until the time axis adjustment of the time window of the Fourier transformer 4 is completely completed), that is, Based on the envelope signal of the symbol S0, the gain of the automatic gain control amplifier 2 is controlled. Thereafter, the control signal output unit 6 controls the gain of the automatic gain control amplifier 2 in the second operation mode, that is, based on the symbol energy signal of the symbol S0.

  As described above, according to the embodiment of FIG. 2, a specific symbol S 0 is periodically detected by the reference timing generator 62, and an envelope signal or symbol energy signal for the symbol S 0 is sampled and held by the sample hold unit 66. Since the feedback is made to the control terminal 2c of the automatic gain control amplifier 2, the accuracy of gain control of the automatic gain control amplifier 2 can be improved. In addition, attenuation in the transmission path is complemented by gain control, that is, the reception level is corrected, so that erroneous determination of demodulated data can be prevented.

  In the above embodiment, the symbol S0 is inserted at intervals of 15 symbols, but may be inserted at other symbol intervals. In the above embodiment, only one carrier is used as an unmodulated single tone signal, and the other carriers are suppressed to configure the symbol S0. However, the symbol S0 has a time axis component and a frequency axis component. It may be configured by other methods as long as it is a known signal whose amplitude and phase change along the time axis shows a predetermined specific pattern. For example, the amplitude of one carrier may be amplitude-modulated by a plurality of known data (for example, “1” data and “2” data). In this case, some irregularities occur in the envelope of the envelope signal output from the envelope detector 61, but since it is smoothed by the low-pass filter 67, it can be used as a control signal.

  In the above embodiment, the baseband OFDM signal output from the quadrature detector 3 is input to the envelope detector 61. However, if the automatic gain control amplifier 2 or later is used, the automatic gain control amplifier 2, A The output of any of the / D converters 7 and 8 and the Fourier transformer 4 may be input to the envelope detector 61.

  In the above embodiment, the output of the Fourier transformer 4 is inputted to the symbol energy detector 64. However, if the automatic gain control amplifier 2 or later is used, the automatic gain control amplifier 2, the quadrature detector 3, A / Any output of the D converters 7 and 8 may be input to the symbol energy detector 64.

  In the above-described embodiment, the A / D converters 7 and 8 are provided. However, the A / D converters 7 and 8 may be deleted, and the Fourier transform and the symbol energy detection may be performed without changing the analog.

  In the above embodiment, the control signal output unit 6 is configured to operate in two operation modes, but may be configured to operate only in the first operation mode. In this case, the control signal output device includes only the envelope detector 61, the reference timing generator 62, and the sample hold device 66.

  Further, the control signal output unit 6 may be configured to operate only in the second operation mode. In this case, the control signal output device includes only the envelope detector 61, the reference timing generator 62, the symbol timing synchronization circuit 63, the symbol energy detector 64, and the sample hold device 66.

  FIG. 4 is a diagram showing another example of the configuration of the OFDM signal transmitted from the transmission side to the reception side in the present invention. In particular, FIG. 4A shows each symbol of the OFDM signal along the time axis, and FIG. 4B shows an enlarged portion α of FIG. 4A.

  As shown in FIG. 4 (a), the OFDM signal S includes a specific symbol S0 for frequency conversion control indicated by hatching and a demodulation symbol Sm (m = 1, 2) indicated without hatching. ,...) Along the time axis. The symbol S0 is inserted every predetermined symbol interval (for example, every 15 symbol intervals). Note that such an OFDM signal S takes the form of a complex signal in which a real part and an imaginary part are superimposed on the symbols S0 and Sm on the transmission line.

  Each symbol Sm is formed by multiplexing (high-speed inverse Fourier calculation) a plurality of carriers (several tens to thousands, for example, 512) having different frequencies (which are orthogonal to each other at the symbol time ts) on the frequency axis. ing. Each carrier is digitally modulated (for example, QPSK modulation, 16QAM, etc.) with data to be demodulated on the receiving side. For this reason, each symbol Sm exhibits a random amplitude distribution as shown in FIG.

  Each symbol S0 is, for example, a pseudo-random signal by amplitude-modulating one of the plurality of carriers (for example, frequency fc) with a binary (for example, “1” and “2”) pseudo-random code. It is configured by performing a high-speed inverse Fourier calculation on the remaining carrier suppressed. For this reason, each symbol S0 indicates the amplitude distribution of a specific pattern as shown in FIG. Such a symbol S0 has a known time axis component and a known frequency axis component.

  The data speed of the pseudo random code is preferably selected to be an integer multiple of the OFDM symbol rate. By doing so, an integer number of pieces of pseudo-random code information can be accommodated in one symbol S0, and synchronization on the receiving side can be easily achieved. Moreover, it is preferable that the repetition period (repetition period) of the pattern of the pseudorandom code to be used is the same as the symbol period. In this case, the number of times one code (for example, “1”) appears is equal to the number of times the other code (for example, “2”) appears, making it easier to obtain a correlation on the receiving side.

  Incidentally, the OFDM signal S shown in FIG. 4 is sent from the transmission side to the reception side via a wired or wireless transmission path (not shown). For this reason, the transmission side (not shown) converts the OFDM signal S from the intermediate frequency band (center frequency fc) to the occupied frequency band (center frequency fr) of the transmission line. On the other hand, at the time of data demodulation, the received OFDM signal S is converted from the occupied frequency band of the transmission path to an intermediate frequency band (center frequency fc) for demodulation work. In the embodiment described below, the operation of converting the frequency of the OFDM signal S from the occupied frequency band to the intermediate frequency band is performed using the symbol S0. This is because the symbol S0 always includes a signal having the same pattern, so that the change in the frequency band can be accurately measured from the waveform of the symbol S0.

  FIG. 5 is a block diagram showing a configuration of a receiving apparatus according to the second embodiment of the present invention. In FIG. 5, the receiving apparatus includes an input terminal I to which the received OFDM signal is input, a frequency converter 10, a quadrature detector 3, a Fourier transformer 4, a demodulated data detector 5, and a control signal output device. 60 and an output terminal O. The quadrature detector 3 includes a branching device 31, detectors 32 and 33, and a carrier regenerator 34. The control signal output unit 60 includes an envelope detector 61, a reference timing generator 62, a symbol timing synchronization circuit 63, a sample hold unit 66, and a frequency discriminator 68. For the purpose of clarifying the correspondence, in the embodiment of FIG. 5, the same reference numerals are given to the same components as those of the embodiment of FIG.

  FIG. 6 is a waveform diagram showing signals at various parts of the receiving apparatus shown in FIG. Hereinafter, the operation of the receiving apparatus of FIG. 5 will be described with reference to FIG.

  An OFDM signal (see FIG. 6A) in the occupied frequency band (center frequency fr) of the transmission path received by the receiving apparatus is input to the input terminal I, and the intermediate frequency band (center frequency fc) is input by the frequency converter 10. After being converted to an OFDM signal, it is input to the quadrature detector 3.

  The demultiplexer 31 of the quadrature detector 3 demultiplexes the OFDM signal output from the frequency converter 10 into two, and outputs the demultiplexed OFDM signals to the detectors 32 and 33, respectively. The carrier generator 34 outputs the in-phase carrier having the center frequency fc to the detector 32 and outputs the quadrature carrier having the center frequency fc to the detector 33. The detector 32 outputs the real part of the OFDM signal by multiplying the OFDM signal output from the duplexer 31 by the in-phase carrier. The detector 33 outputs the imaginary part of the OFDM signal by multiplying the OFDM signal output from the duplexer 31 by the orthogonal carrier. That is, the quadrature detector 3 converts the intermediate frequency band OFDM signal into a baseband OFDM signal.

  The Fourier transformer 4 performs a Fourier transform operation on the real part of the OFDM signal output from the detector 32 and the imaginary part of the OFDM signal output from the detector 33 in a lump on the frequency axis. The real part and the imaginary part of each digital modulated wave are separated. The demodulated data detector 5 maps the real part and imaginary part of each digital modulated wave on the complex plane, and demodulates the data obtained by modulating each carrier from the mapping position according to the threshold value set therein.

  Next, the operation of the control signal output device 60 will be described in more detail. The envelope detector 61 outputs an envelope signal representing an envelope of each symbol by performing envelope detection on each symbol of the OFDM signal output from the frequency converter 10. The envelope signal output from the envelope detector 61 is given to the reference timing generator 62.

  The reference timing generator 62 stores therein binary pseudorandom data corresponding to a specific pattern of the symbol S0 in advance. Then, for each symbol, the reference timing generator 62 obtains the correlation between the envelope signal output from the envelope detector 61 and the stored binary pseudorandom data along the time axis, thereby obtaining the symbol S0. A reference timing signal indicating whether or not is detected is output. That is, as shown in FIGS. 6A and 6B, the reference timing generator 62 outputs a high-level (voltage V1) reference timing signal when detecting a symbol S0 including a specific pattern, and the specific pattern. When a symbol Sm that does not contain is detected, a low level (voltage V2) reference timing signal is output. The reference timing signal output from the reference timing generator 62 is input to the clock terminal 66 c of the sample hold unit 66 and the symbol timing synchronization circuit 63.

  The symbol timing synchronization circuit 63 outputs a symbol synchronization signal synchronized with each symbol based on the reference timing signal provided from the reference timing generator 62. That is, the symbol timing synchronization circuit 63 includes a clock circuit therein, and each time a rising edge of the reference timing signal is detected, a clock pulse (symbol time ts is synchronized with the head of each symbol from the clock circuit for one cycle. Clock pulse), that is, a symbol synchronization signal is output. This symbol synchronization signal is input to the clock terminal 64 c of the clock terminal 4 c of the Fourier transformer 4.

  The Fourier transformer 4 collectively performs a Fourier transform operation on the real part of the digital OFDM signal output from the detector 32 and the imaginary part of the digital OFDM signal output from the detector 33. The real part and the imaginary part of each digital modulated wave are separated on the frequency axis. Note that the Fourier transformer 4 has a clock terminal 4c and starts adjusting the time axis of the time window used for the Fourier transform based on the symbol synchronization signal output from the symbol timing synchronization circuit 63. Start Fourier transform. The demodulated data detector 5 maps the real part and imaginary part of each digital modulated wave on the complex plane, and demodulates the data obtained by modulating each carrier from the mapping position according to the threshold value set therein.

  The frequency discriminator 68 generates a voltage corresponding to the frequency of each symbol by frequency discriminating each symbol. The sample and hold unit 66 is configured to perform frequency discrimination when a reference timing signal of voltage V1 is input from the reference timing generator 62 to the clock terminal 66c, that is, when a specific symbol S0 is output from the frequency converter 10. The frequency discrimination signal output from the device 68 is sampled and held. The frequency discrimination signal held by the sample-and-hold device 66 is given to the control terminal 10c of the frequency converter 10 as a control signal. The frequency shift amount of the frequency converter 10 changes according to the voltage level of the control signal supplied from the sample and hold device 66.

  When the frequency band of the OFDM signal output from the frequency converter 10 becomes higher, the level of the frequency discrimination signal of the symbol S0 output from the frequency discriminator 68 increases in direct proportion to this, so that it is given to the frequency converter 10. The voltage level of the control signal to be increased. At this time, the frequency converter 10 increases the frequency shift amount so as to lower the frequency band of the output OFDM signal. On the other hand, when the frequency of the OFDM signal is lowered, the level of the frequency discrimination signal of the symbol S0 is also reduced in direct proportion to this, so that the voltage level of the control signal applied to the frequency converter 10 is reduced. At this time, the frequency converter 10 reduces the frequency shift amount so as to increase the frequency band of the output OFDM signal. As a result, the frequency converter 10 can correct the variation of the frequency band of the OFDM signal to an appropriate intermediate frequency band (center frequency fc).

  As described above, according to the second embodiment of FIG. 5, the reference timing generator 62 periodically detects a specific symbol S0, samples and holds the frequency discrimination signal in the symbol S0 as a control signal, and performs control. Since the signal is fed back to the control terminal 10c of the frequency converter 10, the accuracy of the frequency shift amount control of the frequency converter 10 can be improved. In addition, since fluctuations in the frequency band are corrected by frequency shift amount control, there is no deviation from the intermediate frequency band, and erroneous determination of demodulated data can be prevented.

  FIG. 7 is a block diagram showing the configuration of the receiving apparatus according to the third embodiment of the present invention. Note that portions corresponding to those of the receiving apparatus in FIG. 5 are denoted by the same reference numerals, and description thereof is omitted. What should be noted in the third embodiment is that the control signal output unit 70 is configured by using a frequency domain energy detector 71 instead of the frequency discriminator 68 of FIG.

  FIG. 8 is a waveform diagram for explaining the operation of the frequency domain energy detector 71 of FIG. 8A shows the power spectrum of the symbol S0 along the frequency axis, FIG. 8B shows the integrated value of the power spectrum of FIG. 8A, and FIG. 8C shows the frequency domain energy. The signal is shown. Hereinafter, the operation of the receiving apparatus of FIG. 7 will be described with reference to FIG.

  The frequency domain energy detector 71 performs a series of operations described below for each symbol in synchronization with the symbol synchronization signal supplied from the symbol timing synchronization circuit 63 with respect to the clock terminal 71c. First, as shown in FIG. 8A, the frequency domain energy detector 71 is amplitude-modulated by a carrier (binary pseudo-random signal) distributed in a frequency range of 0 to fs in the output of the Fourier transformer 4. Are divided into two regions α1 and α2 with (1/2) fs as a boundary. Here, fs is the frequency of the sampling clock used in the Fourier transformer 4. Further, since the spectrum of each symbol is folded back at the boundary of (1/2) fs, the high-frequency component is in the region α1 whose frequency is lower than (1/2) fs, and the low-frequency component is (1/1). 2) Appears in a region α2 having a frequency higher than fs.

  Next, as shown in FIG. 8B, the frequency domain energy detector 71 square-integrates each of the power spectrum component of the area α1 and the power spectrum component of the area α2, thereby obtaining the energy E1 of the area α1. And the energy E2 of the region α2. These energies E1 and E2 are proportional to the average level of each symbol. The reason for squaring is that the amplitude of each carrier varies positively and negatively along the time axis, so that the absolute value thereof is taken. Also, the integration is performed to obtain the average of each symbol.

  Next, the frequency domain energy detector 71 compares the energy E1 in the region α1 with the energy E2 in the region α2, and as shown in FIG. 8C, the voltage value corresponding to the energy difference (E1−E2). To generate a frequency domain energy signal. The frequency domain energy signal indicates a positive voltage value VHIGH when the energy E1 in the region α1 is larger, and a negative voltage value VLOW when the energy E2 in the region α2 is larger. By the way, in the symbol S0, when there is no frequency band shift, the power distributions in the regions α1 and α2 are equal, and the voltage value of the frequency domain energy signal is zero. Therefore, based on the polarity and voltage value of the frequency domain energy signal of the symbol S0, the deviation direction and the deviation amount from the center frequency fc are known.

  When the reference timing signal of voltage V1 is input from the reference timing generator 62 to the clock terminal 66c, that is, when the specific symbol S0 is output from the frequency converter 10, the sample-and-hold device 66 has a frequency domain. The frequency domain energy signal output from the energy detector 71 is sampled and held. The frequency domain energy signal held in the sample hold unit 66 is given to the control terminal 10c of the frequency converter 10 as a control signal. The frequency shift amount of the frequency converter 10 changes according to the voltage level of the control signal supplied from the sample and hold device 66.

  When the frequency band of the OFDM signal output from the frequency converter 10 increases, the voltage value VHIGH of the frequency domain energy signal of the symbol S0 output from the frequency domain energy detector 71 increases in the positive direction. The voltage of the control signal applied to is also increased in the positive direction. At this time, the frequency converter 10 increases the frequency shift amount so as to lower the frequency band of the output OFDM signal. On the other hand, when the frequency band of the OFDM signal is lowered, the voltage VLOW of the frequency domain energy signal of the symbol S0 is increased in the negative direction, so that the voltage of the control signal applied to the frequency converter 10 is also increased in the negative direction. At this time, the frequency converter 10 reduces the frequency shift amount so as to increase the frequency of the output OFDM signal. As a result, the frequency converter 10 can correct the variation of the frequency band of the OFDM signal to an appropriate intermediate frequency band (center frequency fc). Note that the control signal sampled and held by the sample hold unit 66 may be averaged over a plurality of periods of the symbol S0.

  As described above, according to the third embodiment of FIG. 7, the reference timing generator 62 periodically detects a specific symbol S0, samples and holds the frequency domain energy signal in the symbol S0 as a control signal, Since the feedback is made to the control terminal 10c of the frequency converter 10, the accuracy of the frequency shift amount control of the frequency converter 10 can be improved. In addition, since fluctuations in the frequency band are corrected by frequency shift amount control, there is no deviation from the intermediate frequency band, and erroneous determination of demodulated data can be prevented.

  FIG. 9 is a block diagram showing a configuration of a receiving apparatus according to the fourth embodiment of the present invention. Note that portions corresponding to those of the receiving apparatus in FIG. 5 are denoted by the same reference numerals, and description thereof is omitted. What should be noted in this embodiment is that the control signal output unit 80 is configured by using a correlation detector 81 and a peak value frequency detector 82 instead of the frequency discriminator 68 of FIG.

  FIG. 10 is a waveform diagram showing signals at various parts of the control signal output unit 80 of FIG. 10A shows the correlation signal along the frequency axis, and FIG. 10B shows the peak value frequency detection signal. Hereinafter, the operation of the receiving apparatus of FIG. 9 will be described with reference to FIG.

  The correlation detector 81 stores in advance information of an ideal frequency component for a specific symbol S0 as reference information. The correlation detector 81 obtains a correlation between the reference information and the data on the frequency axis output from the Fourier transformer 4, thereby outputting a correlation signal as shown in FIG. The correlation detection operation in the correlation detector 81 is performed for each symbol in synchronization with the symbol synchronization signal supplied from the symbol timing synchronization circuit 63 to the clock terminal 81c. In particular, a specific symbol S0 is generated from the Fourier transformer 4. It will be meaningful when output. Therefore, the case where a specific symbol S0 is output from the Fourier transformer 4 will be described. The correlation detector 81 temporarily stores the information of the symbol S0 as detection target information in an internal memory (not shown). Here, the reference information stored in advance by the correlation detector 81 and the detection target information stored in the internal memory are both digital pseudo-random signals that exist discretely on the frequency axis. The correlation detector 81 superimposes the detection target information and the reference information on the frequency axis, multiplies the pieces of code information included in each, and further obtains the sum of them. At this time, the correlation detector 81 obtains the sum of the multiplication results with the reference information while shifting the position of the detection target information on the frequency axis for each code unit. The set of sums becomes a correlation signal. The correlation signal exhibits a peak when the correspondence relationship between each piece of code information included in the detection target information and each piece of code information included in the reference information matches on the frequency axis.

  In the case where the symbol S0 is output from the Fourier transformer 4, for example, when the frequency shift Δf is “0”, the correlation detector 81 detects the position of the center frequency fc as indicated by β1 in FIG. A correlation signal having a peak value is output. Further, when the symbol S0 is output, for example, when there is a frequency shift Δf on the higher side, the correlation detector 81 shifts the appearance of the peak value as indicated by β2 in FIG. A correlation signal generated on the higher side in the frequency axis is output. Therefore, the frequency shift direction and the shift amount can be detected from such a correlation signal.

  The peak value frequency detector 82 compares the location of the peak value of the correlation signal output from the correlation detector 81 with the center frequency fc, and the peak value frequency signal having a voltage value ΔV corresponding to the difference Δf (see FIG. 10 (b)) is output.

  The sample and hold device 66 has a peak value when a reference timing signal of voltage V1 is input from the reference timing generator 62 to the clock terminal 66c, that is, when a specific symbol S0 is output from the frequency converter 10. The peak value frequency signal output from the frequency detector 82 is sampled and held. The peak value frequency signal held by the sample hold unit 66 is given to the control terminal 10c of the frequency converter 10 as a control signal. The frequency shift amount of the frequency converter 10 changes according to the voltage level of the control signal supplied from the sample and hold device 66.

  When the frequency band of the OFDM signal output from the frequency converter 10 increases, the level ΔV of the peak value frequency signal of the symbol S0 output from the peak value frequency detector 82 also increases in the positive direction. The voltage level of the applied control signal is increased. At this time, the frequency converter 10 increases the frequency shift amount so as to lower the frequency band of the output OFDM signal. On the other hand, when the frequency of the OFDM signal decreases, the level ΔV of the peak value frequency signal of the symbol S0 also increases in the negative direction, so that the voltage level of the control signal applied to the frequency converter 10 increases in the negative direction. At this time, the frequency converter 10 reduces the frequency shift amount so as to increase the frequency band of the output OFDM signal. As a result, the frequency converter 10 can correct the variation of the frequency band of the OFDM signal to an appropriate intermediate frequency band (center frequency fc).

  As described above, according to the fourth embodiment of FIG. 9, the reference timing generator 62 periodically detects a specific symbol S0, samples and holds the peak value frequency signal in the symbol S0 as a control signal, Since the feedback is made to the control terminal 10c of the frequency converter 10, the accuracy of the frequency shift amount control of the frequency converter 10 can be improved. In addition, since fluctuations in the frequency band are corrected by frequency shift amount control, there is no deviation from the intermediate frequency band, and erroneous determination of demodulated data can be prevented.

  In the second to fourth embodiments, the symbol S0 is inserted at intervals of 15 symbols, but may be inserted at intervals of other symbols. In the second to fourth embodiments, each symbol S0 is configured by amplitude-modulating only one carrier with a binary pseudorandom code and suppressing other carriers. Any other method may be used as long as the time axis component and the frequency axis component are known and the amplitude and phase changes along the time axis indicate a predetermined specific pattern. For example, a signal (see FIG. 1) in which only one carrier is used as an unmodulated single tone signal and the other carriers are suppressed may be used.

  In the second to fourth embodiments, the intermediate frequency band OFDM signal output from the frequency converter 10 is input to the envelope detector 61 (further, the frequency discriminator 68 in the second embodiment). However, if it is after the frequency converter 10, the output of either the quadrature detector 3 or the Fourier transformer 4 may be input to the envelope detector 61 (and the frequency discriminator 68).

  Further, in the third and fourth embodiments, the output of the Fourier transformer 4 is input to the frequency domain energy detector 71 and the correlation detector 81, respectively. The output of either the frequency converter 10 or the quadrature detector 3 may be input to the frequency domain energy detector 71 and the correlation detector 81.

  Further, the first embodiment is configured to correct the fluctuation of the reception level, and the second to fourth embodiments are configured to correct the fluctuation of the frequency band. By combining any of the modes with the first embodiment, a receiving circuit that can correct both the fluctuation of the reception level and the fluctuation of the frequency band may be configured.

  The transmission method and the reception method according to the present invention are useful for digital audio broadcasting or terrestrial digital television broadcasting that are required to prevent erroneous determination of demodulated data.

The figure which shows an example of a structure of the OFDM signal transmitted from the transmission side in this invention The block diagram which shows the structure of the receiver which concerns on the 1st Embodiment of this invention. Waveform diagram showing signals of each part of the receiving apparatus shown in FIG. The figure which shows the other example of a structure of the OFDM signal transmitted from a transmission side in this invention. The block diagram which shows the structure of the receiver which concerns on the 2nd Embodiment of this invention. Waveform diagram showing signals of each part of the receiving apparatus shown in FIG. The block diagram which shows the structure of the receiver which concerns on the 3rd Embodiment of this invention. Waveform diagram for explaining the operation of the frequency domain energy detector 71 shown in FIG. The block diagram which shows the structure of the receiver which concerns on the 4th Embodiment of this invention. FIG. 9 is a waveform diagram showing signals at various parts of the control signal output unit 80 shown in FIG. The figure which shows the structure of the conventional OFDM signal transmitted from the transmission side 1 is a block diagram showing the configuration of an OFDM signal receiving apparatus inferred from the first and third prior arts.

Explanation of symbols

DESCRIPTION OF SYMBOLS 1 Bandpass filter 2 Automatic gain control amplifier 3 Quadrature detector 31 Demultiplexer 32, 33 Detector 34 Carrier regenerator 4 Fourier transformer 5 Demodulated data detector 6 Control signal output unit 61 Envelope detector 62 Reference timing generator 63 Symbol timing synchronization circuit 64 Symbol energy detector 65 Control signal switch 66 Sample hold device 67 Low pass filter 7, 8 A / D converter 10 Frequency converter 60 Control signal output 68 Frequency discriminator 70 Control signal output 71 Frequency domain Energy detector 80 Control signal output unit 81 Correlation detector 82 Peak value frequency detector S OFDM signal S0, Sm symbol ts symbol time

Claims (13)

A method of transmitting as an orthogonal frequency division multiplexed signal for each symbol including a plurality of carriers having a frequency relationship orthogonal to each other,
Send the first symbol,
Send the second symbol,
It said first symbol includes an integer number of known pseudo-random information in the time axis component,
Said second symbol, Ruki Yaria included in the symbols are by Ri modulation to the transmission data, the transmission method. A method of receiving an orthogonal frequency division multiplex signal transmitted for each symbol including a plurality of carriers having a frequency relationship orthogonal to each other,
Receiving the first symbol,
Receiving a second symbol;
It said first symbol includes an integer number of known pseudo-random information in the time axis component,
Said second symbol, Ruki Yaria included in the symbols are by Ri modulation on transmission data,
A reception method of demodulating the second symbol to obtain the transmission data based on synchronization information obtained from the received first symbol.   The reception method according to claim 2, wherein fluctuation in a frequency band is corrected based on the received first symbol.   The reception method according to claim 2 or 3, wherein fluctuations in reception level are corrected based on the received first symbol. A method of transmitting as an orthogonal frequency division multiplexed signal for each symbol including a plurality of carriers in a frequency relationship orthogonal to each other from a transmission side to a reception side via a wired or wireless transmission path,
The sender side
Send the first symbol,
Send the second symbol,
It said first symbol includes an integer number of known pseudo-random information in the time axis component,
Said second symbol, Ruki Yaria included in the symbols are by Ri modulation on transmission data,
The receiving side
Receiving the second symbol;
Receiving the first symbol;
A transmission method of demodulating the second symbol to obtain the transmission data based on synchronization information obtained from the received first symbol.   The transmission method according to claim 5, wherein fluctuations in a frequency band are corrected based on the received first symbol.   The transmission method according to claim 5 or 6, wherein fluctuations in reception level are corrected based on the received first symbol. A receiving device for receiving an orthogonal frequency division multiplex signal transmitted for each symbol including a plurality of carriers having a frequency relationship orthogonal to each other,
The receiving device includes receiving means for receiving the orthogonal frequency division multiplexing signal,
The orthogonal frequency division multiplexing signal includes a first symbol and a second symbol,
It said first symbol includes an integer number of known pseudo-random information in the time axis component, further,
Said second symbol, Ruki Yaria included in the symbols are by Ri modulation on transmission data,
The receiving apparatus further comprises demodulation means for demodulating the second symbol to obtain the transmission data based on the synchronization information obtained from the received first symbol.   The receiving device according to claim 8, wherein the receiving device corrects a fluctuation in a frequency band based on the received first symbol.   The receiving device according to claim 8 or 9, wherein the receiving device corrects a variation in reception level based on the received first symbol. A method of generating an orthogonal frequency division multiplex signal transmitted for each symbol including a plurality of carriers having a frequency relationship orthogonal to each other,
Generate a first symbol,
Generate a second symbol,
The first symbol includes an integer number of known pseudo-random information in the time axis component,
The second symbol is an orthogonal frequency division multiplex signal generation method in which a carrier included in the symbol is modulated by transmission data. A method of demodulating an orthogonal frequency division multiplexed signal transmitted for each symbol including a plurality of carriers having a frequency relationship orthogonal to each other,
The orthogonal frequency division multiplexing signal includes a first symbol and a second symbol,
The first symbol includes an integer number of known pseudo-random information in the time axis component,
In the second symbol, a carrier included in the symbol is modulated by transmission data,
A demodulation method of demodulating the second symbol to obtain the transmission data based on synchronization information obtained from the received first symbol. A demodulator that demodulates an orthogonal frequency division multiplex signal transmitted for each symbol including a plurality of carriers having a frequency relationship orthogonal to each other,
The orthogonal frequency division multiplexing signal includes a first symbol and a second symbol,
The first symbol includes an integer number of known pseudo-random information in the time axis component, and
In the second symbol, a carrier included in the symbol is modulated by transmission data,
The demodulator includes a demodulator that demodulates the second symbol and obtains the transmission data based on synchronization information obtained from the received first symbol.

Images