JP2016201584A - High-frequency resonator and high-frequency oscillator - Google Patents

Abstract

PROBLEM TO BE SOLVED: To obtain a high-frequency resonator capable of suppressing resonance at a high frequency side, independently of strength/weakness of coupling.SOLUTION: A high-frequency resonator comprises: a first transmission line whose one end is short-circuited; a second transmission line arranged in parallel to the first transmission line, electromagnetically coupled with the first transmission line, and whose one end at an opposite side to the short-circuited end of the first transmission line is short-circuited; a first reactance circuit whose one end is connected to a midpoint of the first transmission line; a second reactance circuit whose one end is connected to a midpoint of the second transmission line, and whose the other end is connected with the other end of the first reactance circuit; and a resistor whose one end is connected with a connection point between the first reactance circuit and the second reactance circuit, and whose the other end is grounded.SELECTED DRAWING: Figure 1

Description

  The present invention relates to a high frequency resonator and a high frequency oscillator.

  As a conventional high-frequency resonator, there is an interdigital coupling resonator disclosed in Patent Document 1, which is used for a band-pass filter. This coupled resonator is composed of two transmission lines each having a quarter wavelength at the resonance frequency when not coupled, and each of the transmission lines has one end short-circuited and the other end open. These transmission lines are arranged in parallel so that the short-circuit points are staggered. Such a resonator is called an interdigital resonator. The high-frequency input terminal is tap-coupled to one transmission line, the high-frequency output terminal is tap-coupled to the other transmission line, and these tap coupling points are mutually connected with respect to the rotational symmetry axis of the coupled resonator having the rotational symmetry axis. It is arranged at a position that is rotationally symmetric.

Next, the operation of the conventional high frequency resonator will be described.
By narrowing the interval between the transmission lines arranged in the interdigital type (hereinafter referred to as “gap”), the transmission line is strongly coupled, and the interdigital coupling resonator has two resonance frequencies. One resonance frequency is a resonance frequency lower than the resonance frequency at the time of non-coupling, and the other resonance frequency is a resonance frequency higher than the resonance frequency at the time of non-coupling. The conventional high-frequency resonator utilizes the fact that the capacitance between the coupled lines depends on the resonance mode, and reduces the gap to increase the capacitance change with respect to the resonance mode. Resonance was obtained. As described above, the conventional high-frequency resonator has a high-frequency resonance sufficiently high and uses a low-frequency resonance to obtain a small resonator and a band-pass filter.

JP 2007-60618 A

  In the conventional high frequency resonator, the coupling between the transmission lines depends on the gap, and when the strong coupling is difficult due to the limitation of the manufacturing accuracy, the resonance frequency on the low frequency side and the high frequency side cannot be sufficiently separated. For this reason, even if an attempt is made to operate the circuit using resonance on the low frequency side, there is a problem that unnecessary resonance on the high frequency side adversely affects circuit characteristics. In particular, in an oscillator using the resonator, there has been a problem of unnecessary oscillation due to unnecessary resonance on the high frequency side.

  The present invention has been made to solve the above-described problems, and provides a high-frequency resonator that exhibits an effect of suppressing high-frequency resonance regardless of coupling strength and a high-frequency oscillator using the same. For the purpose.

  The high-frequency resonator of the present invention is arranged in parallel with the first transmission line whose one end is short-circuited and the first transmission line, and is electromagnetically coupled to the first transmission line. A second transmission line whose one end opposite to the short-circuited end is short-circuited, a first reactance circuit whose one end is connected to the midpoint of the first transmission line, and a midpoint of the second transmission line One end is connected to the connection point between the first reactance circuit and the second reactance circuit, the second reactance circuit having one end connected and the other end connected to the other end of the first reactance circuit. And a grounded resistor.

  According to the present invention, there is an effect that the resonance on the high frequency side can be suppressed without affecting the resonance on the low frequency side regardless of the strength of the coupling between the transmission lines in the high frequency resonator.

1 is a diagram illustrating a configuration example of a high-frequency resonator according to a first embodiment. FIG. 3 is a diagram illustrating a resonance frequency of the high frequency resonator according to the first embodiment. FIG. 3 is a circuit diagram of an even mode in the high frequency resonator according to the first embodiment. It is a figure which shows the voltage distribution in the even mode of a transmission line. FIG. 3 is a circuit diagram of an odd mode in the high frequency resonator according to the first embodiment. It is a figure which shows the voltage distribution in the odd mode of a transmission line. FIG. 6 is a diagram illustrating another configuration example of the high-frequency resonator according to the first embodiment. It is a figure explaining the change of the resonant frequency in the resonator of FIG. It is a layout figure which shows the structural example of the high frequency resonator which concerns on Embodiment 1 of this invention. It is a figure which shows the structural example of the high frequency resonator in case there is one terminal. 5 is a diagram illustrating a configuration example of a high-frequency resonator according to a second embodiment. FIG. FIG. 10 is a diagram illustrating another configuration example of the high frequency resonator according to the second embodiment. 6 is a diagram illustrating a configuration example of a high-frequency oscillator according to Embodiment 3. FIG. FIG. 10 is a diagram illustrating a configuration example of a high-frequency oscillator according to a fourth embodiment. FIG. 10 is a diagram illustrating another configuration example of the high-frequency oscillator according to the fourth embodiment. FIG. 9 is a diagram illustrating a configuration example of a high-frequency oscillator according to a fifth embodiment. 10 is another configuration example of the high-frequency oscillator according to the fifth embodiment.

Embodiment 1
FIG. 1 is a diagram illustrating a configuration example of a high-frequency resonator according to the first embodiment.
In FIG. 1, a high-frequency resonator 1 includes a transmission line 103 (an example of a first transmission line), a transmission line 104 (an example of a second transmission line), a capacitor 105 (an example of a first reactance circuit), a capacitor 106 (an example of a second reactance circuit) and a resistor 107 (an example of a resistor). The high-frequency resonator 1 is connected to a terminal 101 (an example of a terminal) and a terminal 102 (an example of a terminal). In FIG. 1, “@” means that the frequency after “@” is a frequency. For example, λ / 8 @ f ₀ means that the electrical length is λ / 8 at the frequency f ₀ .

The terminal 101 is a terminal to which a signal is input or output, and is a terminal connected to the transmission line 103 at a position away from the short-circuited end of the transmission line 103 by an electrical length α by tap coupling. Here, the tap coupling is to connect a terminal to which a signal is input or output to a portion other than the short-circuited end of the resonator (here, the transmission line).
The terminal 102 is a terminal to which a signal is input or output, and is a terminal connected to the transmission line 104 at a position away from the short-circuited end of the transmission line 104 by an electrical length α by tap coupling.

Each of the transmission lines 103 and 104 is open and short-circuited at one end, has an electrical length of ¼ wavelength at the resonance frequency f ₀ when not coupled, and the short-circuited ends are opposite to each other and arranged in parallel to each other. Transmission line. The transmission lines 103 and 104 are configured by, for example, a microstrip line, a strip line, a slot line, a coplanar line, or the like.

The capacitor 105 is a capacitor having one end connected to the midpoint of the transmission line 103 and the other end connected to the capacitor 106 and the resistor 107. Here, the midpoint is the center in the length direction of the transmission line 103 and is the electrical length center between the open end and the short-circuited end of the transmission line 103.
The capacitor 106 is a capacitor having one end connected to the midpoint of the transmission line 104 and the other end connected to the capacitor 105 and the resistor 107. Here, the midpoint is the center in the length direction of the transmission line 104 and is the electrical length center between the open end and the short-circuited end of the transmission line 104.

  The resistor 107 is a resistor having one end connected to the capacitors 105 and 106 and the other end grounded. That is, the resistor 107 is connected to the connection point between the capacitor 105 and the capacitor 106.

Next, the operation of the high frequency resonator according to the first embodiment will be described.
When the gap (gap) between the transmission line 103 and the transmission line 104 arranged in parallel becomes narrower, the coupling between the transmission line 103 and the transmission line 104 becomes stronger, and the capacitance between the lines starts to affect the resonance frequency, and f ₀ In contrast, resonance occurs on the low frequency side (f _L ) and the high frequency side (f _H ). At this time, f _L operates in the odd mode, f _H operates in the even mode.

FIG. 2 is a diagram illustrating the resonance frequency of the high-frequency resonator according to the first embodiment.
In FIG. 2, the vertical axis represents Z (impedance) or Y (admittance), and is an index of the strength or absence of resonance. The horizontal axis is frequency. The dotted line represents the resonance frequency f ₀ when the gap is infinite, that is, in the case of non-coupling. The solid line represents the resonance frequency when the transmission line 103 and the transmission line 104 are coupled. When the gap becomes smaller, the transmission line 103 and the transmission line 104 are electromagnetically coupled, and the resonance frequency is separated into two. the resonance frequency f _L of the low-frequency side is a resonance frequency of the odd mode with respect to f _0, the resonance frequency f _H of the high-frequency side is a resonance frequency of the even mode for f _0.

FIG. 3 is a circuit diagram of an even mode in the high frequency resonator according to the first embodiment.
In FIG. 3, the arrows in the transmission lines 103 and 104 indicate the direction in which the voltage increases. As shown in FIG. 3, since f _H operates in an even mode, the resistor 107 can be seen through the capacitor 105 and the capacitor 106, and a high-frequency current flows through the resistor 107, causing a loss. The reason will be described below.

FIG. 4 is a diagram illustrating a voltage distribution in the even mode of the transmission line.
In FIG. 4, the vertical axis represents the voltage V of the transmission lines 103 and 104, and the horizontal axis represents the electrical length L from the short-circuited end. α is a position where the transmission lines 103 and 104 are tapped. The voltage is 0 at the short-circuited end, and the voltage increases toward the open end.

The operation in the even mode of the circuit including the capacitor 105, the capacitor 106, and the resistor 107 will be described. In FIG. 3, the capacitor 105 and the capacitor 106 are connected to the midpoint of the transmission line 103 or the transmission line 104. That is, the capacitor 105 and the capacitor 106 are connected at a position of λ / 8 from the short-circuit end. Therefore, the voltage at the point where the capacitor 105 is connected and the voltage at the point where the capacitor 106 is connected have the same value. Since the connection point between the capacitor 105 and the capacitor 106 is the same voltage, no current flows from the transmission line 103 to the transmission line 104 via the capacitor 105 and the capacitor 106, and the current flows through the resistor 107 having one end grounded. In the even mode, current flows through the resistor 107, in this resonator, the loss becomes large at f _H.

FIG. 5 is a circuit diagram of an odd mode in the high frequency resonator according to the first embodiment.
In FIG. 5, arrows in the transmission lines 103 and 104 indicate directions in which the voltage increases. As shown in FIG. 3, since f _L operates in an odd mode, the transmission lines 103 and 104 operate in reverse phase, and a virtual short circuit occurs at the connection point between the capacitor 105 and the capacitor 106. For this reason, the resistor 107 is not visible, a high frequency current does not flow through the resistor 100, and no loss occurs. The reason will be described below.

FIG. 6 is a diagram illustrating a voltage distribution in an odd mode of the transmission line.
In FIG. 6, the vertical axis represents the voltage V of the transmission lines 103 and 104, and the horizontal axis represents the electrical length L from the short-circuited end. α is a position where the transmission lines 103 and 104 are tapped. The voltage is 0 at the short-circuited end of the transmission line 103, and the voltage increases toward the open end. On the other hand, in the transmission line 104, the voltage is 0 at the short-circuited end, but the voltage decreases toward the open end. This is because the transmission line 103 and the transmission line 104 operate in an odd mode.

The operation in the odd mode of the circuit including the capacitor 105, the capacitor 106, and the resistor 107 will be described. In FIG. 5, the capacitor 105 and the capacitor 106 are connected to the midpoint of the transmission line 103 or the transmission line 104. That is, the capacitor 105 and the capacitor 106 are connected at a position of λ / 8 from the short-circuit end. For this reason, the voltage at the point where the capacitor 105 is connected and the voltage at the point where the capacitor 106 is connected have the same absolute value and opposite values. Since the connection point between the capacitor 105 and the capacitor 106 is a reverse voltage, a virtual short circuit is formed at the connection point between the capacitor 105 and the capacitor 106. In this case, since it is considered equivalent to that a ground is connected to the connection point between the capacitor 105 and the capacitor 106, no current flows through the resistor 107. Therefore, in this resonator, the loss does not occur in f _L.

In this high frequency resonator, the tap coupling position of the terminal 101 and the tap coupling position of the terminal 102 are
The transmission lines 103 and 104 have the same electrical length from the short-circuit end. Therefore, as shown in FIGS. 4 and 6, since the voltage amplitude at α has the same value, the terminal 101 and the terminal 102 are connected to the transmission lines 103 and 104 with the same degree of coupling. Therefore, even if the terminal 101 and the terminal 102 are provided, the high-frequency resonator maintains electrical symmetry, can suppress the resonance of an unnecessary mode other than the even mode or the odd mode, and can be caused by the resonance of the unnecessary mode. Loss can be reduced.

If the electrical length from the shorted end of the terminal 101 is different from the electrical length from the shorted end of the terminal 102, the degree of coupling of the terminal 101 and the degree of coupling of the terminal 102 are different. Therefore, the high-frequency resonator cannot maintain electrical symmetry, and resonates in a mixed mode in which an even mode and an odd mode are mixed, for example, at f _L and f _H. As a result, since losses in the resistor 107 by the even mode components in the mixed mode occurs, loss in f _L increases. Further, since the loss of the odd mode component in the mixed mode at f _H is not caused by the resistor 107, the loss at f _H is reduced and the suppression amount of resonance is reduced.

  As described above, according to the first embodiment, in the high frequency resonator 1, one end of the capacitor 105 is connected to the midpoint of the transmission line 103, and one end of the capacitor 106 is connected to the midpoint of the transmission line 104. Thus, the resonance on the high frequency side is suppressed regardless of the strength of the electromagnetic field coupling, and the resonance on the low frequency side can be achieved.

  Further, since the terminal 101 and the terminal 102 are tap-coupled to the high-frequency resonator, the degree of coupling with the high-frequency resonator can be easily changed by changing the position of the tap coupling. Thereby, when realizing an oscillator, a filter, etc. using this high frequency resonator, since a characteristic can be changed by a tap position, there exists an advantage that it is easy to design.

In addition, this high-frequency resonator can obtain a steep frequency characteristic as compared with a high-frequency resonator using a conventional coupled line. Thereby, when this high frequency resonator is used for an oscillator, the phase noise of the oscillator can be reduced. Further, when this high-frequency resonator is used as a filter, it is possible to increase the amount of attenuation with respect to a signal having an unnecessary frequency.
Hereinafter, the reason why steep frequency characteristics can be obtained in this high frequency resonator will be described. Generally, the unloaded Q (Q _u0 ) of the resonator is expressed by the following equation. Q _u0 is the no-load Q at f ₀ .

ここで、Ｇ_ｒ、Ｃ_ｒ、Ｌ_ｒは、それぞれ、伝送線路を形成する基板の誘電体および伝送線路の導体による等価コンダクタンス、等価キャパシタンス、等価インダクタンスである。ω_０は共振角周波数である。本共振器では、この等価キャパシタンスＣ_ｒに、キャパシタ１０５、１０６による容量が加わるため、低域側の共振周波数における無負荷Ｑ（Ｑ_ｕＬ）はさらに大きくなる。Ｑ値が高いと周波数特性は急峻であるため、急峻な周波数特性が得られる。

Here, G _r , C _r , and L _r are an equivalent conductance, an equivalent capacitance, and an equivalent inductance due to the dielectric of the substrate that forms the transmission line and the conductor of the transmission line, respectively. ω ₀ is the resonance angular frequency. In this resonator, this equivalent capacitance _{C r,} to join the capacitance of the capacitor 105 and 106, the unloaded Q at a resonant frequency of the low frequency side _{(Q uL)} is further increased. When the Q value is high, the frequency characteristic is steep, so that a steep frequency characteristic can be obtained.

The high frequency resonator according to the first embodiment may have the following configuration.
FIG. 7 is a diagram illustrating another configuration example of the high-frequency resonator according to the first embodiment.
FIG. 7A is a configuration diagram when the capacitors 105 and 106 are variable capacitors.
Even with this configuration, the above-described effects can be obtained. Furthermore, in this configuration, since it is to change the capacitance value of the capacitor 105 and capacitor 106, it is possible to change the resonance frequency f _L of the low-frequency side. Thereby, when this high frequency resonator is used as an oscillator, the oscillation frequency of the oscillator can be changed, and a plurality of oscillators having different oscillation frequencies can be realized by one oscillator. Further, when this high-frequency resonator is used as a filter, the pass frequency or cut-off frequency can be made variable, and a plurality of filters having different frequency bands can be realized by one filter.

FIG. 7B is a configuration diagram when a variable capacitor is provided at the open end of the transmission line.
As shown in FIG. 7B, even if the open ends of the transmission line 103 and the transmission line 104 are each provided with variable capacitors 105 and 106 having one end grounded, the capacitance component of each transmission line can be changed. Therefore, the resonance frequency can be changed. Alternatively, the capacitor 105 and the capacitor 106 may be variable capacitors, and the configuration shown in FIGS. 7A and 7B may be combined. The same applies to the other embodiments.

FIG. 8 is a diagram for explaining a change in the resonance frequency in the resonator of FIG.
In FIG. 8, the vertical axis represents Z (impedance) or Y (admittance), which is an index of the strength or absence of resonance. The horizontal axis is frequency. The dotted line represents the resonance frequency f ₀ when the gap is infinite, that is, in the case of non-coupling. The solid line represents the resonance frequency when the transmission line 103 and the transmission line 104 are coupled. By varying the capacitance of the capacitor 105 and capacitor 106, without changing the f _H, it is possible to change the f _L.

Hereinafter, a layout configuration when the high-frequency resonator according to the first embodiment is formed on a dielectric substrate will be described.
FIG. 9 is a layout diagram illustrating a configuration example of the high-frequency resonator according to the first embodiment.
FIG. 9A is a layout diagram in the case where the transmission line 103 and the transmission line 104 are arranged on the same dielectric substrate.
FIG. 9B is a layout diagram when the transmission line 103 and the transmission line 104 are arranged on different laminated dielectric substrates, respectively.
FIG. 9C is a layout diagram in which the transmission line 103 and the transmission line 104 are arranged on different laminated dielectric substrates, respectively, and the transmission line 103 and the transmission line 104 are overlapped.
FIG. 9D is a layout diagram of a configuration in which the transmission line 103 and the transmission line 104 are arranged on different laminated dielectric substrates, respectively, and a part of the transmission line 103 and a part of the transmission line 104 are overlapped. .
As shown in FIG. 9A, the transmission line 103 and the transmission line 104 may be disposed on the same layer layer of the dielectric substrate. Moreover, as shown in FIG.9 (b), you may arrange | position to a different layer layer. As shown in FIG. 9B, by providing the transmission line 103 and the transmission line 104 in different layer layers, the strength of electromagnetic coupling between the transmission line 103 and the transmission line 104 is also changed depending on the distance between the layer layers. Therefore, the degree of freedom in designing the high frequency resonator can be increased.
Further, as shown in FIGS. 9C and 9D, they may be arranged in different layer layers to cause overlap. Here, the overlap means an overlap of the transmission lines with respect to the upper and lower sides. In the case of the structure shown in FIGS. 9C and 9D, the strength of electromagnetic coupling between the transmission line 103 and the transmission line 104 is changed by increasing the overlap between the transmission line 103 and the transmission line 104. Therefore, the design freedom of the high frequency resonator can be increased. The configuration example shown in FIG. 9 can be applied to other embodiments.

Heretofore, the case where there are two terminals in the high-frequency resonator has been described, but there may be one terminal.
FIG. 10 is a diagram illustrating a configuration example of a high-frequency resonator when there is one terminal.
Compared with FIG. 1, the terminal 102 is deleted. Even in this configuration, since the transmission line 103 and the transmission line 104 are electromagnetically coupled in the even mode and the odd mode, as described above, the frequency f _{H is} not affected without affecting the resonance frequency of f _L. Can be suppressed. In the case of FIG. 10, the signal is input from the terminal 101, but the signal is reflected by the high-frequency resonator 1 at f _L and output from the terminal 101. The signal of f _H is absorbed by the resistor 107.

Embodiment 2. FIG.
FIG. 11 is a diagram illustrating a configuration example of the high-frequency resonator according to the second embodiment.
In FIG. 11, the same reference numerals as those in FIG. 1 denote the same or corresponding parts, and the description thereof is omitted.
Frequency resonator according to the second embodiment has the structure in which a parallel resonance circuit 2 to the high-frequency resonator 1 is connected to suppress the unwanted resonance other than the resonance frequency f _L of the low-frequency side, the resonance frequency of f _L Is made available.

The parallel resonant circuit 2 includes an inductor 201 and a capacitor 202 connected in parallel to each other, is a parallel resonant circuit that is tap-coupled to the transmission line 104 and performs parallel resonance at the resonance frequency f _L on the low frequency side. One end of the parallel resonant circuit 2 is grounded, and the other end is connected to the terminal 102. The parallel resonant circuit 2 only needs to be tapped to at least one of the transmission line 103 or the transmission line 104.

Next, the operation of the high frequency resonator according to the second embodiment will be described.
Since the internal operation of the high-frequency resonator 1 is the same as that of the first embodiment, the description thereof is omitted.
A signal is input from the terminal 101 to the high-frequency resonator 1. Since the high frequency resonator 1 operates in the even mode at f _H, signal _{f H} is absorbed by resistor 107 through capacitor 105 and capacitor 106.

On the other hand, the f _L, a high frequency resonator 1 operates in the odd mode. Therefore, since a virtual short circuit is formed at the connection point between the capacitor 105 and the capacitor 106, no signal flows through the resistor 107 and no loss occurs. Therefore, the signal input from the terminal 101 is output from the terminal 102 to the parallel resonant circuit 2 via the transmission line 103 and the transmission line 104 that are electromagnetically coupled in an odd mode.

Since the parallel resonance circuit 2 resonates at the resonance frequency f _L on the low frequency side, its impedance is open. Therefore, the signal output from the terminal 102, totally reflected at _{f L.} The signal totally reflected by the parallel resonant circuit 2 is input from the terminal 102 to the high frequency resonator 1. The reflected signal is output from the terminal 101 through the transmission line 103 and the transmission line 104 that are electromagnetically coupled in an odd mode, as in the case of the input. That is, in this configuration, the signal input from the terminal 101 is totally reflected at f _L and output from the terminal 101.

Against the resonance frequency f _L other signals of the low frequency side, the parallel resonance circuit 2 has a finite impedance. Then, a finite impedance is connected to the transmission line 104, and the symmetry between the transmission line 103 and the transmission line 104 is lost. Therefore, the transmission line 103 and the transmission line 104 do not resonate in a single mode of odd mode or even mode, but resonate in a mixed mode of even mode and odd mode. Among them, the even mode causes a loss due to the resistor 107. Therefore, the high frequency resonator 1 gives a loss to signals other than f _L and attenuates the signal. The attenuated signal is output from the terminal 101.

As described above, according to the second embodiment, to suppress the unwanted resonance other than the resonance frequency f _L of the low-frequency side, an effect that can utilize the resonance frequency of f _L.

Here, an example using a parallel resonant circuit in which a capacitor 201 and an inductor 202 are connected in parallel has been described, but a parallel resonant circuit may be configured as follows.
FIG. 12 is a diagram illustrating another configuration example of the high-frequency resonator according to the second embodiment.
The parallel resonant circuit 2 includes a λ / 4 transmission line 203 and a series resonant circuit 204. The transmission line 203 is a transmission line having a length of λ / 4 at f _L. The series resonance circuit 204 is a series resonance circuit in which one end that resonates at f _L is grounded. The series resonant circuit 204 and the transmission line 203 are connected in series, and the transmission line 203 is connected to the terminal 102. In addition, the transmission line 203 is comprised by a microstrip line, a strip line, a slot line, a coplanar line etc., for example.

The impedance of the parallel resonant circuit 2 will be described. The series resonance circuit 204 performs series resonance at f _L , and the impedance becomes a short circuit. Since the transmission line 203 of λ / 4 operates as an impedance inverter, the impedance of the series resonance circuit 204 is inverted. Therefore, the impedance when the series resonant circuit 204 side is viewed from the terminal 102 is an open circuit opposite to the short circuit.
As described above, even a configuration in which the transmission line 203 and the series resonance circuit 204 are connected in series operates as a parallel resonance circuit. The same applies to other embodiments.

Embodiment 3 FIG.
In the first and second embodiments, the high-frequency resonator has been described. In the following third to fifth embodiments, an oscillator using the resonator will be described.
FIG. 13 is a diagram illustrating a configuration example of the high-frequency oscillator according to the third embodiment.
In FIG. 13, the same reference numerals as those in FIG. 1 denote the same or corresponding parts, and the description thereof is omitted.
The high frequency oscillator includes a high frequency resonator 1 and an active circuit 3. The high frequency resonator 1 is connected to the active circuit 3 in parallel.

The active circuit 3 is an active circuit having a gain at f _L. The active circuit 3 includes a transistor and a matching circuit. The active circuit 3 and the high frequency resonator 1 are connected in parallel. The sum of the passing phase of the active circuit 3 and the passing phase of the high-frequency resonator 1 is an integral multiple of 360 ° (including 0) at f _L. Further, the sum of the gains (loop gain) is 0 dB or more. That is, the high frequency resonator 1 forms a positive feedback that satisfies the oscillation condition with respect to the active circuit 3.

Next, the operation of the high frequency oscillator according to Embodiment 3 will be described.
High frequency noise near the resonance frequency f _L existing in the circuit is input to the terminal 301 of the active circuit 3. Next, the active circuit 3 amplifies the power and outputs it to the terminal 101 of the high-frequency resonator 1. Power input to the terminal 101 of the high frequency resonator 1, the resonance frequency f _L, passes through a low loss than other frequencies. The electric power that has passed through the high-frequency resonator 1 is input to the terminal 301 of the active circuit 3 again via the terminal 102. Since the active circuit 3 and the high-frequency resonator 1 are configured to be positive feedback, the original high-frequency noise is further amplified and finally oscillates.

As described in the first embodiment, the high-frequency resonator 1 is odd because the one end of the capacitor 105 is connected to the midpoint of the transmission line 103 and the one end of the capacitor 106 is connected to the midpoint of the transmission line 104. Symmetry is maintained for each of the mode and even mode. For the resonance frequency f _H of the high-frequency side of the operation loss due to the resistance 100 is suppressed occurring in the even mode, can not satisfy the loop gain of the oscillation condition, high frequency noise in the vicinity of f _H is not lead to oscillation, Unnecessary oscillation is suppressed.

As described above, according to the third embodiment, since the high-frequency resonator 1 having the low-frequency side resonance is suppressed and the high-frequency side resonance of the high-frequency resonator is suppressed, the high-frequency side is unnecessary in the oscillator. Oscillation can be suppressed, and the effect of obtaining oscillation on the low frequency side is achieved. In addition, the transmission lines 103 and 104 having an electrical length of ¼ wavelength at the resonance frequency f ₀ at the time of non-coupling can be used to oscillate at f _L , thereby achieving an effect of miniaturization. In addition, since the high-frequency resonator 1 has a high Q value, it is possible to reduce the phase noise of the high-frequency oscillator.

Embodiment 4 FIG.
FIG. 14 is a diagram illustrating a configuration example of a high-frequency oscillator according to the fourth embodiment.
In FIG. 14, the same reference numerals as those in FIG. 1 denote the same or corresponding parts, and the description thereof is omitted.
The high frequency oscillator includes a high frequency resonator 1, an active circuit 4, and an active circuit 5.

The active circuits 4 and 5, an active circuit having a reflection gain at _{f L.} The active circuit 4, the high-frequency resonator 1, and the active circuit 5 are connected in series. The sum (loop phase) of the reflection phase of the active circuit 4 and the reflection phase of the active circuit 5 and the passing phase of the high-frequency resonator 1 becomes an integral multiple (including 0) of 360 ° at the resonance frequency f _L. Of the active circuit 5 and the passage loss of the high-frequency resonator 1 (loop gain) is 0 dB or more. That is, the active circuit 4, the active circuit 5, and the high frequency resonator 1 form a positive feedback that satisfies the oscillation condition.

Next, the operation of the high frequency oscillator according to the fourth embodiment will be described.
High frequency noise near the resonance frequency f _L is input to the terminal 401 of the active circuit 4 to which the terminal 101 of the high frequency resonator 1 is connected, and the reflected power is amplified and input to the terminal 101 of the high frequency resonator 1. The electric power passes through the high-frequency resonator 1 and is input to the terminal 501 of the active circuit 5 connected to the terminal 102, is amplified and reflected by the active circuit 5, and is input to the terminal 102 of the high-frequency resonator 1 and again. The signal passes through the high-frequency resonator 1 and is input from the terminal 101 to the terminal 401 of the active circuit 4. Since this loop is configured to provide positive feedback, the original high-frequency noise is increasingly amplified and finally oscillates. At this time, since the high-frequency resonator 1 operates in an odd mode at the resonance frequency f _L , the active circuit 4 and the active circuit 5 operate in opposite phases, and the terminal 402 of the active circuit 4 and the active circuit 5 Oscillation waves having opposite phases can be obtained from the terminal 502.

As described in the first embodiment, the high-frequency resonator 1 is odd because the one end of the capacitor 105 is connected to the midpoint of the transmission line 103 and the one end of the capacitor 106 is connected to the midpoint of the transmission line 104. Symmetry is maintained for each of the mode and even mode. For the resonance frequency f _H of the high-frequency side of the operation loss due to the resistance 100 is suppressed occurring in the even mode, can not satisfy the loop gain of the oscillation condition, high frequency noise in the vicinity of f _H is not lead to oscillation, Unnecessary oscillation is suppressed.

As described above, according to the fourth embodiment, the high frequency resonator 1 having the low frequency side resonance is suppressed and the high frequency side resonance of the high frequency resonator is suppressed. Oscillation can be suppressed, and the effect of obtaining oscillation on the low frequency side is achieved. In addition, the transmission lines 103 and 104 having an electrical length of ¼ wavelength at the resonance frequency f ₀ at the time of non-coupling can be used to oscillate at f _L , thereby achieving an effect of miniaturization. In addition, since the high-frequency resonator 1 has a high Q value, it is possible to reduce the phase noise of the high-frequency oscillator. Furthermore, with this configuration, it is possible to obtain a reverse phase signal that is highly resistant to disturbance due to common noise.

Here, the configuration example in which the antiphase signal is extracted from the active circuit 4 and the active circuit 5 has been described. However, the signal may be extracted in the following configuration.
FIG. 15 is a diagram illustrating another configuration example of the high-frequency oscillator according to the fourth embodiment.
As shown in FIG. 15, the terminal 402 of the active circuit 4 and the terminal 601 of the synthesis circuit 6 are connected, the terminal 502 of the active circuit 5 and the terminal 602 of the synthesis circuit 6 are connected, and the synthesis circuit 6 The oscillation output of 4 and the oscillation output of the active circuit 5 are combined with the same electrical length. As a result, the signal of f _L that is opposite in phase is canceled, but the even-order harmonics of f _L are in-phase combined, so that the even-order harmonics of f _L are output from the terminal 603 of the combining circuit 6. Such an oscillator is called a Push-Push oscillator. As a result, even-order harmonics can be output while oscillating at f _L , so that an oscillation wave with a low frequency and low phase noise can be obtained.

Embodiment 5. FIG.
FIG. 16 is a diagram illustrating a configuration example of a high-frequency oscillator according to the fifth embodiment.
In FIG. 16, the same reference numerals as those in FIG. 1 denote the same or corresponding parts, and the description thereof will be omitted.
In FIG. 16, the high frequency oscillator includes an active circuit 4 having a reflection gain at the resonance frequency f _L and the high frequency resonator 1. The sum (loop phase) of the reflection phase of the active circuit 4 and the reflection phase of the high-frequency resonator 1 is an integral multiple (including 0) of 360 ° at the resonance frequency f _L , and the reflection gain of the active circuit 4 and the high-frequency resonator The sum of the reflection loss of 1 (loop gain) is 0 dB or more. That is, the active circuit 4 and the high frequency resonator 1 form a positive feedback that satisfies the oscillation condition.

Next, the operation of the oscillator according to the sixth embodiment will be described.
High frequency noise near the resonance frequency f _L is input to the terminal 401 of the active circuit 4 to which the terminal 101 of the high frequency resonator 1 is connected, and the reflected power is amplified and input to the terminal 101 of the high frequency resonator 1. The electric power is reflected by the high frequency resonator 1 and input again from the terminal 101 to the terminal 401 of the active circuit 4. Since this loop is configured to be positive feedback, the original high frequency noise is increasingly amplified and finally oscillates. The electric power generated by the oscillation is output from the terminal 402 of the active circuit 4 to the load.

As shown in the first embodiment, the high-frequency resonator 1 has an odd mode because one end of the capacitor 105 is connected to the midpoint of the transmission line 103 and one end of the capacitor 106 is connected to the midpoint of the transmission line 104. And symmetry with respect to the even mode. For the resonance frequency f _H of the high-frequency side of the operation loss due to the resistance 100 is suppressed occurring in the even mode, can not satisfy the loop gain of the oscillation condition, high frequency noise in the vicinity of f _H is not lead to oscillation, Unnecessary oscillation is suppressed.

As described above, according to the fifth embodiment, the high frequency side resonance of the high frequency resonator is suppressed and the high frequency resonator 1 having the low frequency side resonance is used. Oscillation can be suppressed, and the effect of obtaining oscillation on the low frequency side is achieved. In addition, the transmission lines 103 and 104 having an electrical length of ¼ wavelength at the resonance frequency f ₀ at the time of non-coupling can be used to oscillate at f _L , thereby achieving an effect of miniaturization. In addition, since the high-frequency resonator 1 has a high Q value, it is possible to reduce the phase noise of the high-frequency oscillator. Furthermore, since two active circuits are not required as in the fourth embodiment, a smaller high-frequency oscillator can be obtained.

Note that the high-frequency oscillator according to the fifth embodiment may be configured as follows.
FIG. 17 shows another configuration example of the high-frequency oscillator according to the fifth embodiment.
FIG. 17A shows a high-frequency oscillator in which a parallel resonant circuit 2 and an active circuit 4 are connected to the high-frequency resonator 1.
As shown in FIG. 17A, in this configuration, the terminal 102 of the high-frequency resonator 1 includes the parallel resonant circuit 2 having one end grounded, and the terminal 401 of the active circuit 4 is tap-coupled to the tap coupling position β of the terminal 108. doing. Here, α ≠ β. Since the parallel resonant circuit 2 resonates in parallel at f _L , it has high impedance, and since it can be considered that FIG. 17A and FIG. 16 are equivalent at f _L , this configuration suppresses unnecessary oscillation, The tap coupling position can be selected independently of the tap coupling position of the terminal 102. Thereby, in this structure, the freedom degree of design with respect to a terminal can be enlarged. Here, as described in FIG. 12, the parallel resonant circuit 2 may be a parallel resonant circuit including the transmission line 203 and the series resonant circuit 204.

FIG. 17B shows a high frequency oscillator in which the parallel resonant circuits 2 and 7 and the active circuit 4 are connected to the high frequency resonator 1.
As shown in FIG. 17 (b), the terminals 101 and 102 of the high-frequency resonator 1 may be provided with parallel resonant circuits 2 and 7 having one end grounded, and the active circuit 4 may be separately tapped to the transmission line 103. . The parallel resonant circuit 2 is connected to the terminal 102 of the high frequency resonator 1, and the parallel resonant circuit 7 is connected to the terminal 101 of the high frequency resonator 1. The terminal 401 of the active circuit 4 is connected to the terminal 108 of the high frequency resonator 1. In this case, the parallel resonant circuit 2 and 7, since the parallel resonance at f _L, is a high impedance. Accordingly, in _{f L,} which is equivalent to FIG. 17 (b) and FIG. 16. Therefore, even if the tap coupling position α of the terminals 101 and 102 and the tap coupling position β of the terminal 401 of the active circuit 4 are set independently, it can be seen that the operation is the same as in FIG. Compared to the case of FIG. 17A, the parallel resonant circuits 2 and 7 are arranged electrically symmetrically, and the electrical symmetry of the circuit can be maintained. Therefore, when the resonant frequency is changed, it can be changed to a wide band. it can. The resonance frequency of the high-frequency resonator can be changed by making the reactance of the parallel resonance circuits 2 and 7 variable. The parallel resonance circuits 2 and 7 may be the parallel resonance circuit including the transmission line 203 and the series resonance circuit 204 described with reference to FIG.

  DESCRIPTION OF SYMBOLS 1 High frequency resonator, 2 7 parallel resonance circuit, 3 4 5 active circuit, 6 synthetic circuit, 101 102 terminal, 103 104 203 transmission line, 105 106 202 702 capacitor, 107 resistance, 201 701 inductor 203 series resonance circuit

Claims (7)

A first transmission line with one end short-circuited;
A second transmission arranged parallel to the first transmission line, electromagnetically coupled to the first transmission line, and shorted at one end opposite to the short-circuited end of the first transmission line; Tracks,
A first reactance circuit having one end connected to a midpoint of the first transmission line;
A second reactance circuit having one end connected to the midpoint of the second transmission line and the other end connected to the other end of the first reactance circuit;
A high-frequency resonator comprising a resistor having one end connected to a connection point between the first reactance circuit and the second reactance circuit and the other end grounded. It has a terminal to input or output signals,
The high-frequency resonator according to claim 1, wherein the terminal is tapped to at least one of the first transmission line or the second transmission line. Two terminals are provided,
The high frequency resonance according to claim 2, wherein an electrical length from one of the terminals to the short-circuited end of the first transmission line is the same as an electrical length from the other of the terminals to the short-circuited end of the second transmission line. vessel.   3. The high-frequency resonator according to claim 1, further comprising: a parallel resonant circuit that is tap-coupled to at least one of the first transmission line or the second transmission line. A first transmission line with one end short-circuited;
A second transmission arranged parallel to the first transmission line, electromagnetically coupled to the first transmission line, and shorted at one end opposite to the short-circuited end of the first transmission line; Tracks,
A first reactance circuit having one end connected to a midpoint of the first transmission line;
A second reactance circuit having one end connected to the midpoint of the second transmission line and the other end connected to the other end of the first reactance circuit;
A resistor having one end connected to a connection point between the first reactance circuit and the second reactance circuit and the other end grounded;
A high frequency oscillator having a pass gain and comprising an active circuit tapped to the first transmission line and the second transmission line. A first transmission line with one end short-circuited;
A second transmission arranged parallel to the first transmission line, electromagnetically coupled to the first transmission line, and shorted at one end opposite to the short-circuited end of the first transmission line; Tracks,
A first reactance circuit having one end connected to a midpoint of the first transmission line;
A second reactance circuit having one end connected to the midpoint of the second transmission line and the other end connected to the other end of the first reactance circuit;
A resistor having one end connected to a connection point between the first reactance circuit and the second reactance circuit and the other end grounded;
A high-frequency oscillator having a reflection gain, and comprising an active circuit tapped to at least one of the first transmission line or the second transmission line. 7. The high-frequency oscillator according to claim 5, further comprising: a parallel resonant circuit that is tapped to at least one of the first transmission line or the second transmission line.

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