JP2016152665A - Vehicle driving system - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide a compact vehicle driving system for an AC electric vehicle traveling over different-frequency tracks of AC wiring.SOLUTION: A vehicle driving system for a vehicle traveling on a track having a first electric vehicle wire installed to supply first single-phase AC power and a track having a second electric vehicle wire installed to supply second single-phase AC power having a higher frequency includes a first power converter for converting the single-phase AC power supplied from the first electric vehicle wire or the second electric vehicle wire into DC power to output it to a DC power wire, a second power converter for converting the DC power output to the DC power wire into three-phase AC power, a vehicle driving electric motor to which the three-phase AC power is supplied, a resonance filter connected to the DC power wire in parallel with the first power converter and having a resonance point at a frequency band twice larger than that of the first single-phase ASC power, a voltage detector for detecting the voltage of the DC power wire, and pulsation suppression means for controlling the output of the second power converter according to the detection value of the voltage detector, and suppressing pulsation superimposed on the three-phase AC power.SELECTED DRAWING: Figure 1

Description

The present invention relates to a vehicle drive system, and more particularly to a control technique for suppressing a beat phenomenon that occurs in a main converter of an AC electric vehicle.

  A railcar drive system that receives power supplied from an AC overhead line converts a single-phase AC power into DC power, and converts DC power output by the converter into three-phase AC power of an arbitrary frequency. An inverter and a main motor driven by AC power output from the inverter are included. A DC circuit connecting the converter and the inverter is called a DC stage.

Since the voltage of the DC stage is generated by full-wave rectification of a single-phase AC voltage supplied from the overhead wire, there is a property that a frequency twice as high as the AC overhead wire frequency is superimposed. On the other hand, when a DC voltage is converted into an AC voltage by the inverter, components of the sum and difference of the frequency of the inverter fundamental wave and the vibration frequency of the DC voltage appear in the output voltage of the inverter. In particular, for the frequency difference component, the closer the frequency of the inverter fundamental wave and the vibration frequency of the DC voltage are, the lower the frequency component of the difference becomes, and the impedance of the main motor also decreases accordingly. Is known to pulsate at the difference frequency. Generally, this pulsation is called a beat phenomenon.

As a method for suppressing the beat phenomenon described above, a method of installing a resonance filter having a resonance point with a frequency twice that of the AC overhead line, or a switching control of the inverter is used to adjust the frequency of the output voltage of the inverter. There is a method such as beatless control for suppressing the frequency component of the beat phenomenon of the output voltage. A method of installing a resonance filter is disclosed in Patent Document 1 (EP12888060A), and a configuration of beatless control is disclosed in Patent Document 2 (Japanese Patent Laid-Open No. 11-164565).

EP1288060A Japanese Patent Laid-Open No. 11-164565

  However, the technique for suppressing the beat phenomenon described in each of Patent Documents 1 and 2 described above has the following problems.

  First, in the case of using the resonance filter described in Patent Document 1, an AC electric vehicle that runs on a route composed of a plurality of sections with different frequencies of AC overhead wires and uses AC power of a plurality of frequencies as a power source is adjusted to each frequency. There is a problem that it is necessary to mount a resonance filter, and the on-board equipment (resonance filter) increases in size.

On the other hand, when using the beatless control described in Patent Document 2, when power is supplied from a low-frequency AC power supply, the capacitance of the smoothing capacitor connected in parallel with the converter and inverter of the DC stage is sufficient. If it is not increased, pulsation of the output voltage of the inverter cannot be suppressed. Therefore, when receiving power supply from an AC power source with a low frequency, it is necessary to increase the capacitance of the smoothing capacitor of the DC stage in order to stabilize the output AC voltage. There is a problem of increasing the size.

  In order to solve the above problems, the configuration described in the claims is adopted.

A line on which a first train line for supplying first single-phase AC power is installed, and a second train line for supplying second single-phase AC power having a frequency higher than that of the first single-phase AC power In a vehicle drive system for a vehicle that travels on a route where is installed,
A first power converter that converts single-phase AC power supplied from the first train line or the second train line into DC power and outputs the DC power line;
A second power conversion device that converts the DC power output to the DC power line into three-phase AC power;
An electric motor for driving the vehicle to which the three-phase AC power is supplied;
A resonance filter connected to a DC power line in parallel with the first power converter, and having a resonance point in a frequency band twice that of the first single-phase AC;
A voltage detector for detecting the voltage of the DC power line;
This can be realized by controlling the output of the second power conversion device according to the detection value of the voltage detector and by providing pulsation suppression means for suppressing pulsation superimposed on the three-phase AC power.

ADVANTAGE OF THE INVENTION According to this invention, it becomes possible to reduce in-vehicle apparatus of the alternating current electric vehicle which operate | moves the several area where frequencies differ.

The figure which shows the structure of the drive system in a 1st Example. The figure which shows the structure of a 2nd Example. The figure which shows the structure of a 3rd Example. The figure which shows the relationship between the power supply frequency in 1st Example, and a smoothing capacitor electrostatic capacitance.

Embodiments of the present invention will be described below with reference to the drawings.

  A first embodiment of the present invention will be described with reference to FIG. FIG. 1 shows a configuration of a vehicle drive system in the present embodiment.

  1 is a current collector, 2 is a transformer, 5 is a converter, 5a, 5b, 5c, and 5d constituting the converter 5 are switching elements of the converter 5, 6 is a resonance filter circuit, and 6a that constitutes the resonance filter circuit 6 is resonance. Reactor, 6b is a resonance capacitor, 8 is a smoothing capacitor, 9 is an inverter, 9a, 9b, 9c, 9d, 9e, 9f constituting the inverter 9 are switching elements of the inverter 9, 11 is an electric motor, and 21 is a wheel.

  3 is a voltage detector for measuring the secondary side voltage of the transformer 2, 4 is a current detector for measuring the secondary side current of the transformer 2, and 7 is a voltage detector for measuring the voltage across the smoothing capacitor 8. Reference numeral 10 denotes a current detector for measuring the current of the main motor 11.

  Further, 22 is a first AC power source, 23 is a second AC power source having a frequency different from that of the first AC power source 22, 24 is a first train line for supplying the power of the first AC power source 22 to the vehicle, Reference numeral 25 denotes a second train line for supplying electric power from the second AC power source 23 to the vehicle, 26 denotes a non-electric section that insulates the first train line 24 and the second train line 25, and 27 denotes a track of the vehicle. .

  In this embodiment, as an example, the converter 5 is a two-level single-phase full-bridge power conversion device, and the inverter 9 is a two-level three-phase full-bridge power conversion device. However, the converter and the inverter are in other forms of power conversion. It is also possible to configure with a device, for example a three level circuit.

This drive system is a device for accelerating and decelerating the vehicle. The vehicle uses AC power supplied from the first AC power supply 22 via the train line 24 and the track 27 or from the second AC power supply 23. The supplied AC power is input from the current collector 1 and the wheel 21 via the train line 25 and the track 27. During acceleration, the input AC power is stepped down by the main transformer 2 and converted to DC power by the converter 5. The electric power converted into direct current is smoothed by the smoothing capacitor 8 and then reversely converted into alternating current power by the inverter 9 and supplied to the main motor 11 to accelerate the vehicle by variable speed driving.
During deceleration, AC power generated by the regenerative brake of the main motor 11 is converted into DC power by the inverter 9. The electric power converted into direct current is smoothed by the smoothing capacitor 8, then reversely converted into alternating current power by the converter 5, boosted by the main transformer 2, and then returned from the current collector to the train line 24 or 25. It is.

It is possible to identify whether the electric power is supplied from the train line 24 or the train line 25 having a different frequency by detecting the frequency of the voltage by the voltage detector 3. This is possible by using position detection technology. As this position detection means, a detection means using a track circuit (not shown), a detection means using travel distance information obtained by integrating vehicle speed information, or a detection means using GPS can be applied. The beat suppression function by a resonance filter and a beatless control unit, which will be described later, can be switched according to the power source identified by such a voltage detector or position detection technique. If the power frequency of the train line 24 is lower than the power frequency of the train line 25 and if it is determined that power is being supplied from the train line 25, the beatless control unit is operated to suppress pulsation by beatless control. I do. In addition, when it is determined that electric power is supplied from the train line 24, pulsation is suppressed by the resonance filter. When performing pulsation suppression using a resonance filter, beatless control is not necessary, and therefore the beatless control may be stopped or may be operated without stopping.

Next, reference numeral 100 in the figure denotes a converter control device that performs power conversion control of the converter 5. 101 is a power supply phase detector, 102 is a sine wave generator, 103 and 106 and 108 are subtractors, 104 is a voltage controller, 105 is a multiplier, 107 is a current controller, and 109 is a PWM controller.

  Converter control device 100 detects the secondary voltage of main transformer 2 with voltage detector 3 and detects the electrical angle with power supply phase detector 101. The sine wave generator 102 generates a sine wave having the same phase as the power supply voltage and an amplitude of 1 based on the electrical angle information.

  In parallel with this, the DC voltage Ed of the smoothing capacitor 8 is detected by the voltage detector 7, and the subtractor 103 subtracts the DC voltage Ed from the DC voltage command Ed *. The voltage controller 104 generates a secondary current effective value command Is * for making the DC voltage Ed coincide with the command value Ed * based on the subtraction result. The command Is * and the sine wave generated by the sine wave generator 102 are multiplied by a multiplier 105 to generate a secondary current command is * for the main transformer 2. The secondary current command is * has the same phase as the secondary voltage of the main transformer 2, and thereby controls the input of the converter 5 to have a power factor of 1.

  Thereafter, the subtractor 106 subtracts the secondary current command is * and the secondary current is detected by the current detector 4. The current controller 107 generates an AC voltage command ec based on the subtraction result. Thereafter, the subtractor 107 subtracts the AC voltage command ec from the secondary voltage es, and the PWM controller 109 generates a converter pulse command Sc based on the subtraction result.

The converter pulse command Sc is input to the converter 5, and the DC voltage Ed is controlled to be constant by switching 5a to 5d based on the converter pulse command Sc.

  Furthermore, 200 in the figure is an inverter control device that performs power conversion control of the inverter 9, 201 is a coordinate converter, 202 and 203 are subtractors, 204 is a current controller, 205 is a beatless controller, 206 is an adder, Reference numeral 207 denotes a PWM controller.

The inverter control device 200 inputs the three-phase alternating currents iu, iv, iw detected by the current detector 10 to the coordinate converter 201 and generates a d-axis current Id and a q-axis current Iq. The subtracter 202 subtracts the d-axis current Id from the d-axis current command Id *, and the subtractor 203 subtracts the q-axis current Iq from the q-axis current command Iq *. The current controller 204 calculates a modulation rate Vc, an output frequency Fi, and an output deflection angle δ necessary for variable speed operation of the main motor 11 based on the subtraction results calculated by the subtractor 202 and the subtracter 203, respectively. The beatless controller 205 outputs an output frequency correction value ΔFi based on the DC voltage Ed of the smoothing capacitor 8 detected by the voltage detector 7, and an adder 206 adds the output frequency Fi and the correction value ΔFi and outputs the result. A frequency command Fi * is generated. Thereafter, the PWM controller 207 generates an inverter pulse command Si based on the modulation factor Vc, the output frequency command Fi *, and the output deflection angle δ, and inputs the inverter pulse command Si to drive the main motor 11.

  Here, when a plurality of resonance filters matched to the frequency of the AC power of a plurality of frequencies are mounted, there is a problem that the on-board equipment (resonance filter) becomes large, and when using beatless control, the frequency of In preparation for a low AC power source, it is necessary to increase the capacitance of the smoothing capacitor of the DC stage, and there is a problem that the on-board equipment (smoothing capacitor) increases in size. Further, as another problem when the capacitance of the smoothing capacitor is increased, there is a problem that the discharge current that flows at the time of a short-circuit failure of the converter or the inverter increases and the risk of a secondary failure increases.

  Therefore, although details will be described later, in the present embodiment, the current of the main motor 11 is caused by the pulsation of the frequency twice the AC power supply voltage superimposed on the DC voltage in a railway vehicle that is on a route having two or more types of power supply frequencies. In order to suppress the beat phenomenon appearing in the resonance frequency, both the resonance filter 6 and the beatless controller 205 are provided, and for the overhead line voltage having the lowest frequency, the resonance point has a resonance frequency twice that of the AC power supply voltage. The filter 6 is used to suppress pulsation at a frequency twice that of the AC power supply voltage superimposed on the DC voltage, and for the overhead line voltage at other frequencies, the current of the main motor is controlled by beatless control that is inverter switching control. It is characterized by suppressing the pulsation that occurs.

As an example, considering the case where the present invention is applied to a railway vehicle traveling on a route having two types of 16.7 Hz and 50 Hz as an AC power source, it is hardware for an AC power source with a low frequency of 16.7 Hz. The resonance filter suppresses pulsation at twice the frequency of the AC power supply voltage superimposed on the DC voltage, and suppresses pulsation that occurs in the main motor current by beatless control, which is software, for high-frequency 50 Hz overhead wire voltage To do.

  First, the pulsation of the DC voltage Ed when the resonance filter 6 is not provided in the DC stage will be described below.

The pulsation of the DC voltage Ed of the AC vehicle is caused by the rectification of the converter 5 and that caused by the voltage conversion of the inverter 9.

Since the pulsation caused by the rectification of the converter 5 is caused by the rectification of the single-phase alternating current, the main frequency band of the pulsation has a frequency twice the overhead wire voltage. The relationship between the pulsation of the DC voltage Ed at this time and the electrostatic capacity of the smoothing capacitor 8 necessary for beatless control is shown in Equation (1).

  Here, ΔEcf is the pulsation width of the DC voltage, P is the maximum power of the vehicle drive system, ωc is the angular frequency of the overhead wire voltage, Cf is the capacitance of the smoothing capacitor 8, and Ecf is the DC component of the DC voltage.

As can be seen from the equation (1), the pulsation width ΔEcf of the DC voltage is inversely proportional to the AC frequency ωc of the overhead line voltage.

On the other hand, the pulsation resulting from the voltage conversion of the inverter is generated by converting direct current into three-phase alternating current, so the main frequency band of the pulsation is a frequency six times the output frequency of the inverter. The relationship between the pulsation of the DC voltage at this time and the electrostatic capacity of the smoothing capacitor 8 necessary for beatless control is shown in equation (2).

Here, ωi is an angular frequency at the point where the output power of the inverter becomes maximum. In a system that does not have the resonance filter 6 in the DC stage, it is necessary to suppress the pulsation of the AC output voltage of the inverter by beatless control of the inverter. Therefore, the electrostatic capacitance of the smoothing capacitor shown in the equations (1) and (2) It is necessary to have a capacitance Cf. Therefore, when the AC overhead line is of two types, for example, when the frequency of the AC overhead line is 16.7 Hz and 50 Hz, the pulsation of the AC output voltage of the inverter is suppressed using beatless control for the following three DC voltage pulsations. There is a need to.
(A) DC voltage pulsation due to rectification of converter 5 when overhead line frequency is 16.7 Hz (b) DC voltage pulsation due to rectification of converter 5 when overhead line frequency is 50 Hz (c) DC voltage pulsation in inverter operation DC voltage pulsation under maximum conditions

Here, the condition that the DC voltage pulsation in the inverter operation is maximized is a case where the output voltage of the inverter 9 is maximized. In order to increase the voltage utilization efficiency, the inverter device of a railway vehicle saturates the output voltage at an inverter frequency Fi corresponding to about half of the rated speed, and controls only the inverter frequency Fi at a higher speed. The speed at which this output voltage saturates is called the V / f termination speed. At a speed higher than this termination speed, the output power of the inverter is maximized and the pulsation width ΔEcf of the DC voltage is also maximized.

  The electrostatic capacity Cf of the smoothing capacitor 8 required for beatless control at this time will be described below.

The electrostatic capacity Cf of the smoothing capacitor 8 required for beatless control when the pulsation rate superimposed on the DC voltage Ed is k and the pulsation width generated by the converter operation is to be equal to or less than ΔEcf is expressed by the following equation (3).

Further, the electrostatic capacitance Cf of the smoothing capacitor 8 necessary for beatless control when it is desired to make the pulsation width generated by the inverter operation equal to or less than ΔEcf is the number (4).

For example, in the vehicle drive system in which the resonance filter 6 is not connected to the DC stage, when the conditions of P = 1630 kW, Ecf = 2400 V, k <0.04 are studied, the above three DC voltage pulsations (a) to In contrast to (c), the capacitance Cf of the smoothing capacitor necessary for suppressing the pulsation of the AC output voltage of the inverter using beatless control is as follows.

(A) When the overhead line frequency is 16.7 Hz, the overhead line frequency ωc = 2 × π × 16.7 rad / s in the equation (3) is obtained, which is caused by the rectification of the converter 5 when the overhead line frequency is 16.7 Hz. For the DC voltage pulsation, the capacitance of the smoothing capacitor 8 required to suppress the pulsation of the AC output voltage of the inverter using beatless control is Cf> 28800 μF.

(B) When the overhead line frequency is 50 Hz, the overhead line frequency ωc = 2 × π × 50 rad / s in the equation (3), so that the DC voltage pulsation caused by the rectification of the converter 5 when the overhead line frequency is 50 Hz The capacitance of the smoothing capacitor 8 necessary for suppressing the pulsation of the AC output voltage of the inverter using the beatless control is Cf> 9600 μF.

(C) When the DC voltage pulsation in the inverter operation becomes the maximum, the DC voltage pulsation ΔEcf due to the inverter operation becomes the largest at the point where the output power at the V / f terminal becomes the maximum, and the inverter operating frequency Fi in the equation (4) Is 50 Hz and each frequency ωi = 2 × π × 50 rad / s. Therefore, a smoothing capacitor required for suppressing pulsation of the AC output voltage of the inverter using beatless control against DC voltage pulsation due to the inverter operation. The capacitance of Cf> 3200 μF.

As described above, it is necessary to suppress the pulsation of the AC output voltage of the inverter using beatless control against the dc voltage pulsation that occurs when the low-frequency 16.7 Hz AC voltage is converted into a DC voltage by the converter. The smoothing capacitor 8 has the largest electrostatic capacitance Cf, and the DC output voltage pulsation generated when the AC voltage having a frequency of 50 Hz is converted into a DC voltage by the converter is used to control the AC output voltage of the inverter using beatless control. For the DC voltage pulsation under the condition that the electrostatic capacitance Cf of the smoothing capacitor 8 necessary for suppressing the pulsation is large and the DC voltage pulsation generated by the inverter operation is the maximum, the AC output voltage of the inverter using beatless control The electrostatic capacitance Cf of the smoothing capacitor 8 required for suppressing the pulsation of is the smallest.

  FIG. 4 shows the relationship between the power supply frequency and the capacitance of the smoothing capacitor 8 that is necessary for suppressing the pulsation of the AC output voltage of the inverter using beatless control against the DC voltage pulsation. The horizontal axis is the power supply frequency, and the vertical axis is the capacitance of the smoothing capacitor 8. The figure is based on number (3). This is a trial calculation of the capacitance of the smoothing capacitor required to suppress the pulsation of the AC output voltage of the inverter using beatless control against the pulsation component superimposed on the DC voltage. As the calculation conditions, the values of (a) and (b) described above were used.

From this result, it can be seen that the capacitance of the smoothing capacitor 8 necessary for suppressing the pulsation generated by the converter operation using the beatless control is in an inversely proportional relationship with the frequency of the power source. Therefore, the pulsation of the DC voltage is suppressed by matching the resonance characteristics of the resonance filter 6 with respect to the frequency (low frequency) that is twice the frequency of 16.7 Hz where the frequency of the AC overhead line is low. On the other hand, for the frequency (high frequency) that is twice the frequency of 50 Hz where the frequency of the AC overhead line is high, the pulsation ΔEcf of the DC voltage is not transmitted to the main motor 11 on the inverter output side by applying beatless control. . In this way, the resonance filter 6 and the beatless control function are provided, and the resonance characteristic of the resonance filter 6 is made to coincide with the DC voltage pulsation having the lowest frequency. The electric capacity can be suppressed to about 1/3 or less.

Here, since the electrostatic capacity required for beatless control can be shared from the electrostatic capacity of the smoothing capacitor 8 and the resonant capacitor 6b of the resonant filter 6, the required electrostatic capacity of the resonant capacitor 6b is several (5). .

Here, Clc is the capacitance of the resonance capacitor 6b.

Furthermore, the relationship between the inductance of the resonance reactor 6a and the capacitance of the resonance capacitor 6b can be determined by setting the resonance point of the resonance filter 6 to be twice the overhead line frequency of 16.7 Hz. Good.

  Here, Llc is the inductance of the resonant reactor 6a.

Therefore, the inductance of the resonant reactor 6a in the present embodiment is determined by the expression (7) by expanding the expression (6).

With the above-described configuration, if the electrostatic capacitance Cf of the smoothing capacitor 8 is determined, the electrostatic capacitance Clc of the resonant capacitor 6b and the inductance Llc of the resonant reactor 6a can be determined, and the vehicle is driven using a plurality of frequencies as a power source. System volume and weight can be reduced and optimized.
It should be noted that static voltage of the smoothing capacitor 8 required for suppressing the pulsation of the AC output voltage of the inverter using beatless control against the dc voltage pulsation caused by the rectification of the converter 5 when the overhead line frequency is 16.7 Hz. The capacitance Cf> 28800 μF is an inverter that uses beatless control for the capacitance of the resonance capacitor 6b necessary for suppressing the pulsation component twice the overhead line frequency of 16.7 Hz and the pulsation component twice the 50 Hz. The capacitance Cf of the smoothing capacitor 8 necessary to suppress the pulsation of the AC output voltage is very large as compared with 9600 μF. Therefore, the capacitance of the resonance capacitor 6b necessary for suppressing the pulsation component twice the overhead line frequency of 16.7 Hz and the AC output voltage of the inverter using beatless control for the pulsation component twice the frequency of 50 Hz. The capacitance of the capacitor necessary for the entire system can be reduced by providing the smoothing capacitor 8 with the capacitance Cf> 9600 μF necessary for suppressing pulsation.

In addition, when a short circuit failure occurs in the converter 5 or the inverter 9, the charge stored in the smoothing capacitor 8 is discharged to the failure location, and an accident current flows to the failure location. Since the capacitance of the capacitor can be reduced, current can be suppressed and secondary breakdown of the device can be prevented.

  A second embodiment of the present invention will be described with reference to FIG. FIG. 2 shows the configuration of this embodiment.

  The same parts in FIG. 1 as those in FIG. 1 are represented by the same reference numerals, and the description thereof is omitted.

  In the figure, reference numeral 12 denotes a resonance filter. The resonance filter 12 includes a resonance reactor 12a, a resonance capacitor 12b connected in series with the resonance reactor 12a, and a contactor 12c connected in parallel with the resonance reactor 12a.

  The resonance filter circuit 12 has a feature that the reactor of the resonance filter can be short-circuited with respect to the resonance filter circuit 6 of the first embodiment by inserting the contactor 12c in accordance with an insertion / release command input from the outside.

  The vehicle drive system according to the present embodiment is a beat that appears in the current of the main motor 11 due to pulsation having a frequency twice the power frequency superimposed on the DC voltage in a railway vehicle that enters a route having two or more types of power frequencies. In order to suppress the phenomenon, the resonance filter circuit 12 and the beatless controller 205 are both provided in the same manner as in the first embodiment, but as a component of the resonance filter 12, a resonance reactor 12a and a resonance capacitor 12b are provided. In addition, a contactor 12c is included.

  In this embodiment, the DC stage voltage pulsation suppression method is switched according to the power supply frequency of the AC power supply. Similarly to the first embodiment, the resonance frequency of the resonance filter 12 is set to twice the lowest frequency among the plurality of AC power supplies, and the resonance filter 12 (series connection body of the resonance reactor 12a and the resonance capacitor 12b). The pulsation is suppressed by setting the resonance frequency, and the frequency of the other AC power source is suppressed by the beatless controller 205.

  The beatless controller 205 switches between pulsation suppression by the resonance filter 12 and suppression by beatless control according to the pulsation frequency superimposed on the voltage of the smoothing capacitor 8 measured by the voltage detector 7.

  When the voltage detector 7 detects the same pulsation as the resonance frequency of the resonance filter 12 with the contactor 12c turned on, a contactor release command is output from the beatless controller 205, and the contactor of the resonance filter 12 is output. 12c is opened, and the resonance filter 12 suppresses the pulsation of the DC stage. In this case, since the beatless control is not necessary, the beatless control may be stopped, but the beatless control may be kept operating.

  On the other hand, when a pulsation other than the resonance frequency of the resonance filter 12 is detected by the voltage detector 7 with the contactor 12c opened, a contactor input command is output from the beatless controller 205, and the resonance filter 12 The contactor 12c is turned on to suppress pulsation of the DC stage by beatless control. At this time, when the contactor 12c is inserted, the portion of the resonant reactor 12a is short-circuited, so that the resonant capacitor 12b can be used as a smoothing capacitor for the DC stage.

  The present embodiment differs from the first embodiment in the capacitance Cf of the smoothing capacitor 8 that is necessary for suppressing the pulsation superimposed on the DC voltage. That is, by applying the present embodiment, the resonant capacitor 12b can be used as a part of the smoothing capacitor, so that the capacitance Cf of the smoothing capacitor 8 required to suppress the DC voltage pulsation ΔEcf can be reduced. The apparatus can be reduced in size. Moreover, the loss which generate | occur | produces in the resonance reactor 6a in beatless control can be reduced.

In this embodiment, the form in which the beatless controller 205 controls the opening / closing of the contactor 12c and the operation stop of the beatless control based on the voltage of the smoothing capacitor is shown. However, as in the first embodiment, the voltage detector 3 Based on the detected voltage or the power supply frequency identified by the position detection means, the opening / closing of the contactor 12c and the operation stop of the beatless control may be controlled.
In this case, when it is determined that power is supplied from an AC power source having a frequency that matches the resonance frequency of the resonance filter 12, a contactor opening command is output, and the contactor 12c of the resonance filter 12 is opened. The pulsation of the DC stage is suppressed by the resonance filter 12. When it is determined that power is supplied from an AC power supply having a frequency different from the resonance frequency of the resonance filter 12, a contactor input command is output, the contactor 12c of the resonance filter 12 is input, Beatless control suppresses DC stage pulsation.

In this embodiment, it is determined whether or not the voltage of the smoothing capacitor 8 is the same as the resonance frequency of the resonance filter 12 in the converter control device 100, and the contactor 12c is controlled to open and close based on the determination result. A command may be output, and a control command for starting and stopping beatless control may be output to the beatless controller 205 in the inverter control device 200.

  A third embodiment of the present invention will be described with reference to FIG. FIG. 3 shows the configuration of this embodiment.

  The same parts in FIG. 1 as those in FIG. 1 are represented by the same reference numerals, and have the same functions as those in the first embodiment, and thus the description thereof is omitted.

  The resonance filter 13 shown in the figure includes a resonance reactor 13a, a resonance capacitor 13b connected in series with the resonance reactor 13a, and a contactor 13c further connected in series with the resonance reactor 13a. The converter control device 100 includes a failure detector 110. The inverter device 200 includes an output regulator 208.

  The resonance filter circuit 13 has a feature that the contact filter 13c can be freely turned on and off in accordance with a closing / opening command input from the outside with respect to the resonance filter circuit 6 of the first embodiment. When the resonance filter 13 is operating normally, the contactor 13c of the resonance filter circuit 13 is in the on state.

  In the vehicle drive system in the present embodiment, when the resonance reactor 13a or the resonance capacitor 13b of the resonance filter circuit 13 fails, the failure detector 110 detects the failure state. The detection method is determined by detecting the resonance frequency of the resonance filter circuit from the DC voltage Ed detected by the voltage detector 7.

  When a pulsation other than the resonance frequency of the resonance filter 13 is detected from the voltage detector 7 or when it is determined by the power frequency identification function described in the first embodiment that power is supplied from the lowest frequency power source. The beatless control is executed, and the beatless controller outputs a beatless control command ΔSi for suppressing the beat phenomenon of the main motor 11 due to the DC voltage oscillation to the PWM controller 207.

  On the other hand, when it is determined by the power frequency identification function described in the first embodiment that power is supplied from the power source having the lowest frequency, the beatless control is stopped and superimposed on the DC voltage by the resonance filter 13. Suppresses pulsation. Here, when the resonance frequency of the resonance filter circuit is detected by the voltage detector 7 when the beatless control is stopped and the pulsation of the DC stage is suppressed by the resonance filter 13, the resonance filter circuit 13 has a failure. The failure detector 110 outputs a contactor opening command to the contactor 13c of the resonance filter circuit 13 from the failure detector 110. As a result, the resonance filter circuit 13 that has failed is separated from the circuit, so that the influence of the failure is not exerted on other circuits. At the same time, failure detection information is output to the beatless controller 205 and the output adjuster 208.

  The beatless controller 205 is stopped when the resonance filter 13 is operating normally, operates when receiving failure detection information, and suppresses the beat phenomenon of the main motor 11 due to DC voltage vibration. A beatless control command ΔSi is output to the PWM controller 207.

  In the vehicle drive system in which the resonance filter 13 is installed, if the resonance filter 13 fails and is disconnected from the circuit by the contactor 13c, the capacitance of the smoothing capacitor 8 is insufficient. It becomes difficult to suppress vibrations at. On the other hand, since the vibration of the DC voltage Ed is proportional to the current flowing through the smoothing capacitor 8, if the driving speed of the vehicle is lowered and the load of the main motor 11 is lowered, the current of the smoothing capacitor 8 is also reduced proportionally. Therefore, the vibration of the DC voltage can be reduced, and the beat phenomenon of the main motor 11 can be suppressed by the control. Therefore, when a failure is detected, the failure detection information is input to the output regulator 208 and the current command is narrowed down to reduce the current flowing through the main motor 11 and the beat phenomenon can be suppressed by beatless control. The vehicle can be continuously operated at the time of failure.

  According to the present embodiment, as in the other embodiments, the capacitance Cf of the smoothing capacitor 8 necessary for suppressing the pulsation ΔEcf of the DC voltage can be reduced, and the apparatus can be miniaturized. In addition, by separating the failed resonance filter circuit 13 from the circuit, it is possible to prevent other circuits from being affected by the failure. Further, by executing the beatless control when the failure of the resonance filter circuit 13 is detected, the vehicle can be continuously operated even when the resonance filter failure occurs.

In the present embodiment, the embodiment in which the failure detector 110 is provided in the converter control device 100 has been described. However, the failure detector 110 may be provided in the inverter control device 200.

1 current collector 2 main transformer 3 voltage detector 4 current detector 5 converter (first power conversion means)
5a, 5b, 5c, 5d Switching element 6 Resonant filter 6a Resonant reactor 6b Resonant capacitor 7 Voltage detector 8 Smoothing capacitor 9 Inverter (second power conversion means)
9a, 9b, 9c, 9d, 9e, 9f Switching element 10 Current detector 11 Main motor 12 Resonant filter 12a Resonant reactor 12b Resonant capacitor 12c Contactor 13 Resonant filter 13a Resonant reactor 13b Resonant capacitor 13c Contactor 21 Wheels 22, 23 AC Power supply 24, 25 Train line 26 Electrification section 27 Track 100 Converter control device 101 Power supply phase detector 102 Sine wave generator 103 Subtractor 104 Voltage controller 105 Multiplier 106 Subtractor 107 Current controller 108 Subtractor 109 PWM controller 110 Failure detector 200 Inverter controller 201 Coordinate converter 202 Subtractor 203 Subtractor 204 Current controller 205 Beatless controller 206 Adder 207 PWM controller 208 Output adjuster

es Secondary voltage ec AC voltage command Ed DC voltage Ed * DC voltage command Fi Output frequency id d-axis current iq q-axis current is secondary current iu u-phase current iv v-phase current iw w-phase current id * d-axis current command iq * Q-axis current command is * secondary current command Is * secondary current effective value command Sc converter pulse command Si inverter pulse command ΔSi beatless control command δ output deflection angle ω power supply angular frequency t time P maximum power Ecf of the power converter DC DC component of voltage ΔEcf DC component pulsation component Cf Smoothing capacitor capacitance ωc Overhead angular frequency ωi Output angular frequency k Pulsation factor Llc Resonance reactor inductance Clc Resonance capacitor capacitance

Claims (6)

A line on which a first train line for supplying first single-phase AC power is installed, and a second train line for supplying second single-phase AC power having a frequency higher than that of the first single-phase AC power In a vehicle drive system for a vehicle that travels on a route where is installed,
A first power converter that converts single-phase AC power supplied from the first train line or the second train line into DC power and outputs the DC power line;
A second power conversion device that converts the DC power output to the DC power line into three-phase AC power;
An electric motor for driving the vehicle to which the three-phase AC power is supplied;
A resonance filter connected to a DC power line in parallel with the first power converter, and having a resonance point in a frequency band twice that of the first single-phase AC;
A voltage detector for detecting the voltage of the DC power line;
A vehicle drive system comprising pulsation suppression means for controlling an output of the second power converter according to a detection value of the voltage detector and suppressing pulsation superimposed on the three-phase AC power.
The vehicle drive system according to claim 1,
The resonant filter absorbs a pulsation of a frequency component that is twice the first single-phase AC power superimposed on the DC power,
The pulsation suppressing means controls the output of the second power converter so as to suppress pulsation of a frequency component twice the second single-phase AC power superimposed on the three-phase AC power. Vehicle drive system.
The vehicle drive system according to claim 2,
Power supply determination means for determining whether power is supplied from either the first train line or the second train line;
If it is determined that power is supplied from the first train line, the pulsation suppression means is stopped,
A vehicle drive system characterized by operating pulsation suppression means when it is determined that power is supplied from the second train line.
The vehicle drive system according to any one of claims 1 to 3,
A smoothing capacitor connected to the DC power line in parallel with the first power converter and stabilizing the DC power;
The resonance filter includes a resonance reactor and a resonance capacitor connected in series with each other.
The vehicle drive system according to claim 4,
The resonant filter further includes a contactor connected in parallel to the resonant reactor,
When detecting the same pulsation as the resonance frequency of the resonance filter by the voltage detector, the contactor is opened,
The vehicle drive system, wherein the contactor is turned on when a pulsation other than the resonance frequency of the resonance filter is detected by the voltage detector.
The vehicle drive system according to claim 4,
The resonant filter further comprises a contactor connected in series with the resonant reactor,
When detecting the pulsation of the resonance frequency of the resonance filter by the voltage detector, the beater control is performed while opening the contactor,
When the voltage detector does not detect the pulsation of the resonance frequency of the resonance filter, the vehicle drive system is characterized in that the contactor is turned on and beatless control is stopped.

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