JP2015130793A - permanent magnet type motor - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide a permanent magnet type motor that achieves both cogging torque reduction and torque rippled reduction and also achieves both size and weight reduction and the torque ripple reduction.SOLUTION: An arrangement is employed such that a U1 phase is accommodated in both mutually adjacent slots among a plurality of slots 27 or at least one of the U1 phase and U2 phase is accommodated in one of the mutually adjacent slots. The U1 phase, a V1 phase, a W1 phase and the U2 phase, a V2 phase, and a W2 phase are driven with mutual deviations of 20-40° in electric angle. Further, Ws/(2πRs/Ns)≤0.15 holds for a slot opening width Ws of a stator iron core 22, an inner radius Rs of the stator iron core, and the number Ns of slots of the stator iron core, 0.50≤Wt/(2πRs/Ns)≤0.65 holds for a teeth width Wt of the stator iron core, and cogging torque whose degree is coincident with Ns and sextic torque ripple are both reduced.

Description

  The present invention relates to a permanent magnet type motor, and more particularly to a motor used in an electric power steering device for a vehicle.

Conventionally, as shown in Patent Document 1, for example, a structure of a permanent magnet type motor having a first three-phase stator winding and a second three-phase stator winding has been devised.
Further, Patent Document 2 has a first three-phase winding and a second three-phase winding, and the first three-phase winding and the second three-phase winding are π / 6 each other. A rotating electric machine having a phase difference of 1 is disclosed.

Japanese Patent Laid-Open No. 7-264822 JP 2010-268597 Gazette

However, in the structures of Patent Document 1 and Patent Document 2, since the slot opening width is large, it is very easily affected by the work error on the rotor side and the variation of the shape and magnetic characteristics of the permanent magnet, and the cogging torque increases. There was a problem of ending up.
Therefore, there has been a problem that such a motor is not suitable for an application in which the demand for reducing the cogging torque is very strong, for example, an electric power steering device for a vehicle.

  The present invention has been made to solve the above problems, and provides a permanent magnet type motor that achieves both a reduction in cogging torque and a reduction in torque ripple, as well as a reduction in size and weight and a reduction in torque ripple. The purpose is to do.

The present invention
A rotor comprising a rotor core and a plurality of permanent magnets provided on the rotor core;
A stator core having a plurality of teeth and two sets of three-phase armature windings housed in a plurality of slots formed in the stator core;
In a permanent magnet motor configured such that one armature winding is supplied with current from a first inverter and the other one armature winding is supplied with current from a second inverter,
For the two sets of three-phase armature windings,
When the first armature winding is U1, V1, and W1, the second armature winding is U2, V2, and W2.
Of the plurality of slots, either one of the slots adjacent to each other is arranged such that the U1 phase of the first armature winding is placed in one of the slots adjacent to each other. At least one of the U1 phase of the first armature winding or the U2 phase of the second armature winding is placed;
The U1 phase, V1 phase, W1 phase and U2 phase, V2 phase, W2 phase of the armature winding are driven with an electrical angle of 20 ° to 40 ° shifted from each other,
Furthermore, the slot opening width Ws of the stator core is:
Ws / (2πRs / Ns) ≦ 0.15
Where Rs is the inner radius of the stator core, Ns is the number of slots of the stator core,
The teeth width Wt of the stator core is
0.50 ≦ Wt / (2πRs / Ns) ≦ 0.65,
Both the cogging torque whose order matches Ns and the sixth-order torque ripple are reduced.

  According to the present invention, it is possible to obtain a permanent magnet type motor that can achieve both a reduction in cogging torque and a reduction in torque ripple, as well as a reduction in size and weight, and a reduction in torque ripple. The torque ripple 6th order generated by the magnetic saturation of the stator core is small, and a small, high efficiency, low vibration, low noise permanent magnet motor can be realized.

It is sectional drawing which shows the permanent magnet type motor of Embodiment 1 of this invention. It is sectional drawing which shows the permanent magnet type motor of Embodiment 2 of this invention. It is sectional drawing which shows the permanent magnet type motor of Embodiment 3 of this invention. FIG. 3 is a circuit configuration diagram showing a drive circuit of the permanent magnet type motor according to the first embodiment. It is explanatory drawing which shows the relationship between the torque ripple and cogging torque of the conventional permanent magnet type motor. It is explanatory drawing which shows the relationship between the torque ripple and cogging torque of the permanent magnet type motor of this invention. It is explanatory drawing which shows the cogging torque waveform of this invention and the conventional permanent magnet type | mold motor. It is explanatory drawing which shows the torque ripple waveform of this invention and the conventional permanent magnet type | mold motor. It is sectional drawing which shows the permanent magnet type motor of Embodiment 4 of this invention. FIG. 10 is a cross-sectional view showing another example of the permanent magnet type motor in the fourth embodiment. It is sectional drawing which shows the permanent magnet type motor of Embodiment 5 of this invention. FIG. 3 is a cross-sectional view of the main part showing the slot opening and its peripheral part in the permanent magnet type motor of the first embodiment. FIG. 3 is an explanatory diagram illustrating a connection example of armature windings of the permanent magnet type motor according to the first embodiment. FIG. 6 is an explanatory diagram showing an example of connection of armature windings of a permanent magnet type motor according to a second embodiment. FIG. 10 is an explanatory diagram illustrating an example of connection of armature windings of a permanent magnet type motor according to a fourth embodiment. FIG. 10 is a cross-sectional view showing another example of the permanent magnet motor according to the fifth embodiment. It is a schematic block diagram which shows the electric power steering apparatus of Embodiment 6 of this invention.

Hereinafter, preferred embodiments of a permanent magnet motor for electric power steering according to the present invention will be described with reference to the drawings.
Embodiment 1 FIG.
FIG. 1 is a cross-sectional view of the permanent magnet type motor 10 of the first embodiment, and shows an example of 10 poles and 12 slots.
The rotor 11 is provided so as to be rotatable inside the stator 21, and is provided at equal intervals on the shaft 14, the rotor core 12 provided on the outside thereof, and the outer peripheral side of the rotor core 12. A permanent magnet 13 is provided.
The stator 21 includes an annular core back 23, a total of 12 teeth 24 extending from the core back 23 in the inner diameter direction, and a stator core 22 in which a slot 27 is provided between two adjacent teeth 24. , Armature windings 30 wound around each tooth 24 in a concentrated manner.
In FIG. 1, for simplicity, an insulator provided between the armature winding 30 and the stator core 22 and a frame provided on the outer periphery of the stator core 22 are omitted.
For convenience, numbers 1 to 12 are assigned to the teeth 24. Further, the armature winding (hereinafter also referred to as a coil) 30 that is intensively wound around each tooth 24 is numbered for convenience so that it can be identified as one of the three-phase coils of U, V, and W. It expresses.

Each UVW phase is
U phase is U11, U12, U21, U22
V phase is 4 pieces of V11, V12, V21, V22
The W phase is composed of four pieces of W11, W12, W21, and W22. As shown in FIG. 1, each coil corresponds to each of the teeth 24-1 to U11, U12, V11, V12, W11, W12. , U21, U22, V21, V22, W21, W22 are arranged in this order.

The winding direction of the winding is
U11 and U12 are opposite to each other
U21 and U22 are opposite to each other
V11 and V12 are opposite to each other
V21 and V22 are opposite to each other
W11 and W12 are opposite to each other
W21 and W22 are opposite to each other.

These coils are shown in FIG.
U11 and U21 are connected in series to form a U1-phase coil,
V11 and V21 are connected in series to form a V1-phase coil.
W11 and W21 are connected in series to form a W1 phase coil.
The above three coils are Y-connected with N1 as a neutral point, and constitute a first armature winding 30-1.
Also,
U12 and U22 are connected in series to form a U2-phase coil,
V12 and V22 are connected in series to form a V2-phase coil.
W12 and W22 are connected in series to form a W2-phase coil,
The above three coils are Y-connected with N2 as a neutral point to constitute a second armature winding 30-2.

Next, the drive circuit will be described.
FIG. 4 is a circuit configuration diagram including motor 10 and ECU 101 in the first embodiment.
The motor 10 is the permanent magnet motor 10 having 10 poles and 12 slots as described in FIG.
In FIG. 4, details are omitted for simplicity, and only the armature winding 30 of the motor 10 is shown.
The armature winding 30 of the motor 10 includes a first armature winding 30-1 constituted by a first U-phase winding U1, a first V-phase winding V1, and a first W-phase winding W1. The second armature winding 30-2 is composed of a second U-phase winding U2, a second V-phase winding V2, and a second W-phase winding W2.
Since the ECU 101 is also simple, details are omitted, and only the power circuit portion of the inverter is shown.
The ECU 101 includes two inverters 102 and supplies three-phase currents to the first and second armature windings 30-1 and 30-2 from the respective inverters 102-1 and 102-2.
The ECU 101 is supplied with DC power from a power source 103 such as a battery, and is connected to a power relay 105 through a noise removing coil 104.
In FIG. 4, the power source 103 is depicted as if inside the ECU 101, but in reality, power is supplied from an external power source such as a battery via a connector.
The power relay 105 includes two power relays 105-1 and 105-2, each of which is composed of two MOS-FETs. When a failure occurs, the power relay 105 is opened to prevent an excessive current from flowing.
In FIG. 4, the power supply relay 105 is connected in the order of the power supply 103, the coil 104, and the power supply relay 105, but it goes without saying that the power supply relay 105 may be provided at a position closer to the power supply 103 than the coil 104.
Capacitor 106-1 and capacitor 106-2 are smoothing capacitors. In FIG. 4, each capacitor is composed of one capacitor, but it goes without saying that a plurality of capacitors may be connected in parallel.

Each of the inverter 102-and the inverter 102-2 is configured by a bridge using six MOS-FETs. In the inverter 102-1, the MOS-FET 107-1 and the MOS-FET 107-2 are connected in series, and the MOS-FET 107- 3, MOS-FET 107-4 are connected in series, MOS-FET 107-5 and MOS-FET 107-6 are connected in series, and these three sets of MOS-FETs are connected in parallel.
Further, one shunt resistor is connected to each of the lower three MOS-FETs 107-2, 4 and 6 on the GND (ground) side. The shunt 109-1, the shunt 109-2, and the shunt 109-3 are connected to each other. It is said. These shunt resistors are used for detecting the current value.
In addition, although the example of three shunts was shown, since two shunts may be used, current detection is possible even with one shunt. Needless to say.

As shown in FIG. 4, the current is supplied to the motor 10 side between the MOS-FETs 107-1 and 2 through the bus bar to the U1 phase of the motor 10, and between the MOS-FETs 107-3 and 4 through the bus bar. Is supplied to the W1 phase of the motor 10 from between the MOS-FETs 107-5 and 6 through a bus bar or the like.
The inverter 102-2 has the same configuration. In the inverter 102-2, the MOS-FET 108-1 and the MOS-FET 108-2 are connected in series, and the MOS-FET 108-3 and the MOS-FET 108-4 are connected in series. MOS-FET 108-5 and MOS-FET 108-6 are connected in series, and these three sets of MOS-FETs are connected in parallel.
Further, one shunt resistor is connected to each of the lower three MOS-FETs 108-2, 4 and 6 on the GND (ground) side, and the shunt 110-1, the shunt 110-2, and the shunt 110-3. It is said.
These shunt resistors are used for detecting the current value. In addition, although the example of three shunts was shown, since two shunts may be used, current detection is possible even with one shunt. Needless to say.

As shown in FIG. 4, the current is supplied to the motor 10 from between the MOS-FETs 10-1, 2 to the U2 phase of the motor 10 through a bus bar, and from between the MOS-FETs 108-3, 4 to the motor 10 through the bus bar. Are supplied to the W2 phase of the motor 10 from between the MOS-FETs 108-5 and 6 through a bus bar or the like.
The two inverters 102-1 and 102-2 are switched by sending a signal from the control circuit (not shown) to the MOS-FET in accordance with the rotation angle detected by the rotation angle sensor 111 provided in the motor 10, A desired three-phase current is supplied to the second armature windings 30-1 and 30-2.
For the rotation angle sensor 111, a resolver, a GMR sensor, an MR sensor, or the like is used.

FIG. 12 is a cross-sectional view of the main part showing the slot opening 28 of the stator core 22, the slot opening, and the periphery thereof. For simplicity, only three teeth 24 and three magnetic poles of the permanent magnet 13 are shown.
The stator core 22 has a tooth 24 extending from the annular core back 23 toward the inner diameter side and a tooth tip 26 having a shape extending in the circumferential direction. A slot opening 28 is provided between adjacent teeth 24, and the adjacent teeth 24 are joined by a joining surface 38.
A frame 35 is fixed to the outer peripheral side of the stator core 22 by press fitting or shrink fitting.
An insulator 37 is provided in the slot 27 of the stator core 22 to ensure electrical insulation between the stator core 22 and the armature winding 30.
The armature winding 30 is intensively wound around each tooth 24.

As already described, the coils U11 and U12 are wound in opposite directions to form a U1 phase and a U2 phase. If the phase difference between the U1 phase and the U2 phase is the same or a small phase difference such as 20 ° to 40 °, a large current flows through the two coils simultaneously.
At this time, a leakage magnetic flux is generated in the magnetic path 36 between the adjacent teeth 24. This leakage magnetic flux does not contribute to the torque of the motor 10, but increases the magnetic flux density of the teeth 24 and magnetic saturation occurs in the stator core 22, resulting in torque ripple 6th order (component of electrical angle 360 degree period as primary). There was a problem that it would increase.
That is, when the armature windings 30 of at least one of the U1 phase and the U2 phase are accommodated in both the slots 27 adjacent to each other of the stator core 22, the leakage magnetic flux increases, as described above. There is a big problem.
On the other hand, if the slot opening width Ws of the slot opening 28 is increased, the leakage magnetic flux can be reduced. However, if the slot opening width Ws is large, the permeance pulsation increases, and the shape error on the rotor 11 side and the permanent magnet are increased. There is a problem that the cogging torque having an order that matches the number of slots Ns increases due to the influence of variations in the shape of 13 and magnetic characteristics.
Therefore, in the prior art, it has been impossible to achieve both a reduction in cogging torque in which the order per revolution matches the number of slots Ns and a reduction in the sixth order of torque ripple.

FIG. 5 is a diagram showing the relationship between the slot opening width, cogging torque, and torque ripple of a conventional permanent magnet type motor.
The horizontal axis is a parameter obtained by normalizing the slot opening width Ws with the slot pitch. The slot pitch was a value obtained by dividing the circumference of a circle having the radius Rs in the stator by the number of slots Ns. That is, Ws / (2πRs / Ns) was used as a parameter.
As the slot opening width Ws increases, the cogging torque 12th order (Ns = 12) increases rapidly.
On the other hand, the torque ripple increases as the slot opening width decreases. This is a result of magnetic saturation occurring in the stator core 22 due to the influence of the magnetic flux leaking from the slot opening 28 as the magnetic path 36, as described above.

On the other hand, when the motor 10 of FIG. 1 is driven by the two sets of three-phase inverters 102-1 and 102-2 shown in FIG. Since the cogging torque is not affected by the drive circuit and the winding, it shows the same value as FIG. On the other hand, torque ripple is reduced over the entire area.
This is because the torque difference between the first armature winding 30-1 and the second armature winding 30-2 is 6 to 40 degrees by setting the electrical angle to 20 ° to 40 °, preferably 30 °. This is because the next component is reduced. This phase difference may be changed according to the driving state of the motor 10, or may be fixed at 30 °, for example.
In particular, the torque ripple reduction effect is greater than in the conventional case when the slot opening width Ws is small. Even if magnetic saturation occurs in the stator core 22, torque is generated by the two sets of three-phase inverters 102-1 and 102-2. It shows that the ripple 6th order component is reduced.
Ws / (2πRs / Ns) ≦ 0.15
It can be seen that cogging torque Ns order reduction and torque ripple sixth order reduction are compatible.

FIG. 7 shows a cogging torque waveform. The horizontal axis represents the rotation angle (mechanical angle), and the vertical axis represents the cogging torque. Conventionally, many cogging torques of the 12th order (corresponding to the number of slots Ns) per rotation are included, but in the present invention, they are small and greatly reduced.
FIG. 8 shows a torque ripple waveform.
The horizontal axis represents the rotation angle (electrical angle), and the vertical axis represents the torque ripple. It can be seen that the electrical angle sixth-order component is greatly reduced.

In this example, the case where the armature windings 30 of at least one of the U1 phase and the U2 phase are accommodated in both the slots 27 adjacent to each other in the stator core 22 has been described. The same effect can be obtained even when the U1 phase is accommodated in both of the slots 27 adjacent to each other.
Moreover, although the example of Y connection was shown in FIG. 13, the same effect is acquired also by (DELTA) connection.

Therefore, as in the first embodiment,
A rotor 11 comprising a rotor core 12 and a plurality of permanent magnets 13 provided on the rotor core;
A stator 21 having a stator core 22 having a plurality of teeth 24 and two sets of three-phase armature windings 30 housed in a plurality of slots 27 formed in the stator core;
One armature winding 30-1 is supplied with current from the first inverter 102-1, and the other one armature winding 30-2 is supplied with current from the second inverter 102-2. In the constructed permanent magnet type motor 10,
For the two sets of three-phase armature windings,
When the first armature winding 30-1 is the U1, V1, and W1 phases, and the second armature winding 30-2 is the U2, V2, and W2 phases,
Of the plurality of slots 27, the U1 phase of the first armature winding is housed in both of the adjacent slots.
The U1 phase, V1 phase, W1 phase and U2 phase, V2 phase, W2 phase of the armature winding are driven with an electrical angle of 20 ° to 40 ° shifted from each other,
Furthermore, the slot opening width Ws of the stator core 22 is:
Ws / (2πRs / Ns) ≦ 0.15
However, Rs is the inner radius of the stator core, and Ns is the number of slots of the stator core, so that the torque ripple sixth order generated by the magnetic saturation of the stator core is small, which is small, high efficiency, low A motor with low vibration and noise can be obtained.
Further, it is possible to achieve the effect of coexistence with the reduction of the cogging torque whose order matches the number of slots.
If the slot opening width Ws is smaller than the coil wire diameter Dc, the coil does not come out of the slot 27 toward the rotor 11, and the coil does not get caught between the gaps between the rotor 11 and the stator 21. An effect is also obtained.

In addition, the configuration of the first embodiment has an effect that the tooth width and the core back thickness can be reduced to reduce the size of the motor.
If the tooth width Wt in FIG. 12 is small, the magnetic flux density in the portion of the tooth 24 becomes high, magnetic saturation occurs, and the torque ripple sixth order (with the electrical angle of 360 degrees as the primary) greatly increases. Especially with a small slot opening width Ws
Ws / (2πRs / Ns) ≦ 0.15
In such a case, the effect becomes significant.
However, with the permanent magnet motor 10 having the configuration of the first embodiment, the torque ripple sixth order is reduced even if magnetic saturation occurs in the iron core, so that the cross-sectional area of the slot 27 can be increased, and the armature winding Since the resistance can be reduced, there is an effect that a small and high output motor can be obtained.
When a rare earth permanent magnet is used as the permanent magnet 13, the teeth width Wt is at its smallest point.
0.50 ≦ Wt / (2πRs / Ns) ≦ 0.65
The slot cross-sectional area can be secured widely. Here, Rs is the inner radius of the stator core 22, and Ns is the number of slots of the stator core 22.

The same applies to the core back thickness Wc. If the core back thickness Wc is small, the magnetic flux density in the core back 23 portion increases, magnetic saturation occurs, and the torque ripple sixth order (with an electrical angle of 360 degrees as the primary order) greatly increases.
Especially with a small slot opening width
Ws / (2πRs / Ns) ≦ 0.15
In such a case, the effect becomes significant.
However, with the permanent magnet motor 10 having the configuration of the first embodiment, the torque ripple sixth order is reduced even if magnetic saturation occurs in the iron core, so that the cross-sectional area of the slot 27 can be increased, and the armature winding Since the resistance can be reduced, there is an effect that a small and high output motor can be obtained.
Since the core back 23 particularly affects the diameter of the motor 10, it also has an effect of contributing to space saving of the electric power steering apparatus.
When a rare earth permanent magnet is used as the permanent magnet 13, the core back thickness Wc is at its smallest point.
0.18 ≦ Wc / (2πRs / M) ≦ 0.50
The outer diameter of the motor 10 can be reduced.
However, Rs is the inner radius of the stator core 22, and M is the number of poles.

Embodiment 2. FIG.
FIG. 2 is a cross-sectional view of the permanent magnet type motor 10 of the second embodiment.
The stator 21 includes an annular core back 23, a total of 18 teeth 24 extending in the inner diameter direction from the core back 23, a stator core 22 in which a slot 27 is provided between two adjacent teeth 24, The armature winding 30 is wound around each tooth 24 in a concentrated manner.
In FIG. 2, for the sake of simplicity, an insulator provided between the armature winding 30 and the stator core 22 and a frame provided on the outer periphery of the stator core are omitted. For convenience, numbers 1 to 18 are assigned to the teeth 24.
Further, the armature windings (coils) 30 that are intensively wound around the teeth 24 are numbered for convenience so that they can be identified as any of the three-phase coils U, V, and W. Yes.

Each UVW phase is
U phase is U11, U12, U13, U21, U22, U23
V phase is V11, V12, V13, V21, V22, V23
The W phase is composed of six pieces of W11, W12, W13, W21, W22, and W23. As shown in FIG. 1, each coil corresponds to each of the teeth 24-1 to U11, U11, V11, V12, W11. , U12, U13, V13, W12, W13, U21, V21, V22, W21, U22, U23, V23, W22, W23, that is, at least one of the slots 27 adjacent to each other in the stator core 22 Is arranged such that at least one of the armature windings of the U1 phase or the U2 phase is accommodated.
U11, U12, and U13 are connected in series to form a U1 phase that is a first U-phase winding. At this time, the coil winding direction of U12 is opposite to that of U11 and U13.
U21, U22, and U23 are connected in series to form a U2 phase that is a second U-phase winding. At this time, the coil winding direction of U22 is opposite to that of U21 and U23.
V11, V12, and V13 are connected in series to form the V1 phase that is the first V-phase winding.
At this time, the coil winding direction of V12 is opposite to that of V11 and V13.
Also, V21, V22, and V23 are connected in series to form a V2 phase that is a second V-phase winding. At this time, the winding direction of V22 is opposite to that of V21 and V23.
W11, W12, and W13 are connected in series to form the W1 phase that is the first W-phase winding. At this time, the coil winding direction of W12 is opposite to that of W11 and W13.
W21, W22, and W23 are connected in series to form a W2 phase that is a second W-phase winding. At this time, the coil winding direction of W22 is opposite to that of W21 and W23.
FIG. 14 shows how these 18 coils are connected.

As shown in FIG.
U11, U12, and U13 are connected in series to form a U1 phase coil.
V11, V12, and V13 are connected in series to form a V1 phase coil.
W11, W12, and W13 are connected in series to form a W1 phase coil.
The above three coils are Y-connected with N1 as a neutral point, and constitute a first armature winding 30-1.
Also,
U21, U22, and U23 are connected in series to form a U2-phase coil.
V21, V22, and V23 are connected in series to form a V2-phase coil.
W21, W22, and W23 are connected in series to form a W2-phase coil.
The above three coils are Y-connected with N2 as a neutral point to constitute a second armature winding 30-2.

The rotor 11 is a motor 10 having 14 poles and a stator 21 having 18 slots. The rotor 11 is provided inside the stator 21 so as to be rotatable. The rotor 11 is provided with a shaft 14 serving as a rotating shaft and a rotor core 12 outside the shaft 14.
The permanent magnet 13 has a shape in which the length in the radial direction is longer than the length in the circumferential direction, and 14 permanent magnets 13 are arranged at equal intervals in the circumferential direction. The magnetization direction of the permanent magnet 13 is magnetized so that N and S shown in FIG.
That is, the facing surfaces of the adjacent permanent magnets 13 are magnetized so as to have the same pole. By adopting such a magnetization direction, there is an effect that the magnetic flux is concentrated on the rotor core 12 and the magnetic flux density is increased.

A rotor core 12 is interposed between adjacent permanent magnets 13. The surface of the rotor core 12 facing the stator 21 has a curved surface portion 31, and the curved surface has a convex shape that shortens the gap length with the stator 21 at an intermediate point between adjacent permanent magnets 13. A curved surface is formed.
With such a shape, the waveform of the magnetic flux density generated in the air gap can be smoothed, so that cogging torque and torque ripple can be reduced.
Further, a nonmagnetic portion 32 is provided so as to be in contact with the end face on the inner diameter side of the permanent magnet 13. This part may be air, may be filled with resin, or a nonmagnetic metal such as stainless steel or aluminum may be inserted.
By doing in this way, the leakage magnetic flux of the permanent magnet 13 can be reduced.
A connecting portion 34 is provided between the rotor core 12 between the adjacent permanent magnets 13 and the rotor core 12 provided so as to surround the outer periphery of the shaft 14. This has the function of mechanically connecting the two. Since the connecting portion 34 is longer in the radial direction than the circumferential length, the magnetic flux can be concentrated on the rotor core 12 and the torque becomes high.
In the structure in which the permanent magnet 13 is embedded in the rotor core 12, there is a problem that the torque ripple is increased and the vibration noise is increased as compared with the surface magnet type. However, the connection configuration of the armature winding 30 is shown in FIG. In this way, it is further driven by the two sets of three-phase inverters 102-1 and 102-2 shown in FIG. 4, and the phase difference between the first armature winding 30-1 and the second armature winding 30-2 is calculated. By setting the electrical angle to 20 ° to 40 °, preferably 30 °, the sixth-order torque ripple can be reduced.

Furthermore, the slot opening width Ws of the stator core 22 is
Ws / (2πRs / Ns) ≦ 0.15
However, Rs: the inner radius of the stator core, Ns: the number of slots of the stator core, the cogging torque whose order matches Ns is significantly reduced, and the stator core is affected by leakage magnetic flux. Even if magnetic saturation occurs in 22, sixth-order torque ripple can be reduced.
Furthermore, with 14 poles and 18 slots, the second-order electromagnetic excitation force can be reduced, resulting in low vibration and low noise. That is, it is possible to achieve both high torque and low vibration / noise. In addition to the example of FIG. 2, the same effect can be obtained if the number of poles M = 18n ± 4n and the number of slots Ns = 18n (n is an integer).

Embodiment 3 FIG.
FIG. 3 is a cross-sectional view of the permanent magnet type motor 10 of the third embodiment.
The rotor 11 is provided so as to be rotatable inside the stator 21, and the permanent magnet 14 is provided at equal intervals on the outer periphery of the rotor core 12 and the rotor core 12 provided outside the shaft 14. It has a magnet 13.
The stator 21 includes an annular core back 23, a total of 24 teeth 24 extending in the inner diameter direction from the core back 23, and a stator core 22 in which a slot 27 is provided between two adjacent teeth 24 and each tooth. The armature winding 30 is wound around 24 in a concentrated manner.
In FIG. 3, for the sake of simplicity, an insulator provided between the armature winding 30 and the stator core 22 and a frame provided on the outer periphery of the stator core 22 are omitted.
For convenience, numbers 1 to 24 are assigned to the teeth 24. Further, the armature windings 30 (coils) that are intensively wound around the teeth 24 are numbered and expressed for convenience so that it can be understood which of the three-phase coils U, V, and W. Yes.

Each UVW phase is
There are 8 U phases: U11, U12, U21, U22, U31, U32, U41, U42
V phase is 8 pieces of V11, V12, V21, V22, V31, V32, V41, V42
The W phase is composed of eight pieces of W11, W12, W21, W22, W31, W32, W41, and W42, and each coil corresponds to each of the teeth 24-1 to 24, as shown in FIG. , V11, V12, W11, W12, U21, U22, V21, V22, W21, W22, U31, U32, V31, V32, W31, W32, U41, U42, V41, V42, W41, W42 It has become.

The winding direction of the coil is
U11 and U12 are opposite to each other, U21 and U22 are opposite to each other,
U31 and U32 are opposite to each other, U41 and U42 are opposite to each other, and the same applies to the V phase and the W phase.
These are Y-connected or Δ-connected to form two sets of three-phase armature windings 30.
When the two sets of armature windings 30 are configured, the first armature winding 30-1 is configured from U11, U21, U31, U41, V11, V21, V31, V41, W11, W21, W31, and W41. , U12, U22, U32, U42, V12, V22, V32, V42, W12, W22, W32, W42, constitute a second armature winding 30-2.

In the structure of FIG. 3, the permanent magnet 13 of the rotor 11 is longer in the radial direction than the circumferential length, so that the magnetic flux can be concentrated on the rotor core 12 and the torque becomes high.
The structure in which the permanent magnet 13 is embedded in the rotor core 12 has a problem that the electromagnetic excitation force is increased and the vibration noise is increased as compared with the surface magnet type, but there are two sets of three-phase inverters shown in FIG. The phase difference between the first armature winding 30-1 and the second armature winding 30-2 is set to an electrical angle of 20 ° to 40 °, preferably an electrical angle of 30 °. As a result, the sixth-order torque ripple can be reduced.

Furthermore, the slot opening width Ws of the stator core 22 is
Ws / (2πRs / Ns) ≦ 0.15
However, Rs: the inner radius of the stator core, Ns: the number of slots of the stator core, the cogging torque whose order matches Ns is significantly reduced, and the stator core is affected by leakage magnetic flux. Even if magnetic saturation occurs in 22, sixth-order torque ripple can be reduced.
Further, in the case of 20 poles and 24 slots, when the number of poles is M and the number of slots is Ns, the greatest common divisor P of M and Ns is 4, which is 3 or more.
At this time, the second-order electromagnetic excitation force can be reduced, resulting in low vibration and low noise. That is, it is possible to achieve both high torque and low vibration / noise. If P is 3 or more, the same effect can be obtained.
In addition to the example of FIG. 3, the same effect can be obtained if the number of poles is M = 12n ± 2n and the number of slots is Ns = 12n (n is an integer of 2 or more).

Embodiment 4 FIG.
FIG. 9 is a sectional view of the permanent magnet type motor 10 according to the fourth embodiment.
The rotor 11 is provided so as to be rotatable inside the stator 21, and the permanent core provided at equal intervals on the outer periphery side of the shaft 14, the rotor core 12 provided on the outer side of the shaft 14, and the rotor core 12. It has a magnet 13.
The stator 21 includes an annular core back 23, a total of 48 teeth 24 extending in the inner diameter direction from the core back 23, and a stator core 22 in which a slot 27 is provided between two adjacent teeth 24. Each slot 27 has a distributed armature winding 30.
This is an example in which the number of slots for each pole and each phase is two.
In FIG. 9, for simplicity, an insulator provided between the armature winding 30 and the stator core 22 and a frame provided on the outer periphery of the stator core 22 are omitted.

For convenience, numbers 1 to 6 are assigned to the slots 27.
The coils stored in the slots 27-1 to 6 are U11, U12, W11, W12, V11, V12 in this order, and the slots 27-7 to 12 are U21, U22, W21, W22 in order clockwise. , V21, V22.
In general, Um1, in order of the numbers m, m + 1, m + 2, m + 3, m + 4, and m + 5 of the slot 27.
Um2, Wm1, Wm2, Vm1, and Vm2. However, m represents the integer of 1-8.
Further, Um1, Vm1, and Wm1 constitute a first armature winding 30-1 having three phases of U1, V1, and W1, and Um2, Vm2, and Wm2 are three of U2, V2, and W2, respectively. A second armature winding 30-2 of the phase is configured.
As shown in FIG. 15, two sets of Y connections may be used, or Δ connections may be used.
4 is driven by two sets of three-phase inverters 102-1 and 102-2, and the phase difference between the first armature winding 30-1 and the second armature winding 30-2 is set to an electrical angle of 20 ° to 20 °. 40 °, preferably an electrical angle of 30 °.

As shown in FIG. 9, the slot 27 of the stator core 22 has a structure in which the iron core is completely connected to the adjacent teeth 24, that is, has a closed slot portion 29.
In this case, a leakage magnetic flux is generated through a magnetic path between adjacent teeth 24. As a result, the magnetic flux density of the stator core 22 increases, and magnetic saturation occurs.
Due to this magnetic saturation, the torque ripple sixth-order component becomes large, and the motor 10 is not suitable for the electric power steering apparatus. However, according to the configuration of the present embodiment, the two sets of three-phase inverters 102-1 and 102-2 are used. The phase difference between the first armature winding 30-1 and the second armature winding 30-2 is set to an electrical angle of 20 ° to 40 °, and preferably an electrical angle of 30 °. Ingredients are greatly reduced.
Further, since the closed slot structure is used, the influence of the shape error on the rotor 11 side, the variation of the shape of the permanent magnet 13 and the magnetic characteristics is reduced, and the cogging torque whose order matches the slot number Ns can be reduced.

Here, the slot opening width Ws of the stator core 22 is
Ws / (2πRs / Ns) ≦ 0.15
However, if the configuration is such that Rs is the inner radius of the stator core and Ns is the number of slots of the stator core, the same effect as the closed slot can be obtained.

FIG. 10 is a cross-sectional view of a permanent magnet motor 10 of another example of the present embodiment.
The rotor 11 is a motor 10 having 10 poles and a stator 21 having 60 slots. The stator 21 has an annular core back 23 and a total of 60 teeth 24 extending from the core back 23 in the inner diameter direction. And a stator core 22 having a slot 27 between two adjacent teeth 24, and a distributed armature winding 30 in each slot 27.
In FIG. 10, for simplicity, an insulator provided between the armature winding 30 and the stator core 22 and a frame provided on the outer periphery of the stator core 22 are omitted.

For convenience, numbers 1 to 6 are assigned to the slots 27.
The coils stored in the slots 27-1 to 6 are U11, U12, W11, W12, V11, V12 in this order, and the slots 27-7 to 12 are U21, U22, W21, W22 in order clockwise. , V21, V22.
When generalized, Um1 is sequentially assigned to the numbers m, m + 1, m + 2, m + 3, m + 4, and m + 5 of the slot 27.
Um2, Wm1, Wm2, Vm1, and Vm2. However, m represents the integer of 1-10.
Further, Um1, Vm1, and Wm1 constitute a first armature winding 30-1 having three phases of U1, V1, and W1, and Um2, Vm2, and Wm2 are three of U2, V2, and W2, respectively. A second armature winding 30-2 of the phase is configured.
As shown in FIG. 15, two sets of Y connections may be used, or Δ connections may be used.
4 is driven by two sets of three-phase inverters 102-1 and 102-2, and the phase difference between the first armature winding 30-1 and the second armature winding 30-2 is set to an electrical angle of 20 ° to 40 °, preferably an electrical angle of 30 °.

The rotor 11 is provided inside the stator 21 so as to be rotatable. The rotor 11 is provided with a shaft 14 serving as a rotating shaft and a rotor core 12 outside the shaft 14.
The permanent magnet 13 has a shape in which the length in the radial direction is longer than the length in the circumferential direction, and ten permanent magnets 13 are arranged at equal intervals in the circumferential direction. The magnetization direction of the permanent magnet 13 is magnetized in such a direction that N and S shown in FIG. That is, the facing surfaces of the adjacent permanent magnets 13 are magnetized so as to have the same pole.
By adopting such a magnetization direction, there is an effect that the magnetic flux is concentrated on the rotor core 12 and the magnetic flux density is increased.

A rotor core 12 is interposed between adjacent permanent magnets 13. The surface of the rotor core 12 facing the stator 21 has a curved surface portion 31, and the curved surface has a convex shape that shortens the gap length with the stator 21 at an intermediate point between adjacent permanent magnets. A curved surface is formed.
With such a shape, the waveform of the magnetic flux density generated in the air gap can be smoothed, so that cogging torque and torque ripple can be reduced.
Further, a nonmagnetic portion 32 is provided so as to be in contact with the end face on the inner diameter side of the permanent magnet 13. This part may be air, may be filled with resin, or a nonmagnetic metal such as stainless steel or aluminum may be inserted.
By doing in this way, the leakage magnetic flux of the permanent magnet 13 can be reduced.
A connecting portion 34 is provided between the rotor core 12 between the adjacent permanent magnets 13 and the rotor core 12 provided so as to surround the outer periphery of the shaft 14. This has the function of mechanically connecting the two.

As shown in FIG. 10, the slot 27 of the stator core 22 has a structure in which the iron core is completely connected to the adjacent teeth 24, that is, has a closed slot portion 29.
In this case, a leakage magnetic flux is generated through a magnetic path between adjacent teeth 24. As a result, the magnetic flux density of the stator core 22 increases, and magnetic saturation occurs.
Due to this magnetic saturation, the torque ripple 6th order component becomes large and the motor 10 is not suitable for the electric power steering apparatus. However, according to the configuration of the present embodiment, two sets of three-phase inverters 102- 1 and 2, and the phase difference between the first armature winding 30-1 and the second armature winding 30-2 is set to an electrical angle of 20 ° to 40 °, preferably an electrical angle of 30 °. Torque ripple 6th order component is greatly reduced.
Further, since the structure is closed, the influence of the shape error on the rotor 11 side, the variation of the shape and magnetic characteristics of the permanent magnet 13 is reduced, and the cogging torque whose order matches the slot number Ns can be reduced.

Here, the slot opening width Ws of the stator core 22 is
Ws / (2πRs / Ns) ≦ 0.15
However, if the configuration is such that Rs is the inner radius of the stator core and Ns is the number of slots of the stator core, the same effect as the closed slot can be obtained.

In FIG. 10, since the radial length is longer than the circumferential length, the magnetic flux can be concentrated on the rotor core 12 and the torque becomes high.
The structure in which the permanent magnet 13 is embedded in the rotor core 12 has a problem that the torque ripple is increased and the vibration noise is increased as compared with the surface magnet type, but the configuration of the connection of the armature winding 30 is shown in FIG. In this way, it is further driven by the two sets of three-phase inverters 102-1 and 102-2 shown in FIG. 4, and the phase difference between the first armature winding 30-1 and the second armature winding 30-2 is calculated. By setting the electrical angle to 20 ° to 40 °, preferably 30 °, the sixth-order torque ripple can be reduced.
Although the case where the number of slots for each pole and each phase is 2 is shown, the same effect can be obtained because the same armature winding 30 can be configured if the number is an even number of 2 or more.

Embodiment 5 FIG.
FIG. 11 is an example in which the arrangement of the permanent magnet type motor 10 of FIG. 10 of the fourth embodiment and the permanent magnets 13 of the rotor 11 are different.
The structure of the stator 21 is the same as in FIG. The rotor 11 is provided inside the stator 21 so as to be rotatable.
The rotor 11 is provided with a shaft 14 serving as a rotating shaft and a rotor core 12 outside the shaft 14.
The permanent magnet 13 has a shape in which the length in the radial direction is longer than the length in the circumferential direction, and five permanent magnets 13 are arranged at equal intervals in the circumferential direction.
The magnetization direction of the permanent magnet 13 is magnetized in such a direction that N and S shown in FIG. That is, the adjacent permanent magnets 13 are magnetized so that the facing surfaces have different poles.
Further, a nonmagnetic portion 33 is provided between the adjacent permanent magnets 13. This part may be air, filled with resin, or a nonmagnetic metal such as stainless steel or aluminum may be inserted.
By providing the non-magnetic portion 33 with the magnetization direction described above, the magnetic flux is concentrated on the rotor core 12 and the magnetic flux density is increased.
In addition, the rotor core 12 is present on both sides of the permanent magnet 13 in the circumferential direction.
The surface of the rotor core 12 facing the stator 21 has a curved surface portion 31, and the curved surface has a convex shape that shortens the gap length with the stator 21 at an intermediate point between adjacent permanent magnets. A curved surface is formed.
With such a shape, the waveform of the magnetic flux density generated in the air gap can be smoothed, so that cogging torque and torque ripple can be reduced.
Further, the nonmagnetic portion 32 is provided so as to be in contact with the end surfaces on the inner diameter side of the permanent magnet 13 and the nonmagnetic portion 33. This part may be air, may be filled with resin, or a nonmagnetic metal such as stainless steel or aluminum may be inserted.
By doing in this way, the leakage magnetic flux of the permanent magnet 13 can be reduced.
A connecting portion 34 is provided between the rotor core 12 between the adjacent permanent magnets 13 and the rotor core 12 provided so as to surround the outer periphery of the shaft 14. This has the function of mechanically connecting the two.

In such a rotor 11 structure, since the number of permanent magnets 13 is halved, the magnetic flux density distribution is non-uniform compared to the rotor 11 structure of FIG. 10, resulting in an increase in torque ripple. There was a problem.
In addition, since the stator core 22 has a structure having the closed slot portion 29, there is a problem that torque ripple increases due to magnetic saturation of the iron core caused by leakage magnetic flux between the teeth 24.
However, according to the configuration of the present embodiment, the first armature winding 30-1 and the second armature winding 30- are driven by two sets of three-phase inverters 102-1 and 102-2 as shown in FIG. Since the phase difference of 2 is set to an electrical angle of 20 ° to 40 °, preferably 30 °, the torque ripple sixth-order component is greatly reduced.
Further, since the closed slot structure is used, the influence of the shape error on the rotor 11 side, the variation of the shape of the permanent magnet 13 and the magnetic characteristics is reduced, and the cogging torque whose order matches the slot number Ns can be reduced.

Here, the slot opening width Ws of the stator core 22 is
Ws / (2πRs / Ns) ≦ 0.15
However, if the configuration is such that Rs is the inner radius of the stator core and Ns is the number of slots of the stator core, the same effect as the closed slot can be obtained.

In FIG. 11, since the radial length is longer than the circumferential length, the magnetic flux can be concentrated on the rotor core 12 and the torque becomes high.
The structure in which the permanent magnet 13 is embedded in the rotor core 12 has a problem that the torque ripple is increased and the vibration noise is increased as compared with the surface magnet type, but the configuration of the connection of the armature winding 30 is shown in FIG. As shown in FIG. 4, the two armature windings 102-1 and 10-2 shown in FIG. 4 are further used to drive the phase difference between the first armature winding 30-1 and the second armature winding 30-2. By setting the electrical angle to 20 ° to 40 °, preferably 30 °, the sixth-order torque ripple can be reduced.

Further, in FIG. 11, the amount of the permanent magnet 13 is half that in FIG. 10, but the torque is not halved, the efficiency of magnet utilization is improved, and the torque and output per unit magnet amount are increased. The cost can be reduced.
In general, the above effect can be obtained if M / 2 permanent magnets 13 of the rotor 11 are arranged in the circumferential direction with respect to the number M of poles of the stator 21.
In particular, when a neodymium-based permanent magnet 13, particularly dysprosium is used, there is an effect that the cost reduction effect is very large.
Moreover, although the example which embedded the permanent magnet 13 in the rotor core 12 was shown in FIG. 11, the structure which has arrange | positioned the permanent magnet 13 on the surface of the rotor core 12 like FIG. 16 may be sufficient.
11 and 16 show the case where the number of slots for each pole and each phase is two. However, if the number of slots is an even number of 2 or more, the same configuration can be obtained for the armature winding 30, and the same effect can be obtained.

Embodiment 6 FIG.
FIG. 17 is an explanatory diagram of an electric power steering device for an automobile.
The driver steers a steering wheel (not shown), and the torque is transmitted to the shaft 201 via a steering shaft (not shown).
At this time, the torque detected by the torque sensor 202 is converted into an electrical signal and transmitted to the ECU 101 (control unit) via the connector 203 through a cable (not shown).
On the other hand, vehicle information such as vehicle speed is converted into an electrical signal and transmitted to the ECU 101 via the connector 204. The ECU 101 calculates necessary assist torque from the vehicle information such as the torque and the vehicle speed, and supplies current to the permanent magnet motor 10 through the inverters 102-1 and 102-2 as shown in FIG. The motor 10 is arranged in a direction parallel to the moving direction of the rack shaft (indicated by an arrow).
The power supply to the ECU 101 is sent from the battery or alternator via the power connector 205. Torque generated by the permanent magnet motor 10 is decelerated by a gear box 206 containing a belt (not shown) and a ball screw (not shown), and a rack shaft (not shown) inside the housing 207 is moved in the direction of the arrow. The driving force is generated to assist the driver's steering force.
As a result, the tie rod 208 moves and the tire can be steered to turn the vehicle. Assisted by the torque of the permanent magnet motor 10, the driver can turn the vehicle with a small steering force.
The rack boot 209 is provided so that foreign matter does not enter the apparatus.

In such an electric power steering apparatus, the cogging torque and torque ripple generated by the motor 10 are transmitted to the driver via the gear, and therefore it is desirable that the cogging torque and torque ripple be small in order to obtain a good steering feeling. .
In addition, it is desirable that vibration and noise when the motor 10 is operated be small.
Therefore, when the motor 10 described in the first to fifth embodiments is applied, the effects described in the respective embodiments can be obtained.
In particular, the second-order electromagnetic excitation force can be reduced, resulting in low vibration and low noise. Furthermore, there is an effect that both high torque and low vibration / noise can be achieved.
As shown in FIG. 17, the motor 10 is arranged in a direction parallel to the moving direction of the rack shaft (indicated by an arrow). Although the electric power steering device is a system suitable for a large vehicle, there is a problem that the motor 10 needs to have a high output, and at the same time the vibration and noise caused by the motor 10 increase.
However, if the motor 10 described in the first to sixth embodiments is applied, this problem can be solved, and the electric power steering device can be applied to a large vehicle, and the fuel consumption can be reduced.
Note that the present invention can be freely combined with each other within the scope of the invention, and each embodiment can be modified or omitted as appropriate.

10: Motor, 11: Rotor, 12: Rotor core, 13: Permanent magnet, 14: Shaft, 21: Stator, 22: Stator core, 23: Core back, 24: Teeth, 26: Teeth tip, 27: Slot, 28: Slot opening, 29: Closed slot, 30: Armature winding, 30-1: First armature winding, 30-2: Second armature winding, 31: Curved surface Part, 32: nonmagnetic part, 33: nonmagnetic part, 34: coupling part, 35: frame, 36: magnetic path, 37: insulator, 38: joint surface, 101: ECU, 102: inverter, 102-1: second 1 inverter, 102-2: second inverter, 103: power supply, 104: coil, 105: power relay, 105-1: first power relay, 105-2: second power relay, 106-1: Capacitor, 106-2: Densers, 107-1 to 6: MOS-FET, 108-1 to 6: MOS-FET, 109-1 to 3: Shunt, 110-1 to 3: Shunt, 111: Rotation angle sensor, 201: Shaft, 202: Torque sensor, 203: connector, 204: connector, 205: power connector, 206: gear box, 207: housing, 208: tie rod, 209: rack boot

Claims (15)

A rotor comprising a rotor core and a plurality of permanent magnets provided on the rotor core;
A stator core having a plurality of teeth and two sets of three-phase armature windings housed in a plurality of slots formed in the stator core;
In a permanent magnet motor configured such that one armature winding is supplied with current from a first inverter and the other one armature winding is supplied with current from a second inverter,
For the two sets of three-phase armature windings,
When the first armature winding is U1, V1, and W1, the second armature winding is U2, V2, and W2.
Of the plurality of slots, either one of the slots adjacent to each other is arranged such that the U1 phase of the first armature winding is placed in one of the slots adjacent to each other. At least one of the U1 phase of the first armature winding or the U2 phase of the second armature winding is placed;
The U1 phase, V1 phase, W1 phase and U2 phase, V2 phase, W2 phase of the armature winding are driven with an electrical angle of 20 ° to 40 ° shifted from each other,
Furthermore, the slot opening width Ws of the stator core is:
Ws / (2πRs / Ns) ≦ 0.15
Where Rs is the inner radius of the stator core, Ns is the number of slots of the stator core,
The teeth width Wt of the stator core is
0.550 ≦ Wt / (2πRs / Ns) ≦ 0.65
A permanent magnet type motor characterized by reducing both cogging torque whose order matches Ns and sixth-order torque ripple. A rotor comprising a rotor core and a plurality of permanent magnets provided on the rotor core;
A stator core having a plurality of teeth and two sets of three-phase armature windings housed in a plurality of slots formed in the stator core;
In a permanent magnet motor configured such that one armature winding is supplied with current from a first inverter and the other one armature winding is supplied with current from a second inverter,
For the two sets of three-phase armature windings,
When the first armature winding is U1, V1, and W1, the second armature winding is U2, V2, and W2.
Of the plurality of slots, either one of the slots adjacent to each other is arranged such that the U1 phase of the first armature winding is placed in one of the slots adjacent to each other. At least one of the U1 phase of the first armature winding or the U2 phase of the second armature winding is placed;
The U1 phase, V1 phase, W1 phase and U2 phase, V2 phase, W2 phase of the armature winding are driven with an electrical angle of 20 ° to 40 ° shifted from each other,
Furthermore, the slot opening width Ws of the stator core is:
Ws / (2πRs / Ns) ≦ 0.15
Where Rs is the inner radius of the stator core, Ns is the number of slots of the stator core,
The core back thickness Wc of the stator core is:
0.18 ≦ Wc / (2πRs / M) ≦ 0.50,
A permanent magnet type motor characterized by reducing both cogging torque whose order matches Ns and sixth-order torque ripple. In claim 1 or claim 2,
The U1 phase winding of the first armature winding is wound around one of adjacent teeth among the plurality of teeth, and the U2 of the second armature winding is wound around the other tooth. Phase winding is wound,
The V1 phase winding of the first armature winding is wound around one of the other adjacent teeth, and the V2 phase winding of the second armature winding is wound around the other tooth.
Furthermore, the W1 phase winding of the first armature winding is wound around one of the other adjacent teeth, and the W2 phase winding of the second armature winding is wound around the other tooth. A permanent magnet type motor characterized by that. In claim 1 or claim 2,
The stator iron core is a permanent magnet type motor characterized in that tips of adjacent teeth are connected to each other. In claim 1 or claim 2,
A permanent magnet motor, wherein the greatest common divisor P of M and Ns is 3 or more when the number of poles of the rotor is M and the number of slots of the stator core is Ns. In claim 1 or claim 2,
A permanent magnet motor characterized by satisfying M = 18n ± 4n and Ns = 18n (n: integer), where M is the number of rotor poles and Ns is the number of slots in the stator core. In claim 1 or claim 2,
A permanent magnet motor characterized by satisfying M = 12n ± 2n and Ns = 12n (n: integer) when the number of poles of the rotor is M and the number of slots of the stator core is Ns. In claim 1 or claim 2,
A permanent magnet type motor having a slot opening width Ws smaller than a wire diameter of the armature winding. In claim 1 or claim 2,
A permanent magnet type motor having a structure in which a permanent magnet whose radial length is longer than a circumferential length is embedded in the rotor core. In claim 1 or claim 2,
The permanent magnet has a rectangular cross-sectional shape, and the radial length is longer than the circumferential length,
The magnetization direction of the permanent magnet is such that the facing surfaces of adjacent permanent magnets are the same poles,
The rotor core is interposed between adjacent permanent magnets, the surface of the rotor core facing the stator side has a curved surface portion, and the shape of the curved surface is the intermediate point between adjacent permanent magnets. A convex curved surface is formed to shorten the gap length with the stator.
A non-magnetic portion is provided so as to be in contact with the end face on the inner diameter side of the permanent magnet.   The rotor according to claim 10, further comprising a shaft provided inside the rotor core, wherein the rotor core is formed between the first rotor core and the shaft between adjacent permanent magnets. A permanent magnet type motor comprising: the second rotor core provided on the outside; and a connecting portion provided between the first rotor core and the second rotor core. . In claim 1 or claim 2,
A permanent magnet type motor having a structure in which M / 2 permanent magnets of the rotor are arranged in the circumferential direction with respect to the number of poles M of the rotor. In claim 12,
The rotor core has a structure in which a permanent magnet whose radial length is longer than the circumferential length is embedded, and has a nonmagnetic portion on the inner diameter side of the permanent magnet, and the magnetization direction on the opposing surface A permanent magnet type motor characterized by having a nonmagnetic part between adjacent permanent magnets in the direction in which the poles are opposite to each other. In claim 1 or claim 2,
The stator has a configuration in which the armature winding is a distributed winding, and the number of slots per phase per pole is an even number of 2 or more. In any one of Claims 1-14,
A permanent magnet type motor characterized by being arranged in a direction parallel to a moving direction of a rack shaft of an electric power steering device.

Images