JP2015053756A - Reluctance motor - Google Patents

Abstract

PROBLEM TO BE SOLVED: To realize a high efficient, small-sized and low cost reluctance motor.SOLUTION: A reluctance motor includes: stator magnetic poles 111 and 11D of an A phase, stator magnetic poles 114 and 11G of an A/phase, stator magnetic poles 117 and 11K of a B phase, stator magnetic poles 11A and 11P of a B/phase; and two or more magnetically irregular-shaped characteristic rotor magnetic poles having a width of 90° or more at an electric angle in the circumferential direction. Thereby, the reluctance motor is constituted so that the drive width in which the stator magnetic pole of each phase can generate a torque becomes 90° or more at an electric angle and the continuous torque can be generated in a one-way rotation direction.

Description

  In recent years, energy problems and the like have become apparent, and the efficiency of air conditioners has been increased, and the spread and development of hybrid vehicles and electric vehicles using motors have also been promoted. In addition, high efficiency regulations regarding industrial motors are attracting attention. The present invention relates to improvements in these motors and their drive technology. That is, the present invention relates to higher efficiency, smaller size, lower cost, and lower motor drive cost.

Permanent magnet type synchronous motors are often used as main motors for hybrid vehicles, high-precision, high-response motors for industrial machines, and motors for home appliances such as air conditioners. On the other hand, reluctance motors are being developed and commercialized. The features of the reluctance motor are low cost because it does not require expensive rare earth magnets, winding is simple because the winding is simple and concentrated winding, and winding space factor is increased, so winding There are advantages such that the resistance can be reduced, the length of the coil end in the axial direction of the rotor can be shortened, and the robust rotor configuration can reduce the size and cost by increasing the rotation speed.
FIG. 29 shows a switched reluctance motor having six stator magnetic poles and four rotor magnetic poles. 299 is a stator, and 29B is a rotor shaft. 29A is a salient pole magnetic pole of the rotor, which is 30 ° wide and is arranged at four equal intervals on the entire circumference. Reference numeral 291 denotes an A-phase stator magnetic pole which winds concentrated windings 297 and 298. 292 is also an A-phase stator magnetic pole, and 291 and 292 simultaneously excite the magnetic flux through the rotor. Reference numerals 293 and 294 denote B-phase stator magnetic poles, and reference numerals 295 and 296 denote C-phase stator magnetic poles each having windings for excitation. In order to rotate in the counterclockwise direction CCW from this rotational position, the B-phase stator magnetic poles 293 and 294 are excited to attract the salient pole magnetic poles of the rotor and generate torque. Next, the C-phase stator magnetic poles 295 and 296 are excited and rotated to CCW. Next, the A-phase stator magnetic poles 291 and 292 are excited and rotated to CCW. By sequentially exciting the stator magnetic poles in this way, continuous rotational torque can be generated.
However, in the switched reluctance motor of FIG. 29, the windings used are 1/3 of all windings over the entire rotation range, and the utilization factor of the windings is as low as 1/3. There is a problem that the winding resistance is substantially increased. There is a problem in that vibration and noise are increased because the excitation current is turned on and off, the magnetic flux increases and decreases rapidly, and the stator and rotor are rapidly distorted. Since an excitation current for inducing the magnetic flux of the motor is required, there is a problem that the torque in a small current region is small and the efficiency is low in that region.
FIG. 29 shows an example of a three-phase reluctance motor, but there are also a single-phase reluctance motor and a two-phase reluctance motor. Patent Document 2 shows an example of a single-phase and two-phase reluctance motor having an annular winding. The motor configuration is simple, easy to manufacture, and the utilization factor for utilizing each part of the motor for driving can be increased. However, it is difficult to obtain a continuous torque in these single-phase and two-phase, and the size of the air gap between the stator magnetic pole and the rotor magnetic pole is devised by partial deformation of the rotor magnetic pole. . As a result, there are problems such as increased torque ripple.

JP2013-150492A (FIG. 2) Re-published patent WO2006 / 123659 (FIGS. 6 and 7)

Problems to be solved by the first aspect of the present invention are to increase the rotation angle width at which each stator magnetic pole generates torque and to reduce torque ripple.
The problem to be solved by claim 2 is to improve the torque and reduce the torque ripple of the motor of claim 1.
The problems to be solved by the third aspect are improvement of the winding structure of the motor of the first aspect, higher efficiency, simplification of the drive inverter, and lower cost.
Problems to be solved by claim 4 are improvement of the winding structure of the motor of claim 1, high efficiency, simplification of the drive inverter, and cost reduction.
The problem to be solved by claim 5 is the realization of the simple motor configuration of claim 1.
The problem to be solved by claim 6 is to improve the torque and reduce the torque ripple of the motor of claim 1.
The problem to be solved by claim 7 is to improve the method of manufacturing the rotor of the motor of claim 1 and to reduce noise.
The problem to be solved by claim 8 is to increase the amount of magnetic flux passing through the teeth of the motor of claim 1.
The problem to be solved by claim 9 is to reduce the load of the excitation current of the motor of claim 1.
The problem to be solved by claim 10 is to modify the form of the motor of claim 1 and to configure it by an annular winding and a claw pole-shaped magnetic path, thereby simplifying and reducing the cost.

According to the first aspect of the present invention, there is provided an A-phase stator pole, an A / phase stator pole having a phase difference of 180 ° with respect to the A phase, and a B-phase stator having a phase difference of 90 ° with respect to the A phase. A unit over the entire length in the rotor axial direction of the magnetic pole, the B / phase stator magnetic pole having a phase difference of 270 ° from the A phase, the winding for exciting each stator magnetic pole, and the unit angular width in the circumferential direction of the rotor A first rotating part having a large magnetic resistance average value R1R in the radial direction with respect to the area, a second rotating part arranged in the circumferential direction of the rotor, and a third rotating part arranged in the circumferential direction of the rotor The radial direction permeance (1 / magnetic resistance average value R2R) of the unit area over the entire length in the rotor axis direction of the unit angular width in the circumferential direction of the second rotating unit is the third rotating unit. The unit over the entire length in the rotor axial direction of the unit angular width in the circumferential direction The radial permeance (1 / magnetic resistance average value R3R) of the product is 15% to 85%, and the first rotating unit, the second rotating unit, and the third rotating unit are set to 2 It is the structure of the reluctance motor provided with a set or more.
According to this configuration, it is possible to increase the rotation angle width at which each stator magnetic pole generates torque and reduce torque ripple.

According to a second aspect of the present invention, in the first aspect, the rotor includes six or more rotor magnetic poles including the first rotating portion, the third rotating portion, and the like, the A-phase stator magnetic pole, and the A / This is a configuration of a reluctance motor including a total of eight stator magnetic poles, each of two phase stator magnetic poles, two B-phase stator magnetic poles, and two B / phase stator magnetic poles.
According to this configuration, the torque of the motor of claim 1 can be improved and the torque ripple can be reduced.

According to a third aspect of the present invention, in the first aspect, the current component for exciting the A-phase stator magnetic pole is denoted by Ia, and the current component for exciting the B-phase stator magnetic pole is denoted by Ib. A winding for energizing the current Ij is wound around the slot of (Ia + Ib), a winding for energizing the current Ik is wound around the slot of (Ia-Ib) for energizing the slot, and the current to be energized for the slot is ( 2 × Ia) is wound with a winding for passing the current Im to the slot,
Winding a coil for energizing the current In to the slot of the current to be energized in the slot (2 × Ib), and when the sign of the current to be energized is opposite, the winding is reversed. It is the structure of the reluctance motor which winds a wire.
According to this configuration, it is possible to improve the winding structure of the motor according to claim 1, to improve the efficiency, to simplify the drive inverter, and to reduce the cost.

The invention described in claim 4 is the coil according to claim 3, wherein the winding for passing the current Im is formed by winding a winding for passing the current Ij into the slot and a winding for passing the current Ik. The winding for energizing the current In is a reluctance motor configured by winding a winding for energizing the current Ij and a winding for energizing the current (−Ik).
According to this configuration, it is possible to improve the winding structure of the motor according to claim 1, to improve the efficiency, to simplify the drive inverter, and to reduce the cost.

According to a fifth aspect of the present invention, in the first aspect, the number of stator magnetic poles is four, ie, A phase, A / phase, B phase, and B / phase, and the first rotating portion, the second rotating portion, and the It is the structure of the reluctance motor provided with 2 sets of 3rd rotation parts.
According to this configuration, a simple motor configuration according to claim 1 can be realized.

A sixth aspect of the present invention is the method according to the first aspect, further comprising a fourth rotating portion between the second rotating portion and the third rotating portion in a circumferential direction. The radial permeance (1 / magnetic resistance average value R4R) of the unit area over the entire length in the rotor axis direction of the unit angular width in the circumferential direction is the permeance of the third rotating part (1 / magnetic resistance average value R3R). The reluctance motor has a value of 30% to 85%.
According to this configuration, it is possible to improve the torque of the motor of claim 1 and reduce the torque ripple.

The invention according to claim 7 is the magnetoresistive average value R1R of the first rotating unit, the magnetoresistive average value R2R of the second rotating unit, and the magnetoresistive average of the third rotating unit according to the first aspect. This is a reluctance motor in which the value R3R is made to have a substantially equivalent magnetic resistance ratio by a plurality of holes and grooves formed in the electromagnetic steel sheet, and the electromagnetic steel sheets are laminated in the rotor axial direction.
According to this configuration, it is possible to improve the method for manufacturing the rotor of the motor according to claim 1 and reduce noise.

According to an eighth aspect of the present invention, in the first aspect, in the two stator magnetic poles arranged side by side in the circumferential direction, the magnetic flux direction during energization passing from the outer diameter side to the inner diameter side of the teeth is opposite. This is a configuration of a reluctance motor including a permanent magnet having a polarity for supplying a magnetic flux in which the magnetic flux directions are opposite to each other in the vicinity of the tips of two stator magnetic pole teeth.
According to this configuration, the amount of magnetic flux that passes through the teeth of the motor according to claim 1 can be increased.

A ninth aspect of the present invention is the configuration of the reluctance motor according to the first aspect, wherein the reluctance motor includes a permanent magnet disposed on the motor back yoke and having a polarity facing the magnetic flux direction of each stator magnetic pole.
According to this configuration, the burden of the excitation current of the motor according to claim 1 can be reduced.

A tenth aspect of the present invention is the first aspect, wherein the two or more A-phase stator magnetic poles, the two or more A / phase stator magnetic poles arranged in a claw pole shape, and the A-phase stator magnetic poles, An annular winding for passing a current for exciting magnetic flux passing through both stator poles, two or more B-phase stator poles, arranged so as to intersect the phase stator poles and the A / phase stator poles,
The B-phase stator poles are two or more B / phase stator poles arranged in a claw pole shape,
An annular winding that is arranged so as to intersect the B-phase stator magnetic pole and the B / phase stator magnetic pole and energizes a current that excites magnetic flux passing through both stator magnetic poles, the A-phase stator magnetic pole, and the A A rotor part RAA in which the / phase stator magnetic poles act electromagnetically; and a rotor part RBB in which the B phase stator magnetic poles and the B / phase stator magnetic poles act electromagnetically; The rotor portion RBB is a reluctance motor that is mechanically coupled to each other and arranges each stator magnetic pole at a position where the magnetic flux passing through the A-phase stator magnetic pole and the magnetic flux passing through the B-phase stator magnetic pole are separated.
According to this configuration, the form of the motor according to claim 1 can be modified and configured by an annular winding and a claw pole-shaped magnetic path, whereby simplification and cost reduction can be achieved.

  The reluctance motor of the present invention is a reluctance motor having a simple configuration constituted by stator magnetic poles of A phase, A / phase, B phase, B / phase, etc., but each stator magnetic pole is driven by adopting a novel rotor structure. The possible rotation angle width is widened, and continuous torque with less torque ripple can be realized. Noise can also be reduced. In addition, by improving the stator arrangement structure, the magnetic path space and winding space of each tooth are secured, enabling a large magnetic flux density and a large current flow, and a high torque and high efficiency of the reluctance motor. . In addition, by improving the winding configuration method and energization method, it is possible to reduce copper loss, improve the manufacturability of the motor, and reduce the size and cost of the drive inverter. In addition, an increase in the amount of magnetic flux that can pass through each tooth of the stator and a reduction in the excitation burden of each stator magnetic pole can be realized by adding a permanent magnet, and the reluctance motor can be reduced in size and cost.

motor Development Voltage, current, torque characteristics Driving circuit motor Development Voltage, current, torque characteristics motor motor motor motor motor motor combination motor motor motor motor Driving circuit Driving circuit Driving circuit Development Voltage, current, torque characteristics Development Voltage, current, torque characteristics Rotor Stator motor Conventional motor

  An object of the present invention is to obtain a reluctance motor that is simple, highly efficient, small, and low in cost. If it is not low-cost as a motor system including the drive circuit of a reluctance motor, it is meaningless, and it evaluates as a reluctance motor including the drive method from that viewpoint. The present invention relates to a reluctance motor having a configuration that prioritizes torque in one direction.

  FIG. 1 shows an example of a reluctance motor of the present invention. 13 is a stator, and 14 is a rotor shaft. Reference numerals 15 and 16 denote rotor magnetic poles, which use a soft magnetic material, and have a characteristic that the magnetic resistance of the rotor surface has different values in the circumferential direction. An example in which the circumferential width 12 is 120 ° will be described later with reference to FIG.

  Reference numeral 17 denotes an A-phase stator magnetic pole. Reference numeral 18 denotes an A / phase stator magnetic pole, which has a reverse phase relationship with the A phase. The stator pole width 11 of 17 and 18 is an example of 60 °. Reference numerals 1B and 1C are A-phase windings for exciting the A-phase stator magnetic pole 17, and a current is supplied in the direction of the current symbol shown in the figure. Reference numerals 1E and 1F denote A / phase windings for exciting the A / phase stator magnetic pole 18, and a current is supplied in the direction of the current symbol shown in the figure. Each winding is concentrated around each stator pole, as indicated by the 1D and 1G broken lines. Both stator poles 17 and 18 are energized at the same time, and the excitation magnetic flux passes through the A / phase stator pole 18, passes through the rotor poles 16 and 15, passes through the A / phase stator pole 17 and goes through the stator back yoke.

  Reference numeral 19 denotes a B-phase stator magnetic pole. Reference numeral 1A denotes a B / phase stator magnetic pole, which has a reverse phase relationship with the B phase. The stator magnetic pole widths of 19 and 1A are the same as those of the A phase and the A / phase, and are 60 degrees. Reference numerals 1J and 1H denote B-phase windings for exciting the B-phase stator magnetic poles 19, and energize currents in the direction of the current symbols shown. 1M and 1L are B / phase windings that excite the B / phase stator magnetic pole 1A, and energize the current in the direction of the current symbol shown. Each winding is concentrated around each stator pole, as indicated by the 1K and 1N broken lines. Both the stator poles 19 and 1A are excited at the same time, and the excitation magnetic flux passes through the B / phase stator pole 1A, passes through the rotor poles 16 and 15, passes through the B / phase stator pole 19 and goes through the stator back yoke.

  Next, the operation of the motor of FIG. 1 will be described with reference to the development view of FIG. FIG. 2 is a diagram showing the opposing shapes of the air gap surfaces between the stator and the rotor of FIG. The horizontal axis in FIG. 2 represents the rotation angle θr in the circumferential direction of the counterclockwise rotation direction CCW in FIG. 1, and the vertical axis represents the rotor axial direction. The rotation angle position of 0 ° of the circumferential rotation angle θr is the clockwise end of the A-phase stator pole 17 in FIG. 2A is a diagram in which the shape of the inner peripheral surface of the stator of FIG. 1 is developed horizontally, and 21 is the shape of the surface of the A-phase stator magnetic pole 17 facing the rotor. Similarly, reference numeral 22 denotes a B-phase stator magnetic pole 19, 23 denotes an A / phase stator magnetic pole 18, and 23 denotes a shape of a surface facing each rotor of the B / phase stator magnetic pole 1 </ b> A. Each stator magnetic pole has a circumferential width of 60 ° and a period of 90 °.

  Note that the reluctance motor of the present invention obtains the rotational torque by utilizing the circumferential change of the reluctance (magnetic resistance) between the stator and the rotor. This is an idea that the stator magnetic pole and the rotor magnetic pole face each other, and the facing area of both of them that facilitates passage of magnetic flux is proportional to permeance (1 / magnetic resistance) that is easy to pass magnetic flux. The product of the time change rate dφdt of the magnetic flux φ passing through the winding and the number of turns of the winding is the winding voltage, and the product of the energized current and the voltage is the input power. If the loss in the motor is ignored, the output power of the motor is the product of the torque and the rotational angular frequency (rotational speed), so the torque is calculated if the voltage and current are determined.

  FIG. 2B shows the shape of the surface of the rotor magnetic poles 15 and 16 facing the stator. Reference numeral 25 denotes the shape of the surface of the rotor magnetic pole 15 facing the stator, which is the same as 27 indicated by a broken line described at a position where the 360 ° phase is different. Reference numeral 26 denotes a shape of the surface of the rotor magnetic pole 16 facing the stator, and 25 is a phase difference of 180 °. The counterclockwise rotation direction CCW of the rotor magnetic poles 16 and 16 in FIG. 1 is the direction from left to right on the paper surface of FIG. The rotational angle position of the rotor 25 shown in FIG. 2A is different from the rotational angle position of the rotor 15 shown in FIG. 1, and the counterclockwise direction end of the rotor 15 is the rotor rotational angle θr = 0 °. This is the rotation angle position approaching. The rotation angle position θr of the rotor magnetic pole 15 will be described by defining the end of the rotor magnetic pole 15 in the counterclockwise rotation direction as 0 °. In addition, the direction of the torque acting on the rotor is given priority to the torque generated in the counterclockwise rotation direction CCW, and has a shape convenient for generating the CCW torque. The torque in the clockwise rotation direction CW becomes discontinuous torque depending on the rotor rotation angle position θr.

  The rotor position θr, which is the right end of the rotor magnetic pole 25 shown in FIG. 2B, is in the vicinity of 0 °, the A-phase current Ia is supplied to the A-phase windings 17 and 18, and the A / phase windings 1E and 1F are supplied. By energizing the A / phase current -Ia, a magnetic attraction force is generated, and a CCW torque is generated in FIG. 1 and a rightward torque T2 is generated on the paper surface of FIG. The same torque T2 can be generated when the rotor position θr is from 0 ° to 60 °. Here, at the position where the rotor position θr is 60 °, that is, the rotational position of the rotor magnetic pole 25 of FIG. 2C, the rotor axial width W2 of the portion of the rotor magnetic pole 25 facing the stator magnetic pole 21 is small. It is set to 1/2 of the rotor axial width W3 of the other part. The magnitude of the generated torque is a value related to the rotational change rate d (SSR) / dθr of the area SSR where the rotor magnetic pole 25 faces the stator magnetic pole 21 and the A-phase current Ia. The relational expression of torque is not a simple proportional relation due to the influence of the three-dimensional leakage magnetic flux between the stator and the rotor, the magnitude of magnetic energy, the nonlinearity of the magnetic material, etc. It is assumed that it is roughly proportional to

  FIG. 2C shows a state in which the rotor position θr of the rotor magnetic pole 25 is 60 °. In this state, since the rotor axial width of the portion of the rotor magnetic pole 25 that faces the stator magnetic pole 21 changes from W2 to W3, the width difference (W3-W2) = W2. The torque T3 is the same as the torque T2 when the rotor rotational position θr is between 0 ° and 60 °. This relationship is maintained over the rotor rotational position θr between 60 ° and 120 °, and the torque T3 is generated.

  FIG. 2D shows a state where the rotor rotational position θr = 90 ° of the rotor magnetic pole 25. As described above, torque T3 = T2 is generated. In this motor, the circumferential width of the stator magnetic pole 21 is 60 °, and while being 60 °, the stator magnetic pole 21 can be excited to generate torque for 90 ° or more, and each stator magnetic pole can be excited alternately. This means that a continuous torque can be generated over the entire circumference, and from this point of view, the angle is the boundary of the driving conditions.

  At the rotor rotational position θr = 90 ° of the rotor magnetic pole 25, the B-phase stator magnetic pole 19 and the B / phase stator magnetic pole 1A are also at the rotor rotational position θr at which the CCW torque T2 can be generated by the B-phase excitation current Ib. . The rotor rotational position θr from 90 ° to 120 ° is a section in which both the A phase, the A / phase and the B phase, and the B / phase can generate torque. Similarly, even when θr is between 0 ° and 30 °, θr is between 180 ° and 210 °, and θr is between 270 ° and 300 °, both A phase, A / phase and B phase, and B / phase are torque. Can be generated.

  FIG. 2E shows a state where the rotor position θr of the rotor magnetic pole 25 is 120 °. CCW torque can be generated up to this angle. Conversely, when the rotor rotational position θr exceeds 120 ° with the A-phase current Ia being applied, CW torque is generated. Therefore, in order to control so that CW torque is not generated, it is necessary to reduce the A-phase current Ia to zero before the rotor rotational position θr exceeds 120 °.

  The B phase stator magnetic pole 19 and the B / phase stator magnetic poles 1 and 22 and 24 are also 90 ° behind the A phase and the A / phase, and the CCW torque T2 can be generated by the B phase excitation current Ib. it can. Therefore, the CCW torque T2 can be generated over the entire circumference by alternately driving.

  FIG. 3 is an example of voltage characteristics, current characteristics, and torque characteristics during the motor operation described in FIG. 3A and 3C, the horizontal axis is the rotor rotation angle, and the vertical axis is the induced voltage. 3B and 3D, the horizontal axis is the rotor rotation angle, and the vertical axis is the current. The horizontal axis in FIG. 3E is the rotor rotation angle, and the vertical axis is the torque. FIG. 3A shows an example of the induced voltage of the A-phase winding when the A-phase current Ia is supplied with a constant value when the rotor rotational position θr is between 0 ° and 120 ° and between 180 ° and 300 °. It is. This is a value related to the rotational change rate d (SSR) / dθr of the area SSR and the A-phase current Ia. The negative voltage shown in FIG. 3A is a negative voltage generated as a phenomenon of regenerating the magnetic energy of the motor when the A-phase current is reduced. Note that the shape of the negative voltage varies greatly depending on the current reduction method, the rotational speed, and the like. FIG. 3C shows a constant B-phase current Ib when the rotor rotational position θr is between 90 ° and 210 ° and between 270 ° and 390 °, that is, 30 °, as in FIG. It is an example of the induced voltage of the B-phase winding when energized.

  FIG. 3B shows an example of energization of the A-phase current Ia. During this period, torque having a shape substantially similar to the A-phase current Ia is generated. FIG. 3D shows an example of energizing the B-phase current Ib. During this period, torque having a shape substantially similar to the B-phase current Ib is generated. In FIGS. 3B and 3D, energization is performed so that the A-phase current Ia and the B-phase current Ib flow just alternately. (E) in FIG. 3 is a value obtained by adding the A-phase torque and the B-phase torque, and indicates that a uniform motor torque can be generated. As a result, a method for generating a one-way continuous torque by using four A-phase stator poles 17, A / phase stator poles 18, B-phase stator poles 19, B / phase stator poles of 60 ° less than 90 ° is shown. It was. In principle, high-quality rotational torque without torque ripple can be obtained.

  FIG. 4 shows an example of an inverter that supplies the A-phase current Ia and the B-phase current Ib. Since it is a reluctance motor, both currents can be driven by a one-way current. 3X is a motor control device, 37 is a DC voltage source, T1, T2, T3, and T4 are power control elements for energizing a current Ia, which are switching elements such as power MOSFETs and IGBTs. By turning on T1 and T2, the current Ia flowing to the winding 41 is increased, and by turning it off, energy is regenerated to the DC voltage source 37 by two diodes in opposite directions. The windings 41 are the A-phase windings 1B and 1C and the A / phase windings 1E and 1F in FIG. By turning on T3 and T4, the current Ia flowing to the winding 42 is increased, and by turning it off, energy is regenerated to the DC voltage source 37 by two diodes in opposite directions. The winding 42 is the B phase winding 1J, 1H, B / phase winding 1M, 1L of FIG. It can be driven with a simple circuit.

  Next, an example in which the circumferential width of the stator magnetic pole is increased in order to improve the torque generated by the reluctance motor of FIG. 1 is shown in FIG. The motor of FIG. 1 can obtain a continuous torque without torque ripple. However, as shown in FIG. 2, the rotor axial width of the rotor magnetic pole is ½ of the total length in the magnitude of the torque. The rotational change rate dφa / dθr of the magnetic flux φa interlinked with the winding and the rotational change rate dφb / dθr of the magnetic flux φb interlinked with the B-phase winding are halved in the entire region, and FIGS. ) Is ½. The torque of the rotor magnetic pole is ½ compared to the motor whose rotor axial width is the length of the entire length. In the motor of FIG. 5, the average torque is improved by increasing the circumferential width 51 of the stator magnetic pole to 75 °. That is, while satisfying the condition that the torque is continuously generated in the entire rotation range, the rotational change rates dφa / dθr and dφb / dθr of the magnetic flux are improved and the torque is increased in a part of the rotation angle region of the rotor rotation angle θr. Plan.

  The circumferential magnetic pole width 52 of the rotor magnetic pole is 105 °. Reference numeral 57 denotes an A-phase stator magnetic pole. Reference numeral 58 denotes an A / phase stator magnetic pole, which has a reverse phase relationship with the A phase. The stator pole width 51 of 57 and 58 is 75 °. 5B and 5C are A-phase windings that excite the A-phase stator magnetic pole 57, and energize the current in the direction of the current symbol shown in the figure. 5E and 5F are A / phase windings that excite the A / phase stator magnetic pole 58, and energize the current in the direction of the current symbol shown in the figure. Each winding is concentrated around each stator pole as indicated by 5D and 5G broken lines. Both stator poles 57 and 58 are excited at the same time, and the excitation magnetic flux passes through the A / phase stator pole 58, passes through the rotor poles 56 and 55, passes through the A / phase stator pole 57, and goes through the stator back yoke.

  Reference numeral 59 denotes a B-phase stator magnetic pole. Reference numeral 5A denotes a B / phase stator magnetic pole, which has a reverse phase relationship with the B phase. The stator magnetic pole widths of 59 and 5A are the same as those of the B phase and the B / phase, and are 75 °. 5J and 5H are B-phase windings that excite the B-phase stator magnetic pole 59, and energize the current in the direction of the current symbol shown in the figure. 5M and 5L are B / phase windings that excite the B / phase stator magnetic pole 5A, and energize the current in the direction of the current symbol shown. Each winding is concentrated around each stator pole as indicated by 5K and 5N broken lines. Both stator poles 59 and 5A are excited simultaneously, and the excitation magnetic flux goes through the B / phase stator magnetic pole 5A, passes through the rotor magnetic poles 56 and 55, passes through the B / phase stator magnetic pole 59, and goes through the stator back yoke.

  FIG. 6A is a diagram in which the shape of the inner peripheral surface of FIG. 5 is developed horizontally, and 61 is the shape of the surface of the A-phase stator magnetic pole 57 that faces the rotor. Similarly, 62 is a B-phase stator magnetic pole 59, 63 is an A / phase stator magnetic pole 58, 64 is a shape of the surface of the B / phase stator magnetic pole 5A facing the respective rotors. Each stator magnetic pole has a circumferential width of 75 ° and a period of 90 °.

  FIG. 6B shows the shape of the surface of the rotor magnetic poles 55 and 56 facing the stator. Reference numeral 65 denotes the shape of the surface of the rotor magnetic pole 55 facing the stator, which is the same as 67 indicated by a broken line described at a position where the 360 ° phase is different. Reference numeral 66 denotes the shape of the surface of the rotor magnetic pole 56 that faces the stator. The shape of 65 is the paper surface of FIG. 6, the rotation angle width RFF of the front end portion in the traveling direction is 15 °, and the rotor axial thickness of that portion is ½ of the axial thickness of the rotor. Between 15 ° to 105 ° on the right side of 65, the length in the rotor axial direction is the same as the axial thickness of the rotor core, that is, the total length. As shown in the figure, the shape has two steps.

  The rotor position θr that is the right end of the rotor magnetic pole 65 shown in FIG. 6B is in the vicinity of 0 °, the A-phase current Ia is supplied to the A-phase windings 57 and 58, and the A / phase windings 5E and 5F are supplied. By energizing the A / phase current −Ia, a magnetic attractive force is generated, and a CCW torque is generated in FIG. 5 and a rightward torque T2 is generated on the paper surface of FIG. The same torque T2 can be generated when the rotor position θr is 0 ° to 15 °. Here, at the position where the rotor position θr is 15 °, that is, the rotational position of the rotor magnetic pole 65 shown in FIG. 6C, the rotor axial width W2 of the portion of the rotor magnetic pole 65 facing the stator magnetic pole 61 is small. It is set to 1/2 of the rotor axial width W3 of the other part.

  FIG. 6C shows a state where the rotor position θr of the rotor magnetic pole 65 is 15 °. In this state, the rotor axial width of the portion of the rotor magnetic pole 65 that faces the stator magnetic pole 61 is the rotational angle position where the width changes from W2 to W3, and the generated torque T3 is between the rotor rotational position θr of 15 ° and 75 °. The rotational change rate d (SSR) / dθr of the area SSR facing the stator magnetic pole 61 can take a theoretical maximum value.

  FIG. 6D shows a state where the rotor rotational position θr = 75 ° of the rotor magnetic pole 65. When θr is between 75 ° and 90 °, the rotational change rate d (SSR) / dθr of the facing area SSR is reduced to ½, so the generated torque is also halved.

  FIG. 6E shows a state where the rotor position θr of the rotor magnetic pole 65 is 90 °. CCW torque can be generated up to this angle. Even when the A-phase current Ia is applied, the facing area SSR does not change when the rotor rotational position θr is between 90 ° and 105 ° shown in FIG. dθr = 0, and no torque is generated. During this time, the A-phase current Ia can be reduced to zero.

  The B-phase stator magnetic pole 59 and the B / phase stator magnetic poles 5A and 62 and 64 are also 90 ° behind the A-phase and A / phase, and can generate CCW torque by the B-phase excitation current Ib. . Therefore, torque can be generated over the entire circumference by driving alternately.

  FIG. 7 is an example of voltage characteristics, current characteristics, and torque characteristics during the motor operation described in FIG. 7A and 7C, the horizontal axis is the rotor rotation angle, and the vertical axis is the induced voltage. In FIG. 7B and FIG. 7D, the horizontal axis is the rotor rotation angle, and the vertical axis is the current. In FIG. 7E, the horizontal axis is the rotor rotation angle, and the vertical axis is the torque. FIG. 7A shows an example of an induced voltage of the A-phase winding when the A-phase current Ia is supplied with a constant value when the rotor rotational position θr is between 0 ° and 90 ° and between 180 ° and 270 °. It is. This is a value related to the rotational change rate d (SSR) / dθr of the area SSR and the A-phase current Ia. The negative voltage shown in FIG. 7A is a negative voltage generated as a phenomenon of regenerating the magnetic energy of the motor when the A-phase current is reduced. Note that the shape of the negative voltage varies greatly depending on the current reduction method, the rotational speed, and the like. FIG. 7 (c) shows a case where the B-phase current Ib is energized with a constant value when the rotor rotational position θr is between 90 ° and 180 ° and between 270 ° and 360 °, as in FIG. 7 (a). It is an example of the induced voltage of a B phase winding.

  FIG. 7B is an energization example of the A-phase current Ia, and a torque having a shape substantially similar to the induced voltage of the A-phase winding is generated during this period. FIG. 7D shows an example of energization of the B-phase current Ib. During this period, torque having a shape substantially similar to the induced voltage of the B-phase winding is generated. In FIGS. 7B and 7D, energization is performed so that the A-phase current Ia and the B-phase current Ib flow just alternately. FIG. 7E shows a value obtained by adding the A-phase torque and the B-phase torque. Although this torque is pulsating, its average value is 1.66 times the torque average value shown in FIG. The motor efficiency is also improved, and the motor can be reduced in size and cost. Note that the inverter shown in FIG. 4 can be used as the drive inverter.

  In the motor characteristics shown in FIGS. 5, 6, and 7, the rotation angle width of the torque generated by the A-phase stator pole and the A / phase stator pole is 90 °, and the B-phase stator pole and the B / phase stator pole are The rotation angle width of the generated torque is 90 °. This motor model has a limit shape that can generate torques of both phases and generate continuous torque of multiple rotations. If single-phase torque cannot be generated over a rotation angle width of 90 ° or more, continuous torque with multiple rotations cannot be generated stably. The condition for generating a single-phase torque of 90 ° or more is that when the circumferential angle width of the stator magnetic pole is SSW and the rotation angle width of the front end of the rotor magnetic pole in the paper surface of FIG. 6 is RFF, RFF> (90 ° -SSW). In FIG. 6, since the SSW is set to 75 ° in the circumferential direction of the stator magnetic pole, if the rotation angle width RFF at the front end of the rotor magnetic pole is 15 ° or more, for example, 20 °, one phase The rotation angle width at which the stator magnetic pole suppresses the torque is 95 °, and the margin for generating continuous torque is 5 °.

  Further, if the length in the rotor axial direction at the front end portion of the rotor magnetic pole is 15% or more and 85% or less of the rotor stacking thickness, it can be started by the initial attraction torque by the stator magnetic pole, while the motor The continuous torque can be maintained.

  Next, the Example concerning Claim 2 is shown. FIG. 8 shows an example of a motor in which the motor of FIG. 1 or the motor of FIG. 81, 85, and 86 are A-phase stator magnetic poles. Reference numerals 83, 87, and 8B denote A / phase stator magnetic poles, which have a reverse phase relationship with the A phase. 82, 86 and 8A are B-phase stator magnetic poles. Reference numerals 84, 88, and 8Ch denote B / phase stator magnetic poles, which have a reverse phase relationship with the B phase. Concentrated windings 8F and 8G are wound around the A-phase stator magnetic pole 81, and an A-phase current Ia is energized to be excited. Concentrated windings 8M and 8K are wound around the A / phase stator magnetic pole 83, and an A-phase current Ia is energized to be excited. Concentrated windings 8H and 8J are wound around the B-phase stator magnetic pole 82, and the B-phase current Ib is energized to be excited. Concentrated windings 8P and 8N are wound around the B / phase stator magnetic pole 84, and a B-phase current Ib is energized to be excited.

  The remaining 2/3 of FIG. 8 is the same as the above configuration. The operation of the motor of FIG. 8 is the same as that of the motor of FIG. 1 or FIG. However, since the number of poles is tripled, the rotational speed of the rotor is 1/3.

  Here, the motors of FIGS. 1, 5, and 8 will be evaluated again. These motors are characterized by a simple configuration, but there is a trade-off between the magnetic path formed by the teeth on the stator side and the slot around which each phase winding is wound. There is a problem of being related. Specifically, in the motor of FIG. 1, the axial width of the rotor is set to ½ of the total axial width, which is the thickness of the core on which the electromagnetic steel plates are laminated. Therefore, assuming that the magnetic flux passing through the stator magnetic pole is φ, the rotational change rate dφ / dθr of the magnetic flux φ is ½, and the torque is also ½. In the motor of FIG. 5, the angle of the circumferential width of the stator is expanded to 75 ° so that more magnetic flux φ is obtained. However, the windings 5B, 5C, 5E, 5F, 5J, 5H, 5M, and 5L Space is getting smaller. Although the slot shape shown in FIG. 5 is triangular, it seems to have a certain amount of space. However, since the motor is designed with multiple poles, the slot cross-sectional area becomes small. FIG. 8 shows a diagram in which the width in the circumferential direction of each tooth is reduced to 60% of the pitch of each tooth in order to secure the slot cross-sectional area because it is multipolarized three times. In this case, the magnetic flux density of the rotor must be reduced to 60% for designing. Since the rotational change rate dφ / dθr of the magnetic flux φ decreases, there is a problem that the torque also decreases.

  FIG. 9 shows an example of a motor that alleviates this problem. The motor of FIG. 9 eliminates the B-phase stator pole 82, the A-phase stator pole 85, the B / phase stator pole 88, the A / phase stator pole 8B, and their windings indicated by broken lines in FIG. The space is redistributed by the remaining stator poles and their windings. However, the surface of each remaining stator magnetic pole facing the rotor and the circumferential position in the vicinity thereof are not changed and are set to the same circumferential position as in FIG.

  The motor shown in FIG. 9 has eight stator magnetic poles, which is 2/3. However, since the motors are arranged in a well-balanced manner, similar characteristics can be obtained as a whole motor. In particular, since the circumferential width of each stator magnetic pole can be sufficiently secured, the problem of magnetic saturation is greatly improved, and a motor having a large peak torque can be designed. This is an important characteristic for applications that require a peak torque about three times the continuous rated torque. Of course, the rotational change rate dφ / dθr of the magnetic flux φ acting on each winding can be set to the theoretical maximum value. Since the slot cross-sectional area can be increased, so-called copper loss, which is Joule heat, can be reduced. However, when compared with a motor composed of eight stator magnetic poles and four rotor magnetic poles, the motors of FIGS. 1 and 5 are doubled in number, the motor driving frequency is 1.5 times larger, which is due to the increase in frequency. The increase in iron loss must be taken into account. However, if the number of rotations used is low, the problem of iron loss is small, and there is a method of using a soft magnetic material with low iron loss.

  In FIG. 9, the A-phase stator poles are 91 and 9G, the A / phase stator poles are 94 and 9D, the B-phase stator poles are 9A and 9K, and the B / phase stator poles are 97 and 9P. The A-phase stator magnetic pole 91 is excited by an A-phase current Ia energized in the windings 92 and 93 wound in a concentrated winding. The windings of the other A-phase stator pole 9G are 9H and 9J, and the same. Both the A phase and the A / phase are excited by the A phase current Ia. The A / phase stator pole 94 is excited by a negative A-phase current -Ia that is energized to the windings 95 and 96 wound in a concentrated winding. The windings of the other A / phase stator pole 9D are the same for 9E and 9F. The B-phase stator magnetic pole 9A is excited by a B-phase current Ib energized through the windings 9B and 9C wound in a concentrated winding. The windings of the other B-phase stator pole 9K are 9M and 9N, and the same. The B / phase stator magnetic pole 97 is excited by a negative B-phase current −Ib that is energized to the windings 98 and 99 wound in the concentrated winding. The windings of the other B / phase stator pole 9P are 9Q and 9R, and the same. Both the B phase and the B / phase are excited by the B phase current Ib.

  The portion of each phase stator magnetic pole in FIG. 9 facing the rotor is the same as the position of the corresponding stator magnetic pole in FIG. 8 and both rotors are the same, so both motors can be driven with the same algorithm. That is, the driving method shown in FIGS. 1 to 7 can be applied to the motor shown in FIG. In the motor of FIG. 9, as described above, the space per stator magnetic pole is increased to 12/8 = 1.5 times that of the motor of FIG. Wide. It is possible to pass the magnetic flux passing through the soft magnetic body of the rotor about 1.5 times or more. As a result, the rotational change rate dφ / dθr of the magnetic flux φ passing through the stator magnetic pole is about 1.5 times in proportion to the magnetic flux. The induced voltage constant and the torque constant of the motor are the product of the rotation change rate dφ / dθr of the magnetic flux φ and the number of turns, which means that the motor characteristics are improved. The number of windings wound in each slot is increased by a factor of 1.5, but the number of windings is 8/12, and the total is not different from 1.5 × 8/12 = 1. However, since the number of slots is reduced, winding becomes easier and an improvement in the winding space factor can be expected, and the amount of winding is substantially increased by reducing the insulating paper and improving the winding space factor. be able to.

  As a result, the motor of FIG. 9 can be highly efficient, and can be reduced in size and cost. In addition, since the magnetic saturation of each stator magnetic pole can be reduced, it is easy to ensure peak torque, and this is a great feature particularly in applications that require instantaneous large torque. Furthermore, the motor of FIG. 9 has a margin of space in the circumferential direction in the vicinity of the portion where each tooth faces the rotor, so the width of the tip of the tooth is widened, the position is shifted in the circumferential direction, etc. Therefore, there is room for improvement such as an increase in torque, a reduction in torque ripple, and a reduction in leakage magnetic flux between adjacent magnetic poles during energization.

  Next, FIG. 10 shows another embodiment of the second aspect. In this motor, the positions of the A / phase stator magnetic pole 9D and the A-phase stator magnetic pole 9G of the motor of FIG. 9 are exchanged, and the positions of the B-phase stator magnetic pole 9K and the B / phase stator magnetic pole 9P are exchanged. This is because the A-phase and A / phase are electromagnetic targets, and the B-phase and B / phase are also electromagnetic targets. ing. Since the interaction between the stator magnetic poles varies depending on the arrangement of the stator magnetic poles, even with a motor based on the same concept, it is possible to have a large difference in characteristics.

  The A phase stator poles of the motor of FIG. 10 are 101 and 10D, the A / phase stator poles are 104 and 10G, the B phase stator poles are 10A and 10P, and the B / phase stator poles are 107 and 10K. The A-phase stator magnetic pole 101 is excited by an A-phase current Ia energized in the windings 102 and 103 wound in a concentrated winding. The windings of another A-phase stator pole 10D are 10E and 10F, and the same. Both the A phase and the A / phase are excited by the A phase current Ia. The A / phase stator magnetic pole 104 is excited by a negative A-phase current −Ia that is energized to the windings 105 and 106 wound in a concentrated winding. The windings of the other A / phase stator pole 10G are the same for 10H and 10J. The B-phase stator magnetic pole 10A is excited by a B-phase current Ib energized in the windings 10B and 10C wound in the concentrated winding. The windings of the other B-phase stator magnetic pole 10P are 10Q and 10R, and the same. The B / phase stator magnetic pole 107 is excited by a negative B phase current −Ib that is energized to the windings 108 and 109 wound in the concentrated winding. The other B / phase stator pole 10K has a winding of 10M, 10N, and the same. Both the B phase and the B / phase are excited by the B phase current Ib.

The motor shown in FIG. 10 is characterized in that the two stator magnetic poles arranged in the circumferential direction have the same polarity. The polarity of the tip of the stator magnetic pole is determined from the current direction of the winding wound around the stator magnetic pole, the tip of the A phase stator magnetic pole and the B phase stator magnetic pole is the S pole, and the A / phase stator magnetic pole and the B / phase The tip of the stator magnetic pole is an N pole. Now, consider a method of exciting these stator magnetic poles with permanent magnets even when the currents Ia and Ib are zero. As shown in the motor of FIG. 10, since the A / phase stator magnetic pole 104 and the B / phase stator magnetic pole 107 having an electrical angle of about 90 ° are aligned with a phase difference of 90 °, the electrical angle has a width of 180 °. Becomes the N pole. On the other hand, on the rotor side, there is always one rotor magnetic pole between the electrical angles of 180 °. The relationship does not change even if the rotor rotates. Therefore, if the permanent magnets 10S and 10T having the N-polarity are arranged toward both the stator magnetic poles, it is possible to excite regardless of the rotor rotational position, and it is convenient because the magnetic flux of the permanent magnet is kept almost constant.

Similarly, the B-phase stator magnetic pole 10A and the A-phase stator magnetic pole 10D are arranged with a phase difference of 90 ° to form a 180 ° S pole. Therefore, the south poles of the permanent magnets 10T and 10U are arranged on the back yoke so as to face both the stator magnetic poles.
Similarly, the A / phase stator magnetic pole 10G and the B / phase stator magnetic pole 10X are arranged with a phase difference of 90 ° to form a 180 ° N pole. Accordingly, the N poles of the permanent magnets 10U and 10V are arranged on the back yoke so as to face both the stator magnetic poles.
Similarly, the B-phase stator magnetic pole 10P and the A-phase stator magnetic pole 101 are arranged with a phase difference of 90 ° to form a 180 ° S pole. Therefore, the south poles of the permanent magnets 10V and 10S are arranged on the back yoke so as to face both the stator magnetic poles.

  By arranging permanent magnets in this way, the excitation burden of the stator winding can be reduced, so that copper loss can be reduced, motor efficiency can be increased, and miniaturization can be achieved. In addition, since the attractive force by a permanent magnet acts so that it may balance to CCW and CW, a torque ripple is small.

  Further, the shape of the motor back yoke portion in which the permanent magnet 10S is arranged forms a thin magnetic path of a soft magnetic material on both side surfaces of the permanent magnet 10S. A part of the magnetic flux of the permanent magnet 10S forms a closed circuit through this soft magnetic part. The amount of magnetic flux that passes through the soft magnetic body is limited by the saturation characteristics of the soft magnetic body. In the case of constant output control of the motor up to high speed rotation, it is necessary to increase the amount of magnetic flux at low speed rotation and decrease the magnetic flux amount at high speed rotation. By forming a thin magnetic path of the soft magnetic material, the magnetic flux amount is reduced, and when high torque is required at low speed rotation, the winding current is increased to increase the magnetic flux of the stator magnetic pole. The amount can be increased. By having the soft magnetic body portion in this way, the structure is such that the excitation load of the motor current is reduced and constant output control is possible.

Next, FIG. 11 shows another embodiment of the second aspect.
The A phase stator poles of the motor of FIG. 10 are 111 and 11D, the A / phase stator poles are 114 and 11G, the B phase stator poles are 117 and 11K, and the B / phase stator poles are 11A and 11P. The A-phase stator magnetic pole 111 is excited by an A-phase current Ia energized in the windings 112 and 113 wound in concentrated winding. The windings of the other A-phase stator magnetic pole 11D are 11E and 11F, which are the same. Both the A phase and the A / phase are excited by the A phase current Ia. The A / phase stator pole 114 is excited by a negative A-phase current -Ia that is energized to the windings 115 and 116 wound in a concentrated winding. The windings of the other A / phase stator magnetic pole 11G are the same for 11H and 11J. The B-phase stator magnetic pole 117 is excited by a B-phase current Ib energized through the windings 118 and 119 wound in concentrated winding. The windings of the other B-phase stator magnetic pole 11K are 11M and 11N, and the same. The B / phase stator magnetic pole 11A is excited by a negative B-phase current -Ib that is energized to the windings 11B and 11C wound in a concentrated winding. The other B / phase stator pole 11P has windings 11Q and 11V, which are the same. Both the B phase and the B / phase are excited by the B phase current Ib.

  As described above as the aim of the present invention, it is desired to widen the circumferential width of the stator magnetic pole in order to widen the torque generation area of each stator magnetic pole and improve the average torque. For example, in the motor of FIG. 10, when the circumferential width of the stator magnetic poles 104 and 107 is increased, the tips of both stator magnetic poles approach each other, and when one stator magnetic pole is excited, a large leakage magnetic flux is generated in the other stator magnetic pole. It will be. This leakage magnetic flux promotes the magnetic saturation of the teeth, and there is a problem that the torque is reduced. In addition, the magnetic energy of the leakage magnetic flux is problematic as the number of revolutions increases and the reactive power increases. In addition, since there is a vacant space of 90 ° in electrical angle with 101 stator poles adjacent to 104, the leakage magnetic flux does not increase so much.

  In the motor of FIG. 11, in order to reduce the problem of this leakage magnetic flux, the N and S poles of the adjacent stator magnetic poles are arranged to have opposite polarities. And the permanent magnet is arrange | positioned in the direction of the polarity which reduces a leakage flux between adjacent stator magnetic poles. The permanent magnets 11S, 11T, 11U, and 11V in FIG. For example, since the A / phase stator magnetic pole 114 is N-pole, the 114 side of the magnet 11S is N-pole, and the B-phase stator magnetic pole 117, which is S-pole, faces the S-pole of the permanent magnet 11S.

  These permanent magnets have two major functions and effects. One of them is the action and effect of reducing the leakage magnetic flux. The other is an operation of passing a reverse magnetic flux through both stator magnetic poles and reverse-biasing the magnetic flux B and the magnetic field strength H of the soft magnetic material. This is an effect of increasing the amount of magnetic flux that passes from the rotor to the back yoke through the stator magnetic pole when exciting the stator magnetic pole. Since this motor is a reluctance motor, it has a configuration in which only one direction of magnetic flux acts on each tooth, but it can pass a maximum of twice as much magnetic flux by magnetically reverse-biasing it with a permanent magnet or the like. Become. As the characteristics and sizes of the permanent magnets 11S, 11T, 11U, and 11V in FIG. 11, appropriate values can be selected according to the characteristics required for the motor.

  With the arrangement of the stator magnetic poles and the permanent magnets 11S, 11T, 11U, and 11V between the teeth shown in FIG. 11, the peak torque can be particularly increased. It is suitable as a motor for applications that require peak torque. In addition, reactive power due to the magnetic energy of leakage flux can be reduced, which contributes to improvement in motor efficiency and downsizing of the inverter.

  Next, another embodiment of claim 2 is shown in FIG. In FIG. 12, the A phase stator poles are 121 and 124, the A / phase stator poles are 12D and 12G, the B phase stator poles are 127 and 12A, and the B / phase stator poles are 12K and 12P. The A-phase stator magnetic pole 121 is excited by an A-phase current Ia energized in the windings 122 and 123 wound in concentrated winding. The windings of the other A-phase stator pole 124 are 125 and 126, and the same. Both the A phase and the A / phase are excited by the A phase current Ia. The A / phase stator magnetic pole 12D is excited by a negative A-phase current -Ia energized in the windings 12E and 12F wound in the concentrated winding. The windings of the other A / phase stator pole 12G are the same for 12H and 12J. The B-phase stator magnetic pole 127 is excited by a B-phase current Ib energized through the windings 128 and 129 wound in concentrated winding. The windings of the other B-phase stator pole 12A are 12B and 12C, and the same. The B / phase stator magnetic pole 12K is excited by a negative B-phase current −Ib that is energized to the windings 12M and 12N wound in the concentrated winding. The windings of the other B / phase stator pole 12P are 12Q and 12R, and the same. Both the B phase and the B / phase are excited by the B phase current Ib.

  The motor configuration shown in FIG. 11 is characterized in that four slots are in this state in that two windings for supplying the same positive and negative currents are wound around the same slot. Specifically, the current −Ia is supplied to the winding 123 and the + Ia is supplied to the winding 125. Thus, in general, the two windings are not functioning and can be eliminated. Similarly, the current -Ib is energized in the winding 123, and + Ib is energized in the winding 12B. Winding 12F is energized with current + Ia, and winding 12H is energized with -Ia. Winding 12N is energized with current + Ia, and winding 12Q is energized with -Ib.

  FIG. 13 shows a configuration in which the eight windings in FIG. 11 are eliminated. The eight windings and their corresponding four slots are replaced with recesses 131, 132, 133, 134. The A phase current Ia is applied to the concentrated windings of the windings 122 and 126, the B phase current Ib is applied to the concentrated windings of the windings 128 and 12V, and the negative windings are applied to the concentrated windings of the windings 12E and 12U. A-phase current -Ia is applied, and negative B-phase current -Ib is applied to the concentrated windings of windings 12M and 12R. The depth and shape of the recess can be modified as appropriate. By eliminating these eight windings, the copper loss is halved, the winding cost is reduced, and the weight can be reduced. It can also be expressed that the motor can be made highly efficient and can be reduced in size and cost along with the increased efficiency.

  In the motors of FIGS. 11 and 13, the A-phase stator magnetic pole 121 is the S pole, and the B / phase stator magnetic pole 12P disposed adjacently is the N pole. it can. The same applies to the permanent magnet 12V between the B-phase stator pole 12A and the A / phase stator pole 12D. These permanent magnets can reduce the leakage magnetic flux between two adjacent stator magnetic poles. In addition, since a negative magnetic flux can be passed through each tooth by a permanent magnet, the amount of magnetic flux that passes when each tooth is excited and driven can be increased, and the circumferential width of the corresponding tooth. Can be reduced. This is effective when the motor shown in FIG. Since both the A-phase stator magnetic pole 124 and the B-phase stator magnetic pole 127 are S poles, no magnets can be added. Since both A / phase stator magnetic pole 12G and B / phase stator magnetic pole 12K are N poles, no magnets can be added.

  Further, in the motors of FIGS. 11 and 13, the A-phase stator magnetic poles 121 and 124 and the B-phase stator magnetic poles 127 and 12A are S poles, and the other four stator magnetic poles are N poles. Permanent magnets 12S and 12T having a polarity direction can be added. The four rotor magnetic poles 121, 124, 127, and 12A always have two rotor magnetic poles facing each other. These permanent magnets 12S and 12T can reduce the excitation current component energized in each winding, and the motor can be highly efficient, downsized, and reduced in cost.

  The windings 123 and 125 have currents flowing in opposite directions to cancel the electromagnetic action of the motor. However, in the vicinity of the air gap between the stator and the rotor, a space having a magnetic field strength H is provided. The distribution is greatly affected. Therefore, the motor of FIG. 12 and the motor of FIG. 13 are not completely equivalent. For example, when a large current is applied to 126 and winding 122, leakage magnetic flux is likely to be generated in the recess 131. Therefore, the motor shown in FIG. 13 can exhibit high-efficiency characteristics in applications where a large peak torque is not required, and can also be regarded as a small and low-cost motor.

  9, 10, 11, 12, and 13 show examples in which the arrangement relationship between the stator magnetic poles and their respective windings is changed. The combination of replacement of the stator magnetic poles is as shown in FIG. 14. 13 different arrangements are possible. 9 is combination 1, FIG. 10 is combination 4, FIG. 11 is combination 7, and FIGS. 12 and 13 are combination 9. FIG. The other motors in the order of arrangement of the stator magnetic poles, which are not shown as specific examples, have their respective characteristics.

  The configuration of these motors is that the two A-phase stator magnetic poles and the A-phase have an excitation phase difference of 180 °, and the spatial angle of the stator is an electrical angle of 0 ° or 180 °. The A / phase stator magnetic pole arranged at the position and the A phase are 90 ° excitation phase difference, and the stator is spatially located at the electrical angle 90 ° or 270 ° B from the A phase. The phase stator pole and the phase A have an excitation phase difference of 270 °, and in the space of the stator, the phase A is a B / phase stator pole disposed at a position of 90 ° or 270 ° of the electrical angle. The reluctance motor is provided with a rotor having eight rotor magnetic poles at equal intervals in the circumferential direction, each including two stator poles and a total of eight stator magnetic poles and windings for exciting the stator magnetic poles. These motors can be multi-polarized, and can be combined with various motors or modified.

  Next, a motor shown in FIG. 15 is shown and described as an embodiment of claim 3. In the motor of FIG. YK, for example, the current Ia is supplied to the winding 96 and the current −Ib is supplied to the winding 98, but both currents are not supplied simultaneously in most time zones. Therefore, by integrating the two windings of this slot into one winding, the thickness of the winding, that is, the cross-sectional area can be doubled, and the winding resistance in the slot, Copper loss can be reduced to ½. At this time, the energization current is equivalent if the current value is (Ia-Ib). Similarly, the windings 9C and 9E, the windings 9J and 9M, and the windings 9R and 92 can be expected to have the effect of integrating the windings.

These integrated winding currents can be replaced by the following equations (1) and (2), and can be expressed by currents Ij and Ik.
Ia + Ib = Ij (1)
Ia-Ib = Ik (2)

The sum of the currents flowing through the windings 93 and 95 in FIG. YK is −2 × Ia, the total current flowing through the windings 99 and 9B is 2 × Ib, and the total current flowing through the windings 9F and 9H is At 2 × Ia, the total current flowing through the windings 9N and 9Q is −2 × Ib. These integrated winding currents are replaced by the following formulas (3) and (4), and can be expressed by current Im and current In.
2 × Ia = Im (3)
2 × Ib = In (4)

The motor of FIG. 15 integrates the two windings of each slot of the motor of FIG. 9 and replaces them with new windings. The shape of each stator magnetic pole, the shape of each slot, and the shape of each winding are slightly modified. A current Ij is supplied to the winding 15G, a current Ik is supplied to the winding 15H,
Current -Ij is energized to winding 15J, and current -Ij is energized to winding 15K. Since the cross-sectional areas of these windings are doubled, the winding resistance and loss can be reduced.

  Current -Im is supplied to winding 152, current In is supplied to winding 153, current Im is supplied to winding 151, and current -In is supplied to winding 154. Although the cross-sectional area of these windings is doubled, the current is also doubled, so there is no loss reduction effect. However, in order to change the winding method of the other four windings, the winding structure of the windings 152, 153, 151, 154 must be changed.

  The motor connection and winding method of FIG. 15 must be wound in a slot on the opposite side of 180 ° as indicated by 155. The 15H winding is wound around the 15K winding. The same applies to the other windings. It is not preferable that the distance between the windings is long, which is a big problem such as a long coil end. As a method of reducing this problem, there is multipolarization. For example, if the number of poles is doubled, the length of the coil end can be reduced to ½. If the number of poles is tripled, the length of the coil end can be reduced to 1/3. As a specific motor design, a motor having a multipolar configuration is preferable.

  The winding integration technique shown in FIGS. 15 and (1), (2), (3), and (4) is similarly applied to the 13 types of motors shown in FIG. Can be applied. In particular, in an elongated type motor having a large rotor axial length, the winding resistance in the slot can be reduced, so that the effect of increasing the efficiency is great.

  Further, permanent magnets 152, 153, 154, 155 can be added to the motor of FIG. A permanent magnet is added to a portion where the gap between the two stator magnetic poles is as large as 90 ° in electrical angle. Compared with the example shown in FIG. 11, the effect of reducing leakage magnetic flux is small, but the same effect as the permanent magnets 11S, 11T, 11U, and 11V shown in FIG. Each tooth has a configuration in which only one direction of magnetic flux acts on each tooth. However, by magnetically reverse-biasing with a permanent magnet or the like, it is possible to pass a maximum of twice as much magnetic flux. In the case of the motor shown in FIG. 15, the space between the teeth is wide, and it is possible to create more reverse bias magnetic flux by devising the arrangement of the permanent magnets. The permanent magnets 152, 153, 154, and 155 shown in FIG. 15 can be applied to the motors shown in FIGS.

  Another embodiment of claim 3 is shown in FIG. The motor of FIG. 16 is an example in which the windings of FIG. 13 are integrated according to equations (1) and (2). Windings are wound around the winding 161 and the winding 163, and the current Ij is applied. Windings are wound around the windings 164 and 162, and the current Ik is applied. The operation of the motor is the same as that of FIG. The winding resistance in the slot is halved, the copper loss in the slot is halved, and high efficiency can be achieved. However, there is a problem that the length of the coil end becomes long, and the effect is great when applied to a motor having a large motor length. Alternatively, this problem can be reduced by reducing the coil end length by increasing the number of poles.

  Another embodiment of claim 3 is shown in FIG. The motor shown in FIG. 17 is a motor obtained by applying the winding integration shown in equations (1) and (2) to the motor shown in FIG. Windings 171 and 173 are wound and current Ij is applied. Windings 174 and 172 are wound and current Ik is applied. This motor is a motor having three times the number of poles, and the remaining 2/3 windings are similarly wound and energized. The winding resistance in the slot is halved, and the copper loss can be reduced to ½.

  As described in the description of the motor of FIG. 8, the motor of FIG. 17 has a short circumferential width of the teeth of the stator magnetic pole, and must reduce the magnetic flux acting on the stator magnetic pole. As a result, there is a problem that torque is reduced. In order to reduce this problem, inter-tooth permanent magnets 175, 176, 177, 178, 179, 17A may be added in the same manner as the inter-tooth permanent magnets 11S, 11T, 11U, and 11V shown in FIG. it can. These permanent magnets act to pass a magnetic flux in the opposite direction to the polarity of the stator magnetic poles through both teeth, and to reverse-bias the magnetic flux B and the magnetic field strength H of the soft magnetic material.

  Specifically, for example, the permanent magnet 176 sets the direction of the B-phase stator magnetic pole 82 as the S pole and the direction of the A / phase stator magnetic pole 83 as the N pole. The N pole magnetic flux φpm of the permanent magnet 176 passes through the A / phase stator magnetic pole 83, passes through the back yoke, passes through the B phase stator magnetic pole 82, and returns to the S pole of the permanent magnet 176. As long as the magnetic flux path does not become magnetically saturated for some reason, the magnetic resistance of this magnetic path φpm is kept sufficiently low. On the other hand, when the B stator magnetic pole 82 is excited to generate torque, it acts as the S pole, so that the acting magnetic flux φb passes from the rotor side through 82 to the back yoke side. In the portion 82, the magnetic flux φpm and the magnetic flux φb are superimposed, and the magnetic flux φpm and the magnetic flux φb are in opposite directions. For example, when the magnetic flux φb and the magnetic flux φpm have the same magnitude, the magnetic flux passing through the B-phase stator magnetic pole is zero because the direction of the magnetic flux is opposite. With such an action, the amount of magnetic flux passing through the stator magnetic pole can be increased up to twice as much as when there is no permanent magnet.

  As a result, it is possible to reduce the above problem that the amount of magnetic flux that can pass through the stator magnetic poles of FIG. 17 is insufficient. It should be noted that the same effect cannot be obtained at a place where the polarities of the adjacent stator magnetic poles are the same, for example, between the B-phase stator magnetic pole 82 and the A-phase stator magnetic pole 81. Further, the permanent magnets 175, 176, 177, 178, 179, 17A between these teeth also have an action and an effect of reducing leakage magnetic flux between the stator magnetic poles.

  Further, in the stator of FIG. 17, it is possible to add a permanent magnet to the back yoke portion between the stator magnetic poles having different polarities to reduce the excitation burden of each excitation current. Permanent magnets 17B, 17C, 17D, 17E, 17F, and 17G. The direction of the polarity of the permanent magnet is the direction of the polarity of each stator magnetic pole. When two stator magnetic poles having the same polarity are arranged next to each other, the amount of magnetic flux passing through these two becomes constant regardless of the rotor rotational position, so that these permanent magnets can be added. The amount of magnetic flux generated by the permanent magnet is constant regardless of the rotor rotational position. Since the excitation load of each excitation current can be reduced, the motor can be made highly efficient and downsized.

Next, an embodiment of claim 4 is shown in FIG. The motor shown in FIG. 18 has four types of currents Ij, Ik, Im, and In shown in FIG. 15. In order to avoid complication of an inverter that generates these currents, the currents to be supplied are 2 of Ij and Ik. It is a motor of the structure made into a kind. The following expression is established from the expressions (1), (2), (3), and (4).
2 × Ia = Ij + Ik = Im (5)
2 × Ib = Ij−Ik = In (6)
In this relation, the motor of FIG. 15 can be converted as shown in FIG. Another aim of the motor shown in FIG. 18 is to simplify the wiring connection and coil end.

  The winding 151 in FIG. 15 can be replaced with 187 and 188 in FIG. The winding 152 in FIG. 15 can be replaced with 182 and 181 in FIG. The winding 153 in FIG. 15 can be replaced with 184 and 185 in FIG. The winding 154 of FIG. 15 can be replaced with 18A and 18B of FIG.

  The winding connections in FIG. 18 are significantly different from the winding connections in FIG. The windings 181 and 182 are concentrated windings as indicated by broken lines, and the current Ij is applied. The windings 183 and 184 are concentrated windings as indicated by broken lines, and the current Ik is applied. The windings 185 and 186 are concentrated windings as indicated by broken lines, and the current Ij is applied. The windings 188 and 189 are concentrated windings as indicated by broken lines, and a current Ik is applied. Windings are wound around the windings 18B and 18E, and a current Ik is applied. Windings are wound around the windings 187 and 18A, and the current Ij is applied.

  The motor of FIG. 18 can be driven with two types of currents Ij and Ik. In addition, a somewhat wasteful current flows, but since there is one winding in a narrow slot and two windings in a slot with a wide opening, the winding can be wound without difficulty. The coil end is short compared to the motor of FIG.

  Next, an example of a driving circuit for the currents Ij and Ik will be described with reference to FIG. The current Ij is a one-way current as shown in the equation (1). By turning on T5 and T6, the current flowing to the winding 41 is increased, and by turning it off, energy is generated by two diodes in opposite directions. Is regenerated to the DC voltage source 37. The winding 191 is a general term for windings through which the current Ij is to be applied. As shown in the equation (2), the current Ik is an alternating current in which the positive / negative value of the current changes depending on whether the rotor rotational position θr to be energized Ia or the rotor rotational position θr to be energized Ib is T7, T8, The current in both directions is controlled by T9 and TA. The winding 42 is a general term for windings through which the current Ik is to be applied.

  The drive circuit of FIG. 19 is composed of six transistors, and the power supply from the DC voltage source 37 can be supplied in parallel from two paths. Therefore, when the voltage of the DC voltage source 37 is Vt and the rated current of the transistor is It, the maximum output power Pm1 is 2 × Vt × It. Even in the motor configuration, when rotating at a constant rotational speed, the magnetic fluxes φ1 and φ2 interlinked with both windings change with the rotation of the rotor except for the current switching region, and the rate of change dφ1 of each magnetic flux changes. Since / dt and dφ2 / dt are constant values, the maximum motor input can be set to a value close to 2 × Vt × It. On the other hand, a commonly used three-phase AC voltage / current inverter also uses six transistors, but is a three-terminal network, and the maximum output Pm2 is Vt × It. Accordingly, the inverter of FIG. 19 may be able to reduce the current capacity of the transistor to nearly ½ as compared with a three-phase AC voltage / current inverter, and may be greatly reduced in size.

Next, an example of a drive circuit for the currents Ij, Ik, Im, and In will be described with reference to FIG. Compared with the drive circuit of FIG. 20, it is necessary to add Im and In drive circuits. The current Im is driven by the transistors T11 and T12, and the current In is driven by the transistors T13 and T14.
Winding Yp1 is a general term for windings through which current Im should be applied. Winding Yp2 is a general term for windings through which current In should be passed. The number of transistors becomes ten, and the number of elements increases, which is complicated.

  Next, FIG. 21 shows a simplified example of the inverter of FIG. The current Im is driven by the transistor T15 and its series circuit. The winding 211 is a general term for windings through which the current Im is to be applied. The current In is driven by the transistor T16 and its series circuit. The winding 212 is a general term for windings through which the current In is to be passed. The current 2 × Ij is the sum of the current Im and the current In, and is driven by the transistor T17 and its series circuit. Winding 213 is a general term for windings through which current Ij should be applied. The diodes 214 and 215 may be omitted depending on driving conditions.

  However, FIG. 21 shows the basic concept of energization, and the balance between current and voltage is ignored. That is, the windings 211 and 212 and the winding 213 are in series. The current flowing through 213 is 2 × Ik. Therefore, it is necessary to adjust the number of windings of the four sets of windings 211, 212, 213, and 192 of a specific motor. For example, for the winding 213, there is a method in which the winding is divided into two and arranged in parallel.

  The inverter of FIG. 21 has seven transistors, one more transistor than the inverter of FIG. However, as described above, compared to a three-phase AC voltage / current inverter, since electric power can be supplied through two paths, the entire current capacity of the inverter can be reduced, which is advantageous.

  Next, an embodiment of claim 5 will be described. Claim 5 is a claim limited to the basic configuration, and examples thereof are shown in FIGS. 1, 5, 8, and 17. Various modifications such as multipolarization are possible.

  Next, an embodiment of claim 6 will be shown and described. FIG. 22 is an example in which the rotor shape of FIG. 6 is modified to reduce torque ripple. The horizontal axis in FIG. 22 is the electrical angle of the rotor rotation angle. The vertical axis is the rotor axial direction. 221 in FIG. 22A is the shape of the surface facing the rotor of the A-phase stator magnetic pole 57 in FIG. Similarly, 222 denotes a B-phase stator magnetic pole 59, 223 denotes an A / phase stator magnetic pole 58, 224 denotes a shape of a surface of the B / phase stator magnetic pole 5A facing the respective rotors. Each stator magnetic pole has a circumferential width of 75 ° and a period of 90 °.

  225 and 227 are the same, and are horizontal development views of the shape of the surface facing the stator of the rotor. The direction of the CCW of the rotor is from left to right on the paper surface of FIG. An operation of rotating the rotor to the CCW will be described. The shape of the rotor magnetic pole 225 is the paper surface of FIG. 22, the rotation angle width RFF of the front end portion in the traveling direction is 15 °, and the rotor axial thickness of that portion is 1/3 of the axial thickness of the rotor. The right angle 65 of 15 ° to 75 ° is 2/3 of the axial thickness of the rotor. Between 65 ° on the right side of 65 is 3/3 of the axial thickness of the rotor, that is, the total length. As shown in the figure, the shape has three steps.

  The rotor position θr, which is the right end of the rotor magnetic pole 225 shown in FIG. 22B, is in the vicinity of 0 °, the A-phase current Ia is supplied to the A-phase windings 57 and 58, and the A / phase windings 5E and 5F are supplied. By energizing the A / phase current −Ia, a magnetic attractive force is generated, and a CCW torque is generated in FIG. 5 and a rightward torque T2 is generated on the paper surface of FIG. The same torque T2 can be generated when the rotor position θr is 0 ° to 15 °. Here, at the position where the rotor position θr is 15 °, that is, the rotational position of the rotor magnetic pole 225 in FIG. 22C, the rotor axial width W2 of the portion of the rotor magnetic pole 225 facing the stator magnetic pole 221 is small. 1/3 of the total axial length.

  FIG. 22C shows a state where the rotor position θr of the rotor magnetic pole 225 is 15 °. In this state, the rotor axial width of the portion of the rotor magnetic pole 225 that faces the stator magnetic pole 221 is a rotational angle position where the rotor axial direction changes from W2 to W3, and the generated torque T3 is between the rotor rotational position θr of 15 ° and 75 °. The rotational change rate d (SSR) / dθr of the area SSR facing the stator magnetic pole 221 is 2/3 of the theoretical maximum value.

  FIG. 22D shows a state where the rotor rotational position θr = 75 ° of the rotor magnetic pole 225. When θr is between 75 ° and 90 °, the rotational change rate d (SSR) / dθr of the facing area SSR is reduced to 1/3, so the generated torque is also 1/3.

  FIG. 22E shows a state where the rotor position θr of the rotor magnetic pole 225 is 90 °. When θr is between 90 ° and 105 ° which is (f) of FIG. 22, the rotational change rate d (SSR) / dθr of the facing area SSR is reduced to 1/3, and the generated torque is also 1/3.

  The B-phase stator magnetic pole 59 and the B / phase stator magnetic poles 5A 222 and 224 are also 90 ° behind the A-phase and A / phase, and can generate the CCW torque by the B-phase excitation current Ib. . Therefore, torque can be generated over the entire circumference by driving alternately.

  FIG. 23 is an example of voltage characteristics, current characteristics, and torque characteristics during the motor operation described in FIG. 23A and 23C, the horizontal axis is the rotor rotation angle, and the vertical axis is the induced voltage. In FIGS. 23B and 23D, the horizontal axis is the rotor rotation angle, and the vertical axis is the current. In FIG. 23 (e), the horizontal axis is the rotor rotation angle, and the vertical axis is the torque. FIG. 23A shows an example of an induced voltage of the A-phase winding when the A-phase current Ia is supplied with a constant value when the rotor rotational position θr is between 0 ° and 90 ° and between 180 ° and 270 °. It is. This is a value related to the rotational change rate d (SSR) / dθr of the area SSR and the A-phase current Ia. The negative voltage shown in (a) of FIG. 23 is a negative voltage generated as a phenomenon of regenerating the magnetic energy of the motor when the A-phase current is decreased. Note that the shape of the negative voltage varies greatly depending on the current reduction method, the rotational speed, and the like. FIG. 23 (c) shows a case where the B-phase current Ib is energized with a constant value when the rotor rotational position θr is between 90 ° and 180 ° and between 270 ° and 360 °, as in FIG. 23 (a). It is an example of the induced voltage of a B phase winding.

  FIG. 23B shows an example of energization of the A-phase current Ia. During this period, torque having a shape substantially similar to the induced voltage of the A-phase winding is generated. FIG. 23D shows an example of energization of the B-phase current Ib. During this period, torque having a shape substantially similar to the induced voltage of the B-phase winding is generated. In (b) and (d) of FIG. 23, energization is performed so that the A-phase current Ia and the B-phase current Ib flow just alternately. FIG. 23E shows a value obtained by adding the A-phase torque and the B-phase torque. The maximum value of this torque is 2/3 of the maximum torque value shown in FIG. 7E, and the average torque is reduced, but the torque pulsation is reduced.

  Next, another embodiment of claim 6 will be described. FIG. 24 shows an example in which a torque characteristic is improved by adding a soft magnetic material to the stator and rotor of FIG. Soft magnetic bodies to be added are both axial ends of the stator and axial ends of the rotor. Therefore, there are restrictions on the dimensions that can be easily added, and it is effective for a motor having a relatively flat shape and a small length in the motor axial direction.

  FIG. 24A is a horizontal development view of the stator magnetic poles. A soft magnetic material 248 is added to each stator magnetic pole at both ends in the rotor axial direction. Each stator magnetic pole is added near the rotor. A soft magnetic body 249 is added to each rotor magnetic pole at both ends in the rotor axial direction. Each rotor magnetic pole is added near the stator. Other stator magnetic pole shapes and rotor magnetic pole shapes are the same as in FIG. Reference numeral 241 denotes an A-phase stator magnetic pole, 242 denotes a B-phase stator magnetic pole, 243 denotes an A / phase stator magnetic pole, and 244 denotes a B / phase stator magnetic pole. 245 and 246 are rotor magnetic poles.

  FIG. 24B is a view at a rotor rotation angle of 75 ° corresponding to FIG. In FIG. 6, the torque decreases to ½ between 75 ° and 90 °. However, in FIG. 24, since the soft magnetic bodies 248 and 249 are added, the torque does not decrease. Further, torque can be generated by the soft magnetic bodies 248 and 249 between 90 ° and 105 ° in FIG.

  FIG. 25 shows the voltage, current, and torque characteristics shown in FIG. FIG. 25A shows an induced voltage of the A-phase winding when the A-phase current Ia is energized with a constant value. FIG. 23B is an example of energization of the A-phase current Ia. FIG. 25C shows an induced voltage of the B-phase winding when the B-phase current Ib is energized with a constant value. FIG. 23B is an example of energizing the B-phase current Ib. (E) in FIG. 23 is a value obtained by adding the A-phase torque and the B-phase torque, and the torque pulsation can be eliminated by the effects of the soft magnetic bodies 248 and 249. The torque value is the maximum torque value shown in FIG.

  As a result, although the shape of the soft magnetic bodies 248 and 249 is limited, the torque characteristics can be improved. Also. 24D and 24E are obtained by moving both the soft magnetic bodies 248 and 249 in FIGS. 24A and 24B in the direction of the rotor rotation angle by the same angle. Will not change. The mounting position can be moved for the convenience of design of the configuration of the soft magnetic bodies 248 and 249.

  Next, an embodiment of claim 7 will be described with reference to FIG. Examples of the shape of the rotor magnetic pole are shown in FIGS. Since these rotor shapes change in the rotation direction, there is a problem that manufacturing costs are high. In addition, noise problems may occur at high speed rotation. The configuration of FIG. 26 constitutes a rotor having an equivalent magnetic resistance by providing holes and depressions in the electromagnetic steel sheet. FIG. 26 (a) means the rotor of FIGS. 1 and 2, in which the portion 261 is a space, the portion 263 is clogged with soft magnetic material, and the portion 262 is an intermediate between 261 and 263. It is the magnetic characteristic.

  FIG. 26 (b) realizes magnetic characteristics equivalent to those of FIG. 26 (a) using 264 large holes and 265 elongated holes. If it is such a structure, manufacture which can be comprised only by laminating | stacking the same electromagnetic steel plate is easy. Moreover, since the outer periphery is circular, the noise that the rotor cuts off can be reduced.

  FIG. 26C shows a magnetic characteristic similar to that of FIG. 26A obtained by the air gap between the stator and the rotor. Reference numeral 267 denotes a space, and reference numeral 268 denotes a slightly wide air gap between the stator and the rotor. The portion 269 is a place where the air gap is small and magnetic flux passage between the stator and the rotor is easy. The stator and the rotor can be configured simply by laminating the same electromagnetic steel sheet, and it is easy to manufacture.

  Next, claim 8 will be described. According to an eighth aspect of the present invention, in the two stator magnetic poles arranged side by side in the circumferential direction, the tips of the teeth of the two stator magnetic poles having opposite magnetic flux directions when energized passing from the outer diameter side to the inner diameter side of the teeth. 11 is provided with a permanent magnet having a polarity for supplying magnetic flux so that the direction of the magnetic flux is opposite, and as described above, permanent magnets such as 11S, 11T, 11U, and 11V in FIG. 11 are added. Technology.

  Next, claim 9 will be described. Claim 9 is a configuration including a permanent magnet disposed on the motor back yoke and having a polarity oriented in the magnetic flux direction of each stator magnetic pole. As already described, 10S, 10T, 10U, 10V of FIG. This is a technique for adding a permanent magnet.

  In the case of the motor configuration as shown in FIG. 11, a permanent magnet cannot be added as shown in FIG. In such a case, the configuration of the back yoke shown in FIG. 27 is possible. FIG. 27 is a side view of the stator core, and the upper and lower sides of the drawing are the rotor axial direction. Reference numeral 271 denotes a ring-shaped soft magnetic body constituting the back yoke, and 272 is a soft magnetic body having the same shape constituting the back yoke. Between the 271 and 272, as shown in the figure, a permanent magnet 273 facing the directions of the north and south poles is disposed. In FIG. 11, the back yoke side of the stator magnetic poles 114, 11 </ b> A, 11 </ b> G, 11 </ b> P constituting the N pole is magnetically connected to 272. The back yoke side of the stator magnetic poles 111, 117, 11D, and 11K constituting the S pole is magnetically connected to 271. At this time, the back yoke of the stator shown in FIG. 11 is removed, and each stator magnetic pole is magnetically connected to the 271 or 272. With such a configuration, each stator magnetic pole can be excited by the permanent magnet 273, the excitation current component of each stator magnetic pole can be reduced, and the motor efficiency can be increased. In addition, since this structure comprises not a planar shape but a three-dimensional magnetic path, it is difficult to realize with a structure in which electromagnetic steel sheets are laminated. As one of the countermeasures, the magnetic path can be realized relatively easily by configuring a three-dimensional magnetic path using a dust core.

  Next, an embodiment of claim 10 will be described with reference to FIG. FIG. 28 is a longitudinal sectional view of the motor of the present invention. Reference numeral 281 denotes a rotor shaft, and reference numeral 282 denotes a first rotor having a configuration like the rotor shown in FIG. Reference numeral 283 denotes a similar second rotor. Reference numeral 284 denotes a space having a large magnetic resistance such as a space. Reference numeral 285 denotes a first stator, and reference numerals 286 and 287 denote claw pole-shaped stator magnetic poles which constitute an A-phase stator magnetic pole and an A / phase stator magnetic pole, respectively. Reference numeral 288 denotes an annular A-phase winding for exciting the A-phase stator magnetic pole and the A / phase stator magnetic pole. Reference numeral 289 denotes a second stator, and 28A and 28B denote claw pole-shaped stator magnetic poles, which respectively constitute a B-phase stator magnetic pole and a B / phase stator magnetic pole. 28C is an annular B-phase winding for exciting the B-phase stator pole and the B / phase stator pole. 28D is a space having a large magnetic resistance such as a space. A plurality of stator magnetic poles for each phase are provided on the circumference. Depending on the size of the motor, at least two or more phase stator poles are provided. Further, the characteristics of the stator magnetic pole and the rotor magnetic pole are the same as those of the other examples shown in the present invention.

  The claw pole-shaped magnetic path can be manufactured by a press technique by using a dust core. Also, it is easy to manufacture the annular winding. By using an annular winding and a claw pole-shaped magnetic path, a motor with excellent manufacturability can be configured.

  Moreover, the structure which arrange | positions two motor components like FIG. 28 in parallel can be comprised by methods other than arranging in a rotor axial direction. In this method, the first motor component is disposed on the outer diameter side of the motor, and the second motor component is disposed on the inner diameter side of the motor. There is also a method in which a first motor component and a second motor component are arranged back-to-back in the rotor axial direction by configuring like a so-called axial gap motor.

  Although the present invention has been described above, various modifications, applications, and combinations are possible. For example, the magnetic characteristics in the circumferential direction of the rotor magnetic pole can also be realized by applying a technique of rotor skew or stator skew. It can also be realized in combination with techniques such as step skew. By increasing the number of rotor magnetic poles several times and moving the stator magnetic poles in the circumferential direction at the increased intervals, a motor having the same concept and similar characteristics can be realized. The number of poles can be changed. A motor configuration in which the first motor is arranged on the outer diameter side, the second motor is arranged on the inner diameter side, and a total of two motors are arranged and integrated is possible. Aluminum wire or the like can be used as the type of winding, and is not limited. As the soft magnetic material, not only electromagnetic steel sheets but also various materials such as a pressure magnetic core can be used. Various permanent magnets can be used, and the strength of the magnet can be varied during use. These are also included in the present invention.

111, 11D A phase stator poles 112, 113, 11E, 11F A phase winding 114, 11G A / phase stator poles 115, 116, 11H, 11J A / phase winding 117, 11K B phase stator poles 118, 119, 11M 11N B-phase winding 11A, 11P B / phase stator magnetic poles 11B, 11C, 11Q, 11R B-phase winding

Claims (10)

An A-phase stator pole;
A / phase stator poles having a phase difference of 180 ° from the A phase;
A B-phase stator pole having a phase difference of 90 ° from the A-phase;
A B / phase stator pole having a phase difference of 270 ° from the A phase;
Windings for exciting each stator pole;
A first rotating section having a large radial magnetic resistance average value R1R for a unit area over the entire length in the rotor axial direction of a unit angular width in the circumferential direction of the rotor;
A second rotating part arranged in the circumferential direction of the rotor;
A third rotating part arranged in the circumferential direction of the rotor,
The radial permeance (1 / magnetic resistance average value R2R) of the unit area over the entire length in the rotor axial direction of the unit angular width in the circumferential direction of the second rotating part is the circumferential direction of the third rotating part. Is a value of 15% to 85% of the radial permeance (1 / magnetic resistance average value R3R) of the unit area over the entire length in the rotor axial direction of the unit angular width of
A reluctance motor comprising two or more sets of the first rotating unit, the second rotating unit, and the third rotating unit. In claim 1,
Comprising 6 or more rotor magnetic poles composed of the first rotating part and the third rotating part,
The A-phase stator magnetic pole, the A / phase stator magnetic pole, the B-phase stator magnetic pole, and the B / phase stator magnetic pole, each having two stator magnetic poles in total, Reluctance motor. In claim 1,
A current component that excites the A-phase stator magnetic pole is denoted by Ia, and a current component that excites the B-phase stator magnetic pole is denoted by Ib. A coil that energizes the current Ij to the slot whose current to be supplied to the slot is (Ia + Ib) is wound. Turn
Winding a winding for energizing the current Ik to the slot where the current to be passed through the slot is (Ia-Ib),
Winding a winding to pass current Im to a slot whose current to be passed through the slot is (2 × Ia),
Winding a winding for energizing the current In to the slot where the current to be passed through the slot is (2 × Ib),
A reluctance motor characterized in that when the signs of the currents to be energized are opposite, the windings are turned in the opposite direction. In claim 3,
The winding for energizing the current Im is formed by winding a winding for energizing the current Ij and a winding for energizing the current Ik to the slot,
The winding for energizing the current In is constituted by winding a winding for energizing the current Ij and a winding for energizing the current (−Ik). In claim 1,
There are four stator magnetic poles: A phase, A / phase, B phase and B / phase.
A reluctance motor comprising two sets of the first rotating unit, the second rotating unit, and the third rotating unit. In claim 1,
A fourth rotating part is provided between the second rotating part and the third rotating part in the circumferential direction;
The radial permeance (1 / magnetic resistance average value R4R) of the unit area over the entire length in the rotor axial direction of the unit angular width in the circumferential direction of the fourth rotating part is the permeance (1 / Reluctance motor having a value of 30% to 85% of the magnetic resistance average value R3R). In claim 1,
By means of a plurality of holes and grooves that are applied to the magnetic steel sheet, the magnetic resistance average value R1R of the first rotating part, the magnetic resistance average value R2R of the second rotating part, and the magnetic resistance average value R3R of the third rotating part Created to have an almost equivalent magnetoresistance ratio,
A reluctance motor, wherein the electromagnetic steel plates are laminated in a rotor axial direction. In claim 1,
In the two stator magnetic poles arranged side by side in the circumferential direction, the magnetic flux near the tips of the teeth of the two stator magnetic poles in which the direction of magnetic flux passing through the teeth from the outer diameter side to the inner diameter side is opposite to each other. A reluctance motor comprising a permanent magnet having a polarity for supplying a magnetic flux whose direction is reversed. In claim 1,
A reluctance motor comprising a permanent magnet disposed on a motor back yoke and having a polarity directed to a magnetic flux direction of each stator magnetic pole. In claim 1,
Two or more A-phase stator poles;
The A-phase stator poles are two or more A / phase stator poles arranged in a claw pole shape,
An annular winding that is disposed so as to intersect the A-phase stator magnetic pole and the A / phase stator magnetic pole and energizes a current that excites magnetic flux that passes through both stator magnetic poles;
Two or more B-phase stator poles;
The B-phase stator poles are two or more B / phase stator poles arranged in a claw pole shape,
An annular winding that is arranged so as to intersect the B-phase stator magnetic pole and the B / phase stator magnetic pole and energizes a current that excites a magnetic flux that passes through both stator magnetic poles;
A rotor portion RAA in which the A-phase stator magnetic pole and the A / phase stator magnetic pole act electromagnetically;
A rotor portion RBB in which the B-phase stator magnetic pole and the B / phase stator magnetic pole act electromagnetically;
The rotor part RAA and the rotor part RBB are mechanically coupled,
A reluctance motor, wherein each stator magnetic pole is arranged at a position where a magnetic flux passing through the A-phase stator magnetic pole and a magnetic flux passing through the B-phase stator magnetic pole are separated.

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