JP2011166525A - Optical receiver - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To attain an optical receiver that suppresses demodulation signal fluctuation when a signal light is superposed with noise light and receives an optical phase modulation signal with suppressed bit identification error. <P>SOLUTION: A demodulation optical signal (differential transfer modulated light) is branched, and one signal (main signal) is delay-detected by using a delay interferometer and an optical detector and then demodulated. The other signal is directly detected by the optical detector and a monitor signal is extracted. In a signal processing circuit, the monitor signal is branched into two, and one is delayed and added and then the resulting signal is subtracted from the main signal, thereby canceling the strength fluctuation of the signal. <P>COPYRIGHT: (C)2011,JPO&INPIT

Description

  The present invention relates to an optical signal receiving technique, and more particularly to an optical receiver that receives differential phase shift keying signal light.

  Optical fiber transmission technology is widely used as a system for realizing long-distance and large-capacity signal transmission, and research aimed at further enhancement of performance is underway. There are several modulation / demodulation methods for optical transmission. Among them, the differential phase shift keying (DPSK) method has higher reception sensitivity than the conventional intensity modulation / direct detection method, and is due to nonlinear phenomena in the transmission fiber. It has advantages such as being less susceptible to signal degradation.

  In the DPSK transmission method, a digital signal is transmitted by a phase difference between adjacent time slots. That is, the transmitter transmits a signal light in which the phase difference between adjacent slots is 0 when sending a bit “0” and the phase difference between adjacent slots is π when sending a bit “1”, and the receiver The transmission signal is demodulated by measuring the phase difference of the slots.

  FIG. 5 shows a basic configuration of a conventional optical DPSK signal receiver.

  In the optical DPSK signal receiver shown in the figure, the input signal light is amplified by the optical amplifier 1, and then excess spontaneous emission light output from the optical amplifier 1 is removed by the optical filter 2. The output from the optical filter 2 is branched into two paths by the branching unit 3, one of which is given a time delay for one bit slot, and then combined again by the two-input two-output (2 × 2) optical multiplexer 4. Waved. The outputs of the optical multiplexer 4 are input to the photodetectors 5 and 6, respectively. This branching / delaying / combining configuration is called a “1-bit delay interferometer” (for example, see Non-Patent Documents 1 and 2).

  In the multiplexer 4 of the 1-bit delay interferometer, light passing through the two paths interferes. Here, since one path is delayed by one slot, it is the light in the adjacent time slots that interferes. If the phase difference between adjacent slots is 0 as a result of the interference, the light is output to the photodetector D1, and if it is π, the light is output to the photodetector D2. Therefore, the transmitted signal bits are demodulated by differentially detecting the output signals from the two photodetectors D1, D2 by the differential synthesis circuit 5.

  The method described above is a method of transmitting a binary digital signal by adding it to the phase difference {0, π} of the adjacent slot. As a higher order method, the binary digital signal is converted to a phase difference {0, There is also a system in which π / 2, π, and 3π / 4} are given and transmitted. This is a method called DQPSK (differential quaternary phase shift keying). The receiver configuration is shown in FIG. After the input signal light is amplified by the optical amplifier 11, excess spontaneous emission light output from the optical amplifier 11 is removed by the optical filter 12. The output of the optical filter 12 is branched into two paths by the optical coupler 13 and is input to the 1-bit delay interferometers 15 and 25, respectively. However, the propagation phase differences of the delay paths of the interferometers 15 and 25 are different from each other, the 1-bit delay interferometer 15 has a phase difference of π / 4, and the other 1-bit delay interferometer 25 has −π / 4. Is set. Interferometer outputs are connected to photodetectors D11, D12, D21, D22, respectively. Then, the photodetection signals from the same interferometer output are differentially synthesized by the differential synthesis circuits 16 and 26.

  When the propagation phase difference of the 1-bit delay interferometers 15 and 25 is set as described above, the differential combined output signal for each phase difference of the input signal light is as follows.

If the phase difference is 0, {S1 = + d, S2 = + d};
If the phase difference is π / 2, {S1 = + d, S2 = −d};
{S1 = −d, S2 = −d} for phase difference π;
When the phase difference is 3π / 4, {S1 = −d, S2 = d}.

  However, S1 is a differential output from the interferometer 15 having a phase difference of π / 4, S2 is a differential output from the interferometer 25 having a phase difference of −π / 4, and d is a constant determined by a circuit constant. The combination patterns of the two output values {S1, S2} are all different depending on the four phase difference values. Therefore, if the two output values are determined in combination, the four phase values can be identified, and the four bit values are demodulated.

"Coherent Optical Communication Engineering" Ogoshi, Kikuchi, Ohmsha p.145, 1989. "Coherent optical communication" Shimada, IEICE p.24 Showa 63.

  In a receiving system, noise light is often superimposed on light input to a photodetector in addition to the original transmission signal light. A typical example is spontaneous emission light generated by an optical amplifier. When there is such noise light, the output signal level from the photodetector fluctuates. Such signal level fluctuations cause bit identification errors and cause performance degradation of the transmission system.

  The present invention has been made in view of the above points, and provides an optical receiver that receives an optical phase modulation signal that suppresses demodulated signal fluctuation when noise light is superimposed on signal light and suppresses bit identification errors. The purpose is to provide.

  FIG. 1 is a principle configuration diagram of the present invention.

The present invention (Claim 1) is an optical receiver for receiving a differential phase modulation signal,
The optical branching means 50 for branching the input differential phase modulation signal into the main signal light and the monitor signal light, and the monitor light for converting the light intensity of the monitor signal light branched by the optical branching means 50 into an electrical signal and outputting it Intensity detecting means 70;
A signal demodulating means 60 for demodulating a phase modulated signal as an electric signal from the main signal light branched by the optical branching means 50;
A signal processing means 80 for differentially synthesizing and outputting the demodulated signal output from the signal demodulating means 60 and the monitor signals of two adjacent bit slots output from the monitor light intensity detecting means 70;
With
The signal processing means 80
The monitor light signal output from the monitor light intensity detection means 70 is branched into two, a delay is added to one of the two, and the other monitor light signal branched is added, and subtracted from the demodulated signal output from the signal demodulation means 60 Means for performing signal processing.

  The present invention (Claim 2) is an optical receiver when the differential phase modulation signal is binary differential phase shift keying signal light.

Further, according to the present invention (Claim 3), the signal demodulation means in the optical receiver according to Claim 2 is
The signal light is branched into two, a time delay of one bit slot is given to one of the two branched signal lights, and the two branched lights are combined again by a 2 × 2 optical multiplexer, and the 2 × 2 optical multiplexer Means for detecting the intensity of light output from each of the two output terminals, and differentially synthesizing and outputting the detected light intensities.

  The present invention (Claim 4) is an optical receiver when the differential phase modulation signal is quaternary differential phase shift keying signal light.

Further, according to the present invention (Claim 5), the signal demodulation means in the optical receiver according to Claim 4
Means for branching signal light into signal light A and signal light B;
The branched signal light A is branched into two, a time delay of 1 bit slot and a delay phase φ1 are given to _one of the two branched signal lights, and the 2 branched signal light is again transmitted by the 2 × 2 optical multiplexer A. Means for combining, detecting the intensity of light output from the two output terminals of the optical multiplexer A, respectively, and differentially combining the detected light intensities for output;
The signal light B is branched into two, a time delay of 1 bit slot and a delay phase φ ₂ are given to one of the two branched signal lights, and the two-branched signal light is combined again by the 2 × 2 optical multiplexer B. And means for detecting the intensity of light output from the two output terminals of the optical multiplexer B, respectively, and differentially combining the detected light intensities for output.
With
The delay phases φ ₁ and φ ₂ are optical receivers different from each other by π / 2.

  As described above, the present invention suppresses the received signal fluctuation of the differential phase shift keying signal light due to the noise light by detecting the intensity fluctuation contained in the optical phase modulation signal and canceling the fluctuation in the signal processing means. Thus, an optical receiver with reduced signal demodulation characteristics can be realized.

It is a principle block diagram of this invention. It is a block diagram of the optical receiver in the 1st Embodiment of this invention. It is a block diagram of the signal processing circuit in the 1st Embodiment of this invention. It is a block diagram of the optical receiver in the 2nd Embodiment of this invention. It is a block diagram of the conventional optical DPSK signal receiver. It is a block diagram of the conventional optical DQPSK signal receiver.

  Hereinafter, embodiments of the present invention will be described with reference to the drawings.

[First Embodiment]
FIG. 2 shows a configuration of the receiver according to the first embodiment of the present invention.

  The receiver 100 shown in the figure includes an optical amplifier 110, an optical filter 120, optical splitters 130 and 140, a 2 × 2 multiplexer 150, photodetectors D1 and D2, a differential synthesis circuit 160, a photodetector M170, The signal processing circuit 180 is configured. Among these, the optical branching unit 140 and the 2 × 2 multiplexer 150 constitute the 1-bit delay circuit 101.

  In the present embodiment, the input differential phase modulation signal light is first amplified by the optical amplifier 110, and then the excess spontaneous emission light output from the optical amplifier 110 is removed by the optical filter 120. Part of the output of the optical filter 120 is decomposed by the optical splitter 130 and input to the photodetector M170. The photodetector M170 converts the intensity of the input light into an electric signal and outputs it to the signal processing circuit 180.

  On the other hand, the main signal light partly branched by the optical branching device 130 is input to the 1-bit delay circuit 101 and is detected by the photodetectors D1 and D2, respectively. Differential detection (combining) is performed. This main signal light is the same as described in the section of the prior art.

  In the present embodiment, the difference from the prior art is that differential detection is output via the 1-bit delay interferometer 101, the photodetectors D1 and D2, and the differential synthesis circuit 160, and the signal processing circuit 180 performs the above-described partial processing. The signal processing based on the light intensity signal is performed.

  FIG. 3 shows the configuration of the signal processing circuit according to the first embodiment of the present invention.

  The signal processing circuit 180 is delayed by a delay circuit 182, a branch circuit 181 that branches an electric signal input from the photodetector M170, a delay circuit 182 that delays the electrical signal by time τ, and one signal branched by the branch circuit 181. An addition circuit 183 that adds signals and a subtraction circuit 184 that subtracts the circuit output from the addition circuit 183 from the output from the differential synthesis circuit 160.

  First, the complex amplitude other than the carrier vibration term of the output light of the optical amplifier 110 that has passed through the optical filter 120 is expressed as follows.

上記の式の第１項が本来受信したい信号光、第２項が受信特性劣化を引き起こす雑音光、であり、Ａ_s，Ａ_cはそれぞれの実数振幅、θ_s，θ_cはそれぞれの位相、ｔは時刻、である。ここでは、位相変調信号光を想定し、位相｛θ_s，θ_c｝は時間に依存している一方、実数振幅｛Ａ_s，Ａ_c｝は一定値としている。なお、キャリア振動項を省略しているのは、光フィルタ１２０を透過した光なので、そのキャリア周波数は信号光と雑音光とでほぼ同じためである。

In the above equation, the first term is the signal light that is originally desired to be received, the second term is the noise light that causes the reception characteristic deterioration, A _s and A _c are the respective real amplitudes, θ _s and θ _c are the respective phases, t is the time. Here, assuming phase-modulated signal light, the phase {θ _s , θ _c } depends on time, while the real number amplitude {A _s , A _c } is a constant value. Note that the carrier vibration term is omitted because the light transmitted through the optical filter 120 has a carrier frequency that is substantially the same for the signal light and the noise light.

  After a part of the output of the optical filter 120 is branched by the optical splitter 130, one signal light is input to the 1-bit delay interferometer 101. In the 1-bit delay interferometer 101, the input light is branched into two by the branching unit 140, delayed by one path, and then multiplexed again by the 2 × 2 multiplexer 150. The output light from the multiplexer 150 is expressed as follows.

上記の式において、Ｅ_１は光検出器Ｄ１へ出力される光電場、Ｅ_２は光検出器Ｄ２へ出力される光電場、α_１は光フィルタ１２０から光検出器Ｄ１までの振幅透過率、α_２は光フィルタ１２０から光検出器Ｄ２までの振幅透過率、ｔ_１は光フィルタ１２０から遅延干渉計１０１の短経路を経て光検出器Ｄ１，Ｄ２に到達するまでの時間、τは遅延干渉計１０１の遅延時間、である。なお、τは伝送信号のビット間隔でもある。

In the above equation, E ₁ is a photoelectric field output to the photodetector D1, E ₂ is a photoelectric field output to the photodetector D2, α ₁ is an amplitude transmittance from the optical filter 120 to the photodetector D1, α ₂ is the amplitude transmittance from the optical filter 120 to the optical detector D 2, t ₁ is the time from the optical filter 120 to the optical detectors D 1 and D 2 via the short path of the delay interferometer 101, and τ is the delayed interference 101 delay times in total. Note that τ is also the bit interval of the transmission signal.

The output light from the delay interferometer 101 is input to the photodetectors D1 and D2, and the light intensity is converted into an electrical signal and output. Output signals S ₁ from the photodetector D1, from equation (2) is expressed as follows.

上記の式（４）において、ηは光強度から電気信号への変換係数である。

In the above equation (4), η is a conversion coefficient from light intensity to an electric signal.

Here, the noise light is sufficiently weaker than the main signal light. That is, A _s >> A _c . This is a reasonable assumption in real systems. Under this assumption, equation (4) is approximated as follows:

同様にして、光検出器Ｄ２から出力される電気信号Ｓ_２は、式（３）より、次のように表される。

Similarly, electric signals S ₂ output from the optical detector D2, from equation (3) is expressed as follows.

光検出器Ｄ１からの出力信号と光検出器Ｄ２からの出力信号は差動合成回路１６０で差動的に合成される。式（５）（６）より、差動合成回路１６０の差動合成出力Ｓ_０は次のように表される。

The output signal from the photodetector D1 and the output signal from the photodetector D2 are differentially synthesized by the differential synthesis circuit 160. From equations (5) and (6), the differential combined output S ₀ of the differential combining circuit 160 is expressed as follows.

但し、ｔ_２は光検出器Ｄ１，Ｄ２から差動合成回路１６０までの信号伝播時間である。また、│α_１│^２＝│α_２│^２とし、さらに、２η│α_１│^２＝ｋ_０とおいた。式（７）において、第１項は所望の受信信号であり、（第２項＋第３項）は、雑音光による揺らぎ成分を表している。

Here, t ₂ is a signal propagation time from the photodetectors D 1 and D 2 to the differential synthesis circuit 160. Further, | α ₁ | ² = | α ₂ | ^2, and 2η | α ₁ | ² = k ₀ . In Expression (7), the first term is a desired received signal, and (second term + third term) represents a fluctuation component due to noise light.

On the other hand, a part of the output light from the optical filter 120 is branched by the optical branching device 130, and the light intensity is converted into an electric signal by the photodetector M170. The electrical signal S _m (hereinafter referred to as “monitor signal”) output from the photodetector M170 is expressed as follows by the equation (1).

但し、α_mは光フィルタ１２０から光検出器Ｍ１７０までの振幅透過率、ｔ_ｍ１は光フィルタ１２０から光検出器Ｍ１７０までの伝播時間、である。また、η│α_m│^２＝ｋ_mとおいた。

Where α _m is the amplitude transmittance from the optical filter 120 to the photodetector M170, and t _m1 is the propagation time from the optical filter 120 to the photodetector M170. Also, it puts a η│α _m │ ² = k _m.

In the present invention, the signal processing circuit 180 uses the monitor signal to suppress signal fluctuation that occurs in the main signal. Specifically, first, the monitor signal is branched into two at the branching unit 181 of the signal processing circuit 180, and one of them is delayed by the delay τ circuit 182 by one bit slot time τ. The adder 183 multiplies the above two monitor signals by a coefficient, and the subtraction circuit 184 adds the adder 183 from the main signal S ₀ (output from the differential synthesis circuit 160) expressed by the equation (7). Subtract the output of. Expressed as a formula:

とする。但し、ｔ_３は主信号系の差動合成回路１６０から引き算回路１８４までの信号伝播時間、ｔ_ｍ２は光検出器Ｍ１７０から引き算回路１８４までの信号伝播時間、である。式（７）（８）を式（９）に代入すると、次式となる。

And However, _{t 3} is the signal propagation time from the differential combining circuit 160 of the main signal system to the subtraction circuit _{184, t m @ 2} is the signal propagation time from the photodetector M170 to subtraction circuit 184,. Substituting Equations (7) and (8) into Equation (9) gives the following equation.

ここで、

here,

とする。すると、

And Then

となる。

It becomes.

  In Expression (10), the first term represents a desired received signal component, the second term represents a direct current component, and the third and subsequent terms represent fluctuation components due to noise light. Since signal fluctuation is handled here, the third and subsequent terms will be considered below. First, the fluctuation component ΔS in the equation (10) is written.

なお、上式では、表記の簡便化のため、共通的な項であるＫＡ_ＳＡ_ｃは省略した。上式において、（第１項＋第２項）は主信号系における揺らぎ、（第３項＋第４項）はモニタ信号系における揺らぎ、にそれぞれ対応する。

In the above formula, for simplicity of notation, KA _S A _c is a common term is omitted. In the above equation, (first term + second term) corresponds to fluctuation in the main signal system, and (third term + fourth term) corresponds to fluctuation in the monitor signal system.

By the way, what is received here is the DPSK signal. In this case, the phase θ _s of the main signal light is expressed as follows.

但し、θ_s0はｔ＝０での位相であり、

Where θ _s0 is the phase at t = 0,

一方、θ_c(t)の表式はどのような雑音光を想定するかに依存するが、ここでは、時間変動は速くなく、１ビットスロット時間ではほぼ一定、即ち、

On the other hand, the expression of θ _c (t) depends on what kind of noise light is assumed, but here the time variation is not fast and is almost constant in 1 bit slot time, that is,

である雑音光を想定する。例えば、光増幅器１１０で発生する自然放出光のうち、信号ビットレートの１／２程度以下の速度で変動する成分がこれに相当する。それより早く変動する成分は対象外とするが、速い成分による揺らぎは信号復調時のバースバンドフィルタにより除去されるので、このような想定は、十分実用的である。この状況設定の下では、式（１１）において、
θ_c(t)=θ_c0 (14)
と定数で表される。

Assume that the noise light is. For example, of the spontaneous emission light generated by the optical amplifier 110, a component that fluctuates at a speed that is about ½ or less of the signal bit rate corresponds to this. Components that fluctuate faster than that are excluded, but fluctuations due to fast components are removed by the burst band filter at the time of signal demodulation, so this assumption is sufficiently practical. Under this situation setting, in equation (11):
θ _c (t) = θ _c0 (14)
And a constant.

  Now, assuming that the equations (12) and (14) are satisfied, the fluctuation equation (11) will be considered. First, Expressions (12) and (14) are substituted into Expression (11).

但し、表記の簡略化のため、ｔ'≡ｔ−ｔ_０とした。上式は、更に次のように展開される。

However, t′≡t−t ₀ for simplifying the notation. The above equation is further expanded as follows.

上式において式（１３）であるので、

In the above equation, since it is the equation (13),

式（１７）は、本実施の形態の受信器構成においては揺らぎゼロ、すなわち、雑音光による信号揺らぎが抑えられることを示している。ところで、式（１７）の（第１項＋第２項）は主信号系の揺らぎ、（第３項＋第４項）はモニタ信号の揺らぎ、にそれぞれ対応している。主信号系の揺らぎは従来の受信器構成における揺らぎに対応し、この場合には、

Expression (17) indicates that the receiver configuration of the present embodiment has zero fluctuation, that is, signal fluctuation due to noise light can be suppressed. By the way, (first term + second term) in equation (17) corresponds to fluctuation of the main signal system, and (third term + fourth term) corresponds to fluctuation of the monitor signal. The fluctuation of the main signal system corresponds to the fluctuation in the conventional receiver configuration. In this case,

となり、

And

のときに揺らぎが発生する。本実施の形態は、この主信号系の揺らぎをモニタ信号の揺らぎで打ち消すように構成されている。

Fluctuations occur when The present embodiment is configured to cancel the fluctuation of the main signal system by the fluctuation of the monitor signal.

[Second Embodiment]
FIG. 4 shows a configuration of an optical receiver in the second embodiment of the present invention.

  This embodiment is configured to demodulate a DQPSK signal that transmits a quaternary digital signal.

  The optical receiver shown in FIG. 4 includes an optical amplifier 201, an optical filter 202, an optical splitter 203, an optical coupler 204, optical splitters 205 and 210, a π / 4 delay circuit 206, optical multiplexers 207 and 212, and a photodetector. D11, D12, D21, D22, differential synthesis circuits 208, 213, signal processing circuits 209, 215, and a photodetector M214. Among these, the optical branching unit 205, the π / 4 delay circuit 206, and the optical multiplexer 207 constitute a 1-bit interferometer 230. The optical branching device 210, the −π / 4 delay circuit 211, and the optical multiplexer 212 constitute a 1-bit interferometer 240.

  The configuration of the signal processing circuits 209 and 215 is the same as the configuration of FIG. 3 of the first embodiment described above.

  In the present embodiment, first, the input differential phase-modulated signal light is amplified by the optical amplifier 201, and then excess spontaneous emission light output from the optical amplifier 201 is removed by the optical filter 202. A part of the output of the optical filter 202 is branched by the optical splitter 203 and input to the photodetector M214. The photodetector M214 converts the intensity of the input light into an electric signal and outputs it to the signal processing circuits 209 and 215.

  On the other hand, the main signal light partially branched is branched into two paths by the optical coupler 204, and is input to the 1-bit delay interferometers 230 and 240, respectively. The propagation phase difference of the delay paths of the 1-bit delay interferometers 230 and 240 is π / 4 for one and −π / 4 for the other. Interferometer outputs are connected to photodetectors D11 and D12 and photodetectors D21 and D22, respectively. Then, the light detection signals from the same interferometer output are operatively combined by the differential combining circuits 208 and 213. The main signal light reception configuration is the same as that described in the section of the prior art.

  The difference from this embodiment is that the signal processing circuits 209 and 215 correspond to the above-mentioned partially branched light intensity signals for the differential detection outputs (outputs of the operation synthesis circuits 208 and 213) from the 1-bit delay interferometers 230 and 240, respectively. The signal processing based on this is performed. Hereinafter, the specific signal processing process will be described using equations.

  First, the complex amplitude other than the carrier vibration term of the output light of the optical amplifier 201 that has passed through the optical filter 202 is expressed as follows.

各変数の意味は式（１）と同様である。

The meaning of each variable is the same as in equation (1).

  A part of the output of the optical filter 202 is branched by the optical splitter 203 and then further branched by the optical coupler 204. One is a 1-bit delay interferometer 230 having a delay phase difference of π / 4, and the other is a delay phase difference. Each is input to a 1-bit delay interferometer 240 of −π / 4.

  In the 1-bit delay interferometers 230 and 240, the input light is branched into two by the splitters 205 and 210, respectively, and after being delayed by one path, the signals are multiplexed again by the 2 × 2 multiplexers 207 and 212, respectively. The Respective output lights from the multiplexers 207 and 212 are expressed as follows.

上式において、Ｅ₁₁は光検出器Ｄ１１へ出力される光電場、Ｅ₁₂は光検出器Ｄ１２へ出力される光電場、Ｅ₂₁は光検出器Ｄ２１へ出力される光電場、Ｅ₂₂は光検出器Ｄ２２へ出力される光電場、α₁₁は光フィルタ２０２から検出器Ｄ１１までの振幅透過率、α₁₂は光フィルタ２０２から検出器Ｄ１２までの振幅透過率、α₂₁は光フィルタ２０２から検出器Ｄ２１までの振幅透過率、α₂₂は光フィルタ２０２から検出器Ｄ２２までの振幅透過率、ｔ₁は光フィルタ２０２から１ビット遅延干渉計２３０，２４０の短経路を経て光検出器Ｄ１１，Ｄ１２，Ｄ２１，Ｄ２２に到達するまでの時間、τは遅延干渉計２３０，２４０のそれぞれの遅延時間である。τは伝送信号のビット間隔でもある。

In the above equation, E ₁₁ is the optical field to be output to the photodetector D11, E ₁₂ is the optical field to be output to the photodetector D12, the optical field E ₂₁ is outputted to the photodetector D21, E ₂₂ is light optical field output to the detector D22, alpha ₁₁ is the amplitude transmittance of the optical filter 202 to the detector D11, alpha ₁₂ is the amplitude transmittance of the optical filter 202 to the detector D12, alpha ₂₁ is detected from the optical filter 202 amplitude transmittance to vessels D21, alpha ₂₂ is the amplitude transmittance of the optical filter 202 to the detector D22, t ₁ is the optical detector D11 via short path from the optical filter 202 1-bit delay interferometer 230, 240, D12 , D21 and D22, τ is the delay time of the delay interferometers 230 and 240, respectively. τ is also the bit interval of the transmission signal.

  Respective output lights from the delay interferometers 230 and 240 are input to each photodetector, and the light intensity is converted into an electrical signal and output. By the same derivation procedure as in the first embodiment, the output signal from each detector is expressed as follows.

上式において、Ｓ_１１，Ｓ_１２，Ｓ_２１，Ｓ_２２はそれぞれ検出器Ｄ１１，Ｄ１２，Ｄ２１，Ｄ２２からの出力信号、ηは光強度から電気信号への変換係数である。また、上式では、干渉光は主信号光に比べて十分弱いという仮定に基づく近似を用いた。

In the above equation, S ₁₁ , S ₁₂ , S ₂₁ , and S ₂₂ are output signals from the detectors D 11, D 12, D 21, and D ₂₂ , respectively, and η is a conversion coefficient from light intensity to an electrical signal. In the above equation, an approximation based on the assumption that the interference light is sufficiently weaker than the main signal light is used.

  The output signal from the detector D11 and the output signal from the detector D12 are differentially combined by the differential combining circuit 208. The output signal from the detector D21 and the output signal from the detector D22 are differentially combined by the differential combining circuit 213. Each differential composite output is expressed as follows.

ここで、Ｓ₁₀は検出器Ｄ１１とＤ１２からの差動合成出力、Ｓ₂₀は検出器Ｄ２１とＤ２２からの差動合成出力、ｔ₂は光検出器から差動合成回路２０８，２１３までの信号伝播時間である。また、│α₁₁│^２＝│α₁₂│^２、│α₂₁│^２＝│α₂₂│^２とし、さらに、
２η│α₁₁│^２＝ｋ₁₀、
２η│α₂₁│^２＝ｋ₂₀
とおいた。式（２１）において、第１項は所望の受信信号であり、（第２項＋第３項）は雑音光による揺らぎを表している。

Here, the signal S ₁₀ is differential combined output from the detector D11 and D12, S ₂₀ is differential combined output from the detector D21 and D22, t ₂ is from the photodetector to the differential combining circuit 208,213 Propagation time. Also, │α ₁₁ │ ² = │α ₁₂ │ ² , │α ₂₁ │ ² = │α ₂₂ │ ^2, and
2η│α ₁₁ │ ² = k ₁₀ ,
2η│α ₂₁ │ ² = k ₂₀
It was. In Expression (21), the first term is a desired received signal, and (second term + third term) represents fluctuation due to noise light.

  The differential composite output is input to signal processing circuits 209 and 215 for fluctuation suppression.

On the other hand, as in the first embodiment, the output light from the optical filter 202 partially branched by the optical splitter 203, the monitor signal from the photodetector M170 which branched light is entered S _m output Is done. The monitor signal _Sm is expressed by the following equation.

α_m、ｔ_m1、ｋ_mの意味は、式（８）と同様である。

Meaning of α _m, t _m1, k _m is the same as equation (8).

  Next, the monitor signal is input to signal processing circuits 209 and 215 for fluctuation suppression.

In the signal processing circuits 209 and 215, the monitor signal is first branched into two by the branching unit 181, and one delay is given to one by the delay τ circuit 182. Next, the two monitor signals are subtracted from the main signal S ₀ represented by the equation (21) by the subtraction circuit 184 as follows.

但し、ｔ₃は主信号系の差動合成回路２０8，２１３から引き算回路１８４までの信号伝播時間、ｔ_m2は光検出器M２１４から引き算回路１８４までの信号伝播時間である。式（２１）（２２）を式（２３）に代入すると、次式となる。

However, t ₃ is the signal propagation time from the main signal system differential synthesis circuits 208 and 213 to the subtraction circuit 184, and t _m2 is the signal propagation time from the photodetector M 214 to the subtraction circuit 184. Substituting equations (21) and (22) into equation (23) gives the following equation.

上式において、

In the above formula,

とすると、

Then,

となる。

It becomes.

  In Equation (25), the first term represents a desired received signal component, the second term represents a direct current component, and the third and subsequent terms represent fluctuation components due to noise light. Here, attention is paid to the signal fluctuation, and therefore, the third and subsequent terms will be considered below. First, the fluctuation component of Expression (25) is written as ΔS.

上式では、表記の簡略化のため、共通的な項であるＫＡ_ｓＡ_ｃは省略した。式（２６）において、（第１項＋第２項）は主信号系における揺らぎ、（第３項＋第４項）はモニタ信号系における揺らぎ、にそれぞれ対応する。

In the above equation, KA _s A _c, which is a common term, is omitted for the sake of simplicity. In Expression (26), (first term + second term) corresponds to fluctuation in the main signal system, and (third term + fourth term) corresponds to fluctuation in the monitor signal system.

By the way, what is received here is a DQPSK signal. In this case, the phase θ _s of the main signal light is expressed as follows.

但し、

However,

一方、θ_ｃ（ｔ）については、第１の実施の形態と同様に、信号速度よりは遅く変動する雑音光を想定し、

On the other hand, for θ _c (t), as in the first embodiment, assuming noise light that fluctuates slower than the signal speed,

とする。

And

  Hereinafter, assuming that the expressions (27) and (29) are satisfied, the fluctuation expression (26) will be considered. First, Expressions (27) and (29) are substituted into Expression (26).

但し、表記の簡略化のため、ｔ'≡ｔ−ｔ₀とした。上式は、さらに次のように展開される。

However, for simplification of description, t′≡t−t ₀ . The above formula is further expanded as follows.

上式は、△Ｓ₁と△Ｓ₂の揺らぎ方は同じであることを示している。そこで以下では、△Ｓ₁について述べていく。

The above formula shows that the fluctuations of ΔS ₁ and ΔS ₂ are the same. Therefore, ΔS ₁ will be described below.

  If there is no monitor signal,

となる。

It becomes.

  In the formulas (31a) and (32),

である。そこで、式（３１ａ）（３２）を使い、各△θ_sの値について、モニタ信号がある時とない時の△Ｓ_１を比較する。

It is. Therefore, using equations (31a) and (32), for each Δθ _s value, ΔS ₁ when there is a monitor signal and when there is no monitor signal are compared.

この他にも△θ_s（ｔ'）がπまたは３π／２の場合もあるが、△θ_s（ｔ'）と△θ_s（ｔ'−τ）は対称的であるので、上記８パターンについて考えれば十分である。

In addition, although Δθ _s (t ′) may be π or 3π / 2, Δθ _s (t ′) and Δθ _s (t′−τ) are symmetric, so the above eight patterns It is enough to think about.

As described above, the difference depending on the presence / absence of the monitor signal depends on the phase difference pattern, and the two cannot be quantitatively compared as they are. Therefore, the variance of ΔS ₁ for each case is calculated and the sum is compared. That is, for each phase pattern

を計算してその合計を比べる。なお、<>は（θ_s0−θ_c0）についての平均の意味である。

And compare the totals. Note that <> means an average for (θ _s0 −θ _c0 ).

となる。これにより、モニタ信号による信号処理を行った方が揺らぎが小さいことが示される。

It becomes. Thus, it is shown that the fluctuation is smaller when the signal processing using the monitor signal is performed.

  As described above, according to the present embodiment, it is possible to reduce reception signal fluctuation of DQPSK signal light due to noise light.

  The present invention is not limited to the above-described embodiment, and various modifications and applications can be made within the scope of the claims.

1, 11, 110 Optical amplifiers 2, 12, 120 Optical filters 3, 130, 203, 140, 205, 210 Optical splitters 4, 150, 207, 212 2 × 2 multiplexers 5, 16, 26, 160, 208 , 213 Differential combining circuit 13, 204 Optical coupler 15, 25, 101, 230, 240 1-bit delay interferometer 50 Optical branching means 60 Signal demodulating means 70 Monitor light intensity detecting means 80 Signal processing means 170, 214 Photodetector M
180, 209, 215 Signal processing circuit D1, D2, D21, D22 Photodetector

Claims (5)

An optical receiver for receiving a differential phase modulation signal,
An optical branching means for branching the input differential phase modulation signal into the main signal light and the monitor signal light; and a monitor light intensity for converting the light intensity of the monitor signal light branched by the optical branching means into an electrical signal and outputting it. Detection means;
A signal demodulating means for demodulating a phase modulation signal as an electric signal from the main signal light branched by the optical branching means;
A signal processing means for differentially combining the demodulated signal output from the signal demodulating means and the monitor signals of two adjacent bit slots output from the monitor light intensity detecting means;
With
The signal processing means includes
The demodulated signal output from the signal demodulating means is added by branching the monitor optical signal output from the monitor light intensity detecting means into two branches, adding a delay to one of them, and adding the other branched monitor optical signal. An optical receiver comprising means for performing signal processing subtracted from the optical receiver. 2. The optical receiver according to claim 1, wherein the differential phase modulation signal is binary differential phase shift keying signal light. The signal demodulating means in the optical receiver according to claim 2,
The signal light is branched into two, a time delay of one bit slot is given to one of the two branched signal lights, and the two branched lights are combined again by a 2 × 2 optical multiplexer, and the 2 × 2 optical multiplexer 3. An optical receiver according to claim 2, further comprising means for detecting the intensity of light output from each of the two output terminals, and differentially synthesizing and outputting the detected light intensities. 2. The optical receiver according to claim 1, wherein the differential phase modulation signal is quaternary differential phase shift keying signal light. The signal demodulating means in the optical receiver according to claim 4,
Means for branching signal light into signal light A and signal light B;
The branched signal light A is branched into two, a time delay of 1 bit slot and a delay phase φ1 are given to _one of the two branched signal lights, and the 2 branched signal light is again transmitted by the 2 × 2 optical multiplexer A. Means for combining, detecting the intensity of light output from the two output terminals of the optical multiplexer A, respectively, and differentially combining the detected light intensities for output;
The signal light B is branched into two, a time delay of one bit slot and a delay phase φ ₂ are given to one of the two branched signal lights, and the two-branched signal light is combined again by a 2 × 2 optical multiplexer B. Means for detecting the intensity of the light output from the two output terminals of the optical multiplexer B, differentially combining the detected light intensities, and outputting the differential intensity;
With
5. The optical receiver according to claim 4, wherein the delay phases [phi] ₁ and [phi] ₂ differ by [pi] / 2.

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