JP2008199884A - Unipolar or bipolar chopping converter having magnetically coupled two windings - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a circuit for reducing the cost of a chopping converter for supplying continuous voltage to a terminal of a load (Z). <P>SOLUTION: The circuit having the two windings (Lp, Ls) and a single magnetic core is proposed, thereby enabling reduction in the cost of the circuit and reduce its size. In that case, although two diode (D3, D4) needs to be attached to the circuit, these constituents are low cost and small in size. <P>COPYRIGHT: (C)2008,JPO&INPIT

Description

  The present invention is in quadrants (Is> 0, Vs> 0) and (Is <0, Vs <0) with magnetically coupled windings that can be configured in a regulated mode compatible with the current source or voltage source. And a unipolar or bipolar chopping converter that operates at zero output current or voltage. The present invention applies to any type of ground, marine or aviation equipment using this type of chopping converter, and in particular to a regulating automaton electromechanical actuator controller for a turbine engine.

  Control of electric actuators with RL type loads (series resistors and inductances) can be realized by applying a regulated voltage to the terminals of the actuator control coil or by a current source, this latter This solution is often inherently preferred in harsh environments as it allows the power used to control the accessory to be limited.

  Chopping current sources can traditionally use the load inductance as an energy storage element during the chopping operation and group them together between the current sources, resulting in chopping alternating positive and negative voltages across the load terminals Applying at a frequency, the transition between the two states is ideally considered instantaneous and the current source provides a continuous current and thus a continuous voltage to the terminals of the load, where the energy storage element for chopping is Located on the control card itself.

  A chopping current source using load inductance as an energy storage element has the advantage of having a simple control at first glance. They contain little or possibly no inductive elements, which leads to a certain saving in circuit dimensions. On the other hand, they have a certain number of drawbacks. They have a high dependence on the inductance value of the load, and the ability to control the instantaneous current at the switch of the current source is directly dependent on the charge inductance value. It is very difficult to make it resistant to short circuits (circuits) between the output terminals of the converter or between any output terminal and ground. In fact, if a short circuit occurs at the load, it is impossible to limit the instantaneous current unless additional components are added. Therefore, in practice, adding inductance to the converter output to limit the short-circuit current, adding protection and ultra-fast cut-off devices to limit the maximum short-circuit current, In order to manage the cut-off after detection, it is necessary to add a circuit for demagnetizing the output inductance and to make the interface (input filtering capacitor) large enough to withstand the short-circuit current. With respect to electromagnetic compatibility aspects (essentially conducted emissions), when high chopping frequencies are desired to limit the size of the passive components of the converter, especially when the load is controlled at the tip of a few meters of cable. These converters are difficult to meet aviation emission standards. As a result, the chopping frequency is reduced to typically less than 10 kHz, and the required output filter (shared mode and differential mode) plays an important role in assembly stability and has a non-negligible size. There is an obligation to do so. This type of chopping current source is limited to high power applications where low chopping frequency is not necessarily detrimental.

  For converters that supply continuous voltage to the terminals of the load, chopping no longer occurs in the load, but the current (or voltage) is regulated by the output of the chopping converter, including at least the inductance that stores all the energy transferred to the load A capacitor is added to smooth the output voltage. Thus, the output voltage is substantially continuous at the load terminals. Therefore, it is not so difficult to meet aviation standards for noise emitted during conduction. If a short circuit occurs at the load, the current in the converter remains naturally limited. Chopping frequencies above 100 kHz can be expected to be limited in nature by the efficiency of the converter and the performance of the gate control circuit consisting of switch elements.

  FIG. 1A is an electrical circuit diagram of a prior art chopping converter that supplies a continuous voltage to a load terminal. The circuit is supplied with a positive voltage Vp (eg, + 25V) and a negative voltage Vm (eg, −25V) with respect to ground. The chopping converter includes two elements T1 and T2, each including two windings magnetically coupled around the core. Windings of the same element T1 or T2 are wound in opposite directions, as indicated by the dots in FIG. 1A. The winding E1 of the element T1 has a first end connected to the voltage Vp via a diode D5 mounted in the opposite direction to the voltage Vp, and a second end connected to ground. . Winding E2 of element T1 has a first end connected to the first terminal of switch Q3 and a second terminal of switch Q3 connected to voltage Vp. The second end of the winding E2 is connected to the output terminal S1P of the circuit. The winding E3 of the element T2 has a first end connected to the voltage Vm via a diode D6 mounted in the opposite direction to the voltage Vm, and a second end connected to ground. . Winding E4 of element T2 has a first end connected to the first terminal of switch Q4 and a second terminal of switch Q4 connected to voltage Vm. The second end of the winding E4 is connected to the output terminal S1P of the circuit. A smoothing capacitor C1 is connected between the output unit S1P and the ground.

  The converter is converted to a current source by adding means for measuring the output current and appropriate adjustment means and a modulator. This is illustrated in FIG. 1B, where the load connected to the output of the converter is represented in the form of a resistor Rc and an inductance Lc connected in series. The output current is measured by the measuring means 1 which sends a representative signal to the first input of the adjusting means (ie equalizer) 2. The second input Ec of the adjusting means 2 receives a set value signal. The output signal of the adjusting means 2 is addressed to the input of the modulator 3 which sends the command signal SQ3 to the switch Q3 and sends the command signal SQ4 to the switch Q4.

Thus, the converter shown in FIG. 1A includes four windings and two magnetic cores, which results in a relatively high cost and a relatively large circuit size.
European Patent Application No. 0913919

  To save the cost and reduce the size of a chopping converter that supplies a continuous positive, negative or zero voltage to the load terminals, a circuit having two windings coupled on a single core is provided. Proposed in accordance with the present invention. In that case, it is necessary to add two diodes to the circuit, but these elements are inexpensive and small.

  A first subject matter of the present invention is a chopping converter that is supplied with a positive voltage and a negative voltage with respect to ground and that sends an output voltage between a first output terminal and a second output terminal. Includes two windings wound in opposite directions around the magnetic core, the number of turns of the second winding is greater than the number of turns of the first winding, and the first end of the first winding The first branch is connected to the midpoint of the first branch connecting the positive voltage to the negative voltage, and further includes first and second diodes mounted in opposite directions, the midpoint of the first branch Is located between the first diode and the second diode, the second end of the first winding is connected to ground, and the first end of the second winding is positive Connected to the midpoint of the second branch connecting the voltage to the negative voltage, and connecting the midpoint to the positive voltage A portion of the second branch that includes the first switch-forming means and the third diode arranged in series and directly attached to the positive voltage, and direct and inverse capability a second one directly connected to the negative voltage, in which a part of the second branch, which integrally forms a one-way switch with blocking capability, and whose middle point is connected to the negative voltage, is arranged in series The unidirectional switch including the switch forming means and the fourth diode and having the direct reverse blocking capability is integrally formed, and the second end of the second winding is connected to the output terminal.

  Advantageously, a smoothing capacitor is connected between the first output terminal of the converter and ground.

  Also advantageously, in the second branch connecting the positive voltage to the negative voltage, the series arrangement arranges the first and second switch forming means on the positive voltage side or the negative voltage side, respectively, and The third and fourth diodes are arranged on the intermediate point side of the second branch.

  The switch forming means may be selected from among MOS transistors, bipolar transistors and IGBT transistors, or other switches having bidirectional conduction capability and direct blocking capability.

  The converter may further comprise means for measuring its output voltage, the measuring means sending an output signal representative of the output voltage to the first input of the adjusting means, the second input of the adjusting means being set by the setting means The value signal is received, the adjusting means sends the supplied signal to the input of the modulator, the first output of the modulator sends the command signal to the first switch forming means, and the second of the modulator The output of which sends a command signal to the second switch forming means, whereby the converter is configured in the form of a voltage source.

  The converter may further comprise means for measuring its output current (is), said measuring means sending an output signal representative of the converter's output current to the first input of the adjusting means, and a second of the adjusting means. The input unit receives the set value signal, the adjusting unit sends the supplied signal to the input unit of the modulator, and the first output unit of the modulator sends the command signal to the first switch forming unit, The second output of the modulator sends a command signal to the second switch forming means, and the converter is configured in the form of a current source.

  The chopping converter according to the present invention can be installed in an electromechanical actuator controller, a regulating automaton, a turbine engine, or a ground, marine or aviation device.

  The chopping converter according to the present invention can operate according to the following method.

The first method is to allow a negative current to flow in the load during the operation cycle.
During the first part of the cycle, the first switch forming means is opened, the fourth diode is conducting, the second switch forming means is closed, and the first, second and third diodes A first step wherein the converter is blocked and the converter operates in a continuous or discontinuous mode;
Following the first step, during the second part of the cycle, the first and second switch forming means are opened, the second diode is conducting, and the first, third and fourth diodes A second step wherein the second part of the period does not end the period when the converter operates in discontinuous mode and ends the period when the converter operates in continuous mode; and
Following the second step, if the converter operates in discontinuous mode, the first and second switch forming means are opened during the third portion of the period ending at the end of the period, and the first, second A third step in which the second, third and fourth diodes are blocked.

The second method is to allow a positive current to flow in the load during the operating cycle.
During the first part of the cycle, the first switch forming means is closed, the third diode is conducting, the second switch forming means is opened, and the first, second and fourth diodes A first step wherein the converter is blocked and the converter operates in a continuous or discontinuous mode;
During the second part of the cycle, following the first step, the first diode is conducting, the first and second switch forming means are open, and the second, third and fourth diodes A second step wherein the second part of the period does not end the period when the converter operates in discontinuous mode and ends the period when the converter operates in continuous mode; and
Following the second step, if the converter operates in discontinuous mode, the first and second switch forming means are opened during the third portion of the period ending at the end of the period, and the first, second A third step in which the second, third and fourth diodes are blocked.

The third method is to allow a negative current to flow in the load during the operating cycle.
During the first part of the cycle, the first switch forming means is closed, the third diode is conducting, the second switch forming means is opened, and the first and fourth diodes are blocked. The first step is blocked when the absolute value of the voltage of the first output relative to ground is sufficiently low;
Following the first step, during the second part of the period, the first diode is conducting, the first and second switch forming means are open, and the second, third and fourth diodes A second step, wherein
Following the second step, during the third part of the cycle, the second switch forming means is closed, the fourth diode is conducting, the first switch forming means is opened, and the first, A third step in which the second and third diodes are blocked;
Following the third step, during the fourth part of the cycle ending at the end of the cycle, the second diode is conducting, the first and second switch forming means are opened, and the first, second The converter operates in a continuous mode, including a fourth step in which the third and fourth diodes are blocked.

The fourth method is to allow a positive current to flow in the load during the operating cycle.
During the first part of the cycle, the first switch forming means is closed, the third diode is conducting, the second switch forming means is opened, and the first, second and fourth diodes A first step, wherein
Following the first step, during the second part of the period, the first diode is conducting, the first and second switch forming means are open, and the second, third and fourth diodes A second step, wherein
Following the second step, during the third part of the cycle, the second switch forming means is closed, the fourth diode is conducting, the first switch forming means is opened, and the second and A third step, wherein the third diode is blocked and the first diode is blocked if the absolute value of the voltage of the first output relative to ground is sufficiently low;
Following the third step, during the fourth part of the cycle ending at the end of the cycle, the second diode is conducting, the first and second switch forming means are opened, and the first, second The converter operates in a continuous mode, including a fourth step in which the third and fourth diodes are blocked.

  The present invention is best understood and other advantages and specificities will become apparent by referring to the following description, which is provided by way of illustration only and is in no way limiting, and with reference to the accompanying drawings, in which: Will.

  FIG. 2 is an electrical circuit diagram of a chopping converter leading to the development of the present invention for supplying a continuous voltage to a load terminal. This converter adds means (direct or indirect) to measure the load current and appropriate equalizers and modulators as in the converter described in FIGS. 1A and 1B. Thus, it can be converted into a chopping current source. In the case of FIG. 1A, the circuit is supplied with a positive voltage Vp (eg, + 25V) and a negative voltage Vm (eg, −25V) with respect to ground. The circuit includes a transformer that includes three windings Lp, Ls1, and Ls2 forming an element and wound around a unique magnetic core. The winding direction is indicated by dots in FIG. Windings Ls1 and Ls2 are mounted in series to form the secondary side of the transformer forming the element, and their common point (the first end thereof) is connected to ground. The winding Lp constitutes the primary side of the transformer forming the element. The second end of the winding Ls1 is connected to the voltage Vp via a diode D1 attached in the opposite direction to the voltage Vp. A second end of the winding Ls2 is connected to the voltage Vm via a diode D2 attached in the opposite direction to the voltage Vm. Winding Lp has a first end connected to the cathode of diode D3 and the anode of diode D4. The second end of the winding Lp is connected to the output terminal SP of the circuit. The first terminal of the switch Q1 is connected to the anode of the diode D3, and the second terminal is connected to the voltage Vp. The first terminal of the switch Q2 is connected to the cathode of the diode D4, and the second terminal is connected to the voltage Vm. The smoothing capacitor Cs is connected between the output unit SP and the ground. The output part SM can be connected to mechanical ground directly or via a resistor, depending on the needs of the user.

  Switches Q1 and Q2 are advantageously N-channel or P-channel MOSFET transistor elements, depending on user needs. They can be replaced by other switches with bidirectional conduction capability and direct blocking capability.

  When Np is the number of turns of the winding Lp, Ns1 is the number of turns of the winding Ls1, and Ns2 is the number of turns of the winding Ls2, Np is larger than Ns1 and Ns2, for example, Ns1 = Ns2 = 0.75 Np.

FIG. 2 describes the following voltages:
The voltage vq1 at the terminal of Q1,
The voltage vq2 at the terminal of Q2,
The voltage vd1 at the terminal of D1,
Voltage vd2 at the terminal of D2,
Voltage vd3 at the terminal of D3,
D4 terminal voltage vd4,
The voltage vls1 at the terminal of Ls1,
The voltage vls2 at the terminal of Ls2,
Lp terminal voltage vlp and Cs terminal voltage vs, ie the converter output voltage.

FIG. 2 also describes the following currents:
Current ils1, which flows through winding Ls1,
Current ils2 flowing through the winding Ls2,
A current lip flowing through the winding Lp, and a current is flowing through the load Z of the converter, that is, an output current.

  The current source of FIG. 2 has certain advantages compared to the prior art current source shown in FIG. 1A. Reading the measurements performed on the assembly as shown in FIG. 2 allowed us to observe in an unexpected manner that the anode of diode D1 and the cathode of diode D2 were always at the same potential. Therefore, these two points are electrically connected and one of the secondary windings is omitted. This is illustrated in FIG. 3, where the remaining secondary winding is known as Ls, and the number of turns is such that Ns is less than the number of turns Np of the primary winding Lp. FIG. 3 shows a load Z connected to the output of the converter.

Next, the operation of the chopping converter will be described in accordance with commands (closed circuit, open circuit) sent to the switches Q1 and Q2 with reference to FIGS. 4A to 4N. In these figures, the current flowing in the circuit is indicated by a thick line. As can be seen, the converter according to the invention is a two-quadrant converter, ie (vs> 0, is> 0) and (vs <0, is <0).
It is.

  4A-4F show a single transistor Q1 or Q2 (forming a switch) when the output current is positive (is> 0) or when the output current is negative (is <0). Is related to the operation mode in which.

  4A to 4C relate to an operation mode in which the output current “is” is negative during the operation cycle (from t = 0 to t = T).

FIG. 4A shows the first step of the operating period between instants t = 0 and t = t ₁ (where t ₁ <T). The circuit can operate in continuous and discontinuous modes. During this step, the circuit commands are as follows:
Q2 and D4 conduct,
Q1, D1, D2 and D3 are blocked.

FIG. 4B shows the second step of the operating period between the instants t = t ₁ and t = t ₂ . The circuit can operate in continuous mode (in this case t ₂ = T) or in discontinuous mode. During this step, the circuit commands are as follows:
D2 conducts,
Q1, Q2, D1, D3 and D4 are blocked.

FIG. 4C shows the third step of the operating period between t = t ₂ and t = T, uniquely as a discontinuous mode. During this step, the circuit commands are as follows:
Q1, Q2, D1, D2, D3 and D4 are blocked,
The current “is” flowing in the load is supplied by the energy stored in the capacitor Cs.

  FIG. 5A shows a chronogram of an operating period corresponding to the operating mode illustrated by FIGS. 4A to 4C as a discontinuous mode and thus comprising three steps.

  FIG. 5B shows a chronogram of an operating period corresponding to the operating mode illustrated by FIGS. 4A and 4B as a continuous mode and thus comprising two steps.

  4D to 4F relate to an operation mode in which the output current “is” is positive during the operation period (from t = 0 to t = T).

FIG. 4D shows the first step of the operating cycle between instants t = 0 and t = t ₁ (where t ₁ <T). The circuit can operate in continuous and discontinuous modes. During this step, the circuit commands are as follows:
Q1 and D3 conduct,
Q2, D1, D2 and D4 are blocked.

FIG. 4E shows the second step of the operating cycle between the instants t = t ₁ and t = t ₂ . The circuit can operate in continuous mode (in this case t ₂ = T) or in discontinuous mode. During this step, the circuit commands are as follows:
D1 conducts,
Q1, Q2, D2, D3 and D4 are blocked.

FIG. 4F shows the third step of the operating period between t = t ₂ and t = T for the uniquely discontinuous mode. During this step, the circuit commands are as follows:
Q1, Q2, D1, D2, D3 and D4 are blocked,
The current “is” flowing in the load is supplied by the energy stored in the capacitor Cs.

  FIG. 5C shows a chronogram during the operating period corresponding to the operating mode shown by FIGS. 4D to 4F in the case of discontinuous mode and thus comprising three steps.

  FIG. 5D shows a chronogram during the operating period corresponding to the operating mode illustrated by FIGS. 4D and 4E in the case of continuous mode and thus comprising two steps.

  FIGS. 4G to 4N show operating modes in which two transistors Q1 and Q2 (forming a switch) conduct when the output current is negative (is <0) and the output current is positive (is> 0). Related to. The depicted motion is in continuous mode.

  4G to 4J relate to an operation mode in which the output current “is” is negative during the operation period (from t = 0 to t = T).

FIG. 4G shows the first step of the operating period between the instants t = 0 and t = t ₁ . During this step, the control of the circuit is as follows:
Q1 and D3 conduct,
Q2, D1 and D4 are blocked,
D2 is blocked when the absolute value of the voltage at the output SP with respect to ground is sufficiently low.

FIG. 4H shows the second step of the operating cycle between the instants t = t ₁ and t = t ₂ . During this step, the circuit commands are as follows:
D1 conducts,
Q1, Q2, D2, D3 and D4 are blocked.

FIG. 4I shows the third step of the operating cycle between the instants t = t ₂ and t = t ₃ . During this step, the circuit commands are as follows:
Q2 and D4 conduct,
Q1, D1, D2 and D3 are blocked.

FIG. 4J shows the fourth step of the operating period between the instants t = t ₃ and t = T. During this step, the circuit commands are as follows:
D2 conducts,
Q1, Q2, D1, D3 and D4 are blocked.

  4K to 4N relate to an operation mode in which the output current “is” is positive during the operation cycle (from t = 0 to t = T).

FIG. 4K shows the first step of the operating cycle between the instants t = 0 and t = t ₁ . During this step, the circuit commands are as follows:
Q1 and D3 conduct,
Q2, D1, D2 and D4 are blocked.

FIG. 4L shows the second step of the operating cycle between the instants t = t ₁ and t = t ₂ . During this step, the circuit commands are as follows:
D1 conducts,
Q1, Q2, D2, D3 and D4 are blocked.

FIG. 4M shows the third step of the operating period between the instants t = t ₂ and t = t ₃ . During this step, the circuit commands are as follows:
Q2 and D4 conduct,
Q1, D2 and D3 are blocked,
D1 is blocked when the absolute value of the voltage at the output SP with respect to the ground is sufficiently low.

FIG. 4N shows the fourth step of the operating period between the instants t = t ₃ and t = T. During this step, the circuit commands are as follows:
D2 conducts,
Q1, Q2, D1, D3 and D4 are blocked.

  FIG. 5E shows a chronogram during the operating period corresponding to the operating mode shown by FIGS. 4G to 4J and thus including four steps.

  FIG. 5F shows a chronogram during the operating period corresponding to the operating mode illustrated by FIGS. 4K to 4N and thus also including four steps.

  6A adds a converter 11 according to the invention with means 11 for measuring the voltage difference between the outputs SP and SM, a suitable equalizer 12 for receiving the set value Ec, and a suitable modulator 13. Thus, the principle of use as a voltage source is shown. The output of the modulator 13 supplies the command voltages SQ1 and SQ2 of the transistors Q1 and Q2.

  FIG. 6B shows the converter according to the invention by adding means 21 for measuring the converter output current “is”, a suitable equalizer 22 for receiving the setpoint Ec, and a suitable modulator 23. The principle used as a source is shown. The output of the modulator 23 supplies the command voltages SQ1 and SQ2 of the transistors Q1 and Q2.

It is an electric circuit diagram of a conventional chopping converter that supplies a continuous voltage to a terminal of a load. FIG. 1B is an electrical schematic of the converter of FIG. 1A used as a chopping current source by adding output current measuring means and appropriate equalizers and modulators. FIG. 2 is an electrical circuit diagram of a chopping converter that supplies a continuous voltage to a load terminal, leading to the development of the present invention. 1 is an electrical circuit diagram of a chopping converter for supplying a continuous voltage to a load terminal according to the present invention; FIG. It is a figure which shows the operation mode of this invention. It is a figure which shows the operation mode of this invention. It is a figure which shows the operation mode of this invention. It is a figure which shows the operation mode of this invention. It is a figure which shows the operation mode of this invention. It is a figure which shows the operation mode of this invention. It is a figure which shows the operation mode of this invention. It is a figure which shows the operation mode of this invention. It is a figure which shows the operation mode of this invention. It is a figure which shows the operation mode of this invention. It is a figure which shows the operation mode of this invention. It is a figure which shows the operation mode of this invention. It is a figure which shows the operation mode of this invention. It is a figure which shows the operation mode of this invention. 4C is a chronogram corresponding to the operation modes shown in FIGS. 4A to 4C. 4B is a chronogram corresponding to the operation mode shown in FIGS. 4A to 4B. FIG. FIG. 5 is a chronogram corresponding to the operation modes shown in FIGS. 4D to 4F. 4D is a chronogram corresponding to the operating modes shown in FIGS. 4D to 4E. 4C is a chronogram corresponding to the operation modes shown in FIGS. 4G to 4J. FIG. 4D is a chronogram corresponding to the operation modes shown in FIGS. 4K to 4N. 1 is a diagram illustrating the principle of using a converter according to the present invention as a voltage source. 1 is a diagram illustrating the principle of using a converter according to the present invention as a current source. FIG.

Explanation of symbols

DESCRIPTION OF SYMBOLS 1 Measuring means 2, 12, 22 Adjusting means 3, 13, 23 Modulator 11 Differential voltage measuring means 21 Output current measuring means

Claims (14)

  A positive voltage (Vp) and a negative voltage (Vm) are supplied to the ground, and an output voltage is sent between the first output terminal (SP) and the second output terminal (SM). The output terminal (SM) is a chopping converter connected directly to ground or via a resistor, and includes two windings (Ls, Lp) wound in opposite directions around the magnetic core, The number of turns of the winding (Lp) is larger than the number of turns of the first winding (Ls), and the first end of the first winding (Ls) converts the positive voltage (Vp) to the negative voltage ( Vm) further including a first diode (D1) and a second diode (D2) connected in the opposite direction and connected to the midpoint of the first branch connected to Vm), the midpoint of the first branch Is located between the first diode (D1) and the second diode (D2), The second end of the winding (Ls) is connected to ground, and the first end of the second winding (Lp) connects the positive voltage (Vp) to the negative voltage (Vm). A portion of the second branch connected to the midpoint of the second branch and connecting the midpoint to the positive voltage (Vp) is directly attached to the positive voltage (Vp) arranged in series A first switch forming means (Q1) and a third diode (D3) and having a direct reverse blocking capability are integrally formed, and an intermediate point thereof is connected to a negative voltage (Vm) A portion of the second branch that includes the second switch forming means (Q2) and the fourth diode (D4) arranged in series, directly attached to the negative voltage (Vm), and directly A one-way switch having reverse blocking capability is integrally formed, and the second winding (Lp) End of 2 is connected to the output terminal (S), chopping converter.   The chopping converter according to claim 1, wherein the smoothing capacitor (Cs) is connected between the first output terminal (SP) of the converter and ground.   In the second branch in which the positive voltage (Vp) is connected to the negative voltage (Vm), the series arrangement is configured so that the first (Q1) and second (Q2) switch forming means are connected to the positive voltage side or the negative voltage, respectively. 3. The chopping converter according to claim 1, wherein the chopping converter is arranged on the side and the third (D3) and fourth (D4) diodes are arranged on an intermediate point side of the second branch.   The first (Q1) and second (Q2) switch forming means are selected from among MOS transistors, bipolar transistors and IGBT transistors, or other switches having bidirectional conduction capability and direct blocking capability. 4. The chopping converter according to any one of items 1 to 3.   Further comprising means (11) for measuring the output voltage of the converter, this measuring means sends an output signal representing the output voltage to the first input of the adjusting means (12), and the second means of the adjusting means (12). The input unit receives the set value signal, the adjusting means (12) sends the supplied signal to the input unit of the modulator (13), and the first output unit of the modulator (13) receives the command signal. (SQ1) is sent to the first switch forming means (Q1), and the second output of the modulator (13) sends the command signal (SQ2) to the second switch forming means (Q2), whereby the voltage The chopping converter according to claim 1, wherein the chopping converter is configured in the form of a source.   It further comprises means (21) for measuring the output current (is) of the converter, and this measuring means sends an output signal representing the output current of the converter to the first input part of the adjusting means (22), and the adjusting means ( 22) receives the set value signal, the adjusting means (22) sends the supplied signal to the input of the modulator (23), and the first output of the modulator (23). Sends the command signal (SQ1) to the first switch forming means (Q1), and the second output part of the modulator (23) sends the command signal (SQ2) to the second switch forming means (Q2). 5. A chopping converter as claimed in any one of the preceding claims, configured in the form of a feed and thereby a current source.   An electromechanical actuator control device including the chopping converter according to any one of claims 1 to 6.   An adjustment automaton including the chopping converter according to any one of claims 1 to 6.   A ground, marine or aviation device comprising the chopping converter according to any one of claims 1-6.   A turbine engine comprising the chopping converter according to any one of claims 1 to 6. The converter is supplied with a positive voltage (Vp) and a negative voltage (Vm) with respect to the ground, and the converter is connected between the first output terminal (SP) and the second output terminal (SM). A method for operating a chopping converter according to any one of claims 1 to 6, wherein an output current (is) is sent in (Z), wherein a negative current is generated in the load (Z) during an operating cycle. To shed
During the first part of the cycle, the first switch forming means (Q1) is opened, the fourth diode (D4) is conducting, the second switch forming means (Q2) is closed, and the first A first step in which the 1 (D1), second (D2) and third (D3) diodes are blocked and the converter operates in continuous or discontinuous mode;
Following the first step, during the second part of the cycle, the first (Q1) and second (Q2) switch forming means are opened, the second diode (D2) is conducting, and the first step The first (D1), third (D3) and fourth (D4) diodes are blocked and this second part of the period does not terminate the period when the converter operates in discontinuous mode, and the converter is continuous A second step of ending the cycle when operating in mode;
Following the second step, if the converter operates in discontinuous mode, the first (Q1) and second (Q2) switch forming means are opened during the third part of the period ending at the end of the period. And a third step, wherein the first (D1), second (D2), third (D3) and fourth (D4) diodes are blocked. In a load (Z) supplied with a positive voltage (Vp) and a negative voltage (Vm) with respect to ground and connected between the first output terminal (SP) and the second output terminal (SM). A method for operating a chopping converter according to any one of claims 1 to 6 for delivering an output current (is), in order to pass a positive current in a load (Z) during an operating period,
During the first part of the cycle, the first switch forming means (Q1) is closed, the third diode (D3) is conducting, the second switch forming means (Q2) is opened, and the first A first step in which 1 (D1), 2nd (D2) and 4th (D4) diodes are blocked and the converter operates in continuous or discontinuous mode;
Following the first step, during the second part of the cycle, the first diode (D1) is conducting, the first (Q1) and second (Q2) switch forming means are opened, and the first step The second (D2), third (D3) and fourth (D4) diodes are blocked and this second part of the period does not terminate the period when the converter operates in discontinuous mode, and the converter is continuous A second step of ending the cycle when operating in mode;
Following the second step, if the converter operates in discontinuous mode, the first (Q1) and second (Q2) switch forming means are opened during the third part of the period ending at the end of the period. A third step, wherein the first (D1), second (D2), third (D3) and fourth (D4) diodes are blocked. In a load (Z) supplied with a positive voltage (Vp) and a negative voltage (Vm) with respect to ground and connected between the first output terminal (SP) and the second output terminal (SM). The method for operating a chopping converter according to any one of claims 1 to 6, wherein the output current (is) is sent out, in order to pass a negative current in the load (Z) during an operation cycle.
During the first part of the cycle, the first switch forming means (Q1) is closed, the third diode (D3) is conducting, the second switch forming means (Q2) is opened, and the first The first (D1) and fourth (D4) diodes are blocked and the second diode (D2) is blocked if the absolute value of the voltage of the first output (SP) with respect to ground is sufficiently low. One step,
Following the first step, during the second part of the cycle, the first diode (D1) is conducting, the first (Q1) and second (Q2) switch forming means are opened, and the first step A second step in which 2 (D2), 3rd (D3) and 4th (D4) diodes are blocked;
Following the second step, during the third part of the cycle, the second switch forming means (Q2) is closed, the fourth diode (D4) is conducting, and the first switch forming means (Q1) ) Is opened and the first (D1), second (D2) and third (D3) diodes are blocked;
Following the third step, the second diode (D2) is conducting during the fourth part of the period ending at the end of the period, and the first (Q1) and second (Q2) switch forming means And the first (D1), third (D3) and fourth (D4) diodes are blocked, and a fourth step, wherein the converter operates in a continuous mode. The converter is supplied with a positive voltage (Vp) and a negative voltage (Vm) with respect to the ground, and the converter is connected between the first output terminal (SP) and the second output terminal (SM). A method for operating a chopping converter according to any one of claims 1 to 6, wherein an output current (is) is sent in (Z), wherein a positive current is generated in the load (Z) during the operating period. To shed
During the first part of the cycle, the first switch forming means (Q1) is closed, the third diode (D3) is conducting, the second switch forming means (Q2) is opened, and the first A first step in which 1 (D1), 2nd (D2) and 4th (D4) diodes are blocked;
Following the first step, during the second part of the cycle, the first diode (D1) is conducting, the first (Q1) and second (Q2) switch forming means are opened, and the first step A second step in which 2 (D2), 3rd (D3) and 4th (D4) diodes are blocked;
Following the second step, during the third part of the cycle, the second switch forming means (Q2) is closed, the fourth diode (D4) is conducting, and the first switch forming means (Q1) ) Is open and the second (D2) and third (D3) diodes are blocked, the first diode (D1) has a sufficient absolute value for the voltage of the first output (SP) with respect to ground A third step, which is blocked if low,
Following the third step, the second diode (D2) is conducting during the fourth part of the period ending at the end of the period, and the first (Q1) and second (Q2) switch forming means And the first (D1), third (D3) and fourth (D4) diodes are blocked, and a fourth step, wherein the converter operates in a continuous mode.

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