JP2008118176A - Radio transmitter, radio receiver, radio communication system and electronic apparatus - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a radio transmitter capable of superior frequency conversion of inputted signal into a signal suitable for an output system, and to provide a radio receiver, a radio communication system and an electronic apparatus. <P>SOLUTION: In the radio transmitter, an IF up-conversion section 200 is provided with variable amplifiers 221 and 231 provided for each of inputted signals (modulated wave signal 1a and a modulated wave signal 2a) of a plurality of systems, and adjusting the signal level of each of the inputted signals of the plurality of systems, prior to up-converting the inputted signals of the plurality of systems. <P>COPYRIGHT: (C)2008,JPO&INPIT

Description

  The present invention relates to a wireless transmission device, a wireless reception device, a wireless communication system, and an electronic device, and more particularly to a device that wirelessly communicates broadcast waves in the microwave and millimeter wave frequency bands.

  In recent years, various broadband wireless communication systems have been proposed with an increase in information communication capacity. Among them, millimeter-wave wireless communication is used particularly in the field of broadcasting and communication. Millimeter waves can narrow the beam sharply, so that interference between satellites arranged in orbit and on the ground can be prevented, while radio waves can be transmitted evenly to specific areas. In addition, the millimeter wave band shown here shows the frequency band also including a microwave band.

  As a conventional millimeter wave band wireless communication system, for example, Patent Document 1 discloses a wireless communication system including a wireless transmitter and a wireless receiver. Therefore, the configuration and operation of the conventional radio transmitter and radio receiver will be described with reference to FIG.

  FIG. 9 is a schematic diagram showing the configuration of a conventional transmitter 1000 and receiver 1500.

  The transmitter 1000 includes an input unit 1100, a first up-conversion unit 1200, a second up-conversion unit 1300, and a transmission antenna 1400.

  The first up-conversion unit 1200 is a part that converts an input modulated wave signal to an intermediate frequency, and includes a frequency mixer 1201, a filter 1202, a power combiner 1203, an amplifier 1204, a power distributor 1205, and a reference signal source 1206. , And an attenuator 1207.

  The first IF signal IF1 is input to the first up-conversion unit 1200. This signal IF1 is a modulated wave signal modulated by, for example, an orthogonal multicarrier modulation scheme (OFDM modulation scheme).

  The frequency mixer 1201 multiplies the input signal IF1 and the first LO signal (fLO1) output from the reference signal source 1206.

  Next, the filter 1202 provided immediately after the frequency mixer 1201 mainly extracts only the signal component output from the first up-conversion unit 1200. Here, it is assumed that the filter 1202 selects and passes the upper-band signal (fRF1) from the output signal of the frequency mixer 1201.

  On the other hand, the power distributor 1205 distributes a part of the signal (fLO1) output from the reference signal source 1206. The attenuator 1207 adjusts the level of the distributed signal. The signal (fLO1) output from the attenuator 1207 is combined with the signal (fRF1) by the power combiner 1203.

  As a result, an intermediate frequency multiplexed signal of the signal (fRF1) converted from the original modulated wave signal to the intermediate frequency signal and the signal (fLO1) serving as the reference signal is generated. The intermediate frequency multiplexed signal is amplified by the amplifier 1204, and the amplified intermediate frequency multiplexed signal is output to the second up-conversion unit 1300 as the second IF signal IF2 (fLO1, fRF1).

  The second up-conversion unit 1300 is a unit that converts the frequency of the input signal IF2 into a millimeter wave band, and includes a mixer 1301, a filter 1302, an amplifier 1303, and a local oscillator 1304.

  When the signal IF2 output from the first up-conversion unit 1200 is input to the second up-conversion unit 1300, the mixer 1301 generates an intermediate frequency multiplexed wave signal including the signal (fRF1) and the signal (fLO1). The second LO signal (fLO2) output from the local oscillator 1304 is multiplied and up-converted to the millimeter wave band.

  Next, a filter 1302 provided immediately after the mixer 1301 allows the radio multiplexed signal having only a desired frequency to pass through the up-converted radio multiplexed signal. As a result, a radio multi-wave signal including a radio modulation signal component (fRF1 + fLO2) and a radio reference signal component (fLO1 + fLO2) is generated. This radio multiwave signal is amplified by amplifier 1303, and the amplified radio multiwave signal is output to transmitting antenna 1400.

  Then, a radio multi-wave signal 2000 including a radio reference signal component (fLO1 + fLO2) and a radio modulation signal component (fRF1 + fLO2) is transmitted from the transmission antenna 1400, that is, the transmitter 1000.

  Next, the receiver 1500 that receives a signal transmitted from the transmitter 1000 will be described.

  The receiver 1500 includes a reception antenna 1600, a first down-conversion unit 1700, and a second down-conversion unit 1800. The receiver 1500 receives the signal transmitted from the transmitter 1000, and down-converts the received signal into the original modulated wave signal (IF1).

  The receiving antenna 1600 receives the radio multi-wave signal 2000 composed of the reference signal component (fLO1 + fLO2) and the radio modulation signal component (fRF1 + fLO2) transmitted from the transmitting antenna 1400 of the transmitter 1000.

  The first down-conversion unit 1700 is a part that converts an input radio multi-wave signal into an intermediate frequency signal, and includes a filter 1701, an amplifier 1702, a mixer 1703, an amplifier 1704, and a local oscillator 1705.

  A filter 1701 passes the required signal. Then, the amplifier 1702 amplifies the passed signal. Next, the mixer 1703 performs a first frequency conversion on the signal (fLO2) from the local oscillator 1705. That is, the reference signal component (fLO1 + fLO2) and the radio modulation signal component (fRF1 + fLO2) are down-converted into the second IF signal IF2 (that is, fLO1, fRF1) that is an intermediate frequency multiplexed wave signal.

  As a result, the second IF signal IF2 (fLO1, fRF1) is generated. The second IF signal is amplified by the amplifier 1704, and the amplified signal IF2 is output to the second down-conversion unit 1800.

  The second down-conversion unit 1800 is a part that converts the frequency of the input second IF signal IF2 into the first IF signal IF1, and includes a distributor 1801, a filter 1802, a filter 1803, a mixer 1804, an amplifier 1805, and An output unit 1806 is provided.

  When the second IF signal IF2 is input to the second down-conversion unit 1800, the signal is distributed by the distributor 1801. One of the distributed signals is input to the mixer 1804 via a filter 1802 through which only the signal (fRF1) can pass. The other signal is amplified by an amplifier 1805 via a filter 1803 through which only the signal (fLO1) can pass, and then input to the mixer 1804.

  The mixer 1804 multiplies the signal (fRF1) and the signal (fLO1). Thereby, the signal (fRF1) is down-converted. That is, the first IF signal IF1 is demodulated.

As described above, the receiver 1500 demodulates the first IF signal IF1. The first IF signal IF1 is the original first IF signal IF1 in the transmitter 1000.
JP 2003-258655 A (published on September 12, 2003)

  However, the conventional transmitter 1000 and receiver 1500 have the following problems.

  First, in the transmitter 1000, even if there are a plurality of input modulated wave signals, the first up-conversion unit 1200 converts the frequency of the plurality of modulated wave signals at once as it is. Therefore, there is a problem when the modulated wave signal extends over the octave band.

  More specifically, for example, the broadcast wave signal (fIF1) is composed of a plurality of channel signals (signal components in fIF1 are f1, f2,...) Each composed of video / audio. In a plurality of broadcast wave signals (for example, fIF1a, fIF1b,...), Each signal has a wide bandwidth ranging from several hundred MHz to 1 GHz octave band.

  For this reason, if the first up-conversion unit 1200 up-converts the frequency of the broadcast wave signal (fIF1) as it is, second-order distortion characteristics are generated in the output signal of the frequency mixer 1201 along with the up-conversion. The second-order distortion characteristics include, for example, 2 × f1 and 2 × f2 second-order harmonic components and f1-f2 and f1 + f2 distortion components.

  Therefore, in the transmitter 1000 and further in the wireless communication system, it is difficult to perform good frequency conversion and ensure good transmission characteristics even when a plurality of signals having a wide bandwidth are input. Has a problem.

  Secondly, in the receiver 1500, one of the signals distributed by the distributor 1801 in the second down-conversion unit 1800 is input to the mixer 1804 via the filter 1802 through which only the signal (fRF1) can pass. At the same time, the other signal is amplified by the amplifier 1805 via the filter 1803 through which only the signal (fLO1) can pass, and then input to the mixer 1804.

  With the above configuration, it is difficult to realize a filter that can pass only the signal (fRF1) when the frequencies of the signal (fRF1) and the signal (fLO1) are close to each other. Furthermore, it is difficult to realize a filter that can pass only the signal (fLO1). Therefore, the receiver 1500 and further the radio communication system have a problem that it is difficult to perform frequency conversion while ensuring signal quality and bandwidth.

  Third, in the receiver 1500, when there are a plurality of signals to be frequency down-converted to the original modulated wave signal, a plurality of mixers are required, and a plurality of local oscillators are required. At this time, if one reference signal is shared and used as a local oscillation signal to be input to each mixer, the local oscillation terminals of each mixer are connected to each other, and signal leakage from each mixer causes leakage to other mixers. It flows in. For this reason, there is a problem that good frequency conversion is difficult.

  In order to prevent signal leakage from each mixer, a plurality of amplifiers or isolators are required to separate the local oscillation terminals from each other. Therefore, there are problems that the number of parts is increased, the board size is increased, and the power consumption is increased.

  The present invention has been made in view of the above-described conventional problems, and an object of the present invention is to provide a radio transmission apparatus and radio reception capable of satisfactorily frequency-converting a signal suitable for a method of outputting an input signal. To provide an apparatus, a wireless communication system, and an electronic device.

  In order to solve the above-described problem, a wireless transmission device of the present invention includes a first up-conversion unit that up-converts a plurality of series of input signals using a reference signal, and a signal output from the first up-conversion unit. Multiplex signal generating means for generating a multiplexed signal by combining power with the reference signal, and a second signal for up-converting the multiplexed signal output from the multiplexed signal generating means to approximately the microwave band or more using a local transmission signal An up-conversion means for transmitting a radio multiplexed signal output from the second up-conversion means, wherein the first up-conversion means is provided for each input signal of the plurality of sequences, Provided with input signal level adjusting means for adjusting the signal level of the plurality of input signals before up-converting the plurality of input signals. It is characterized in that.

  According to the above configuration, even when a plurality of series of signals composed of signals having various signal levels according to the reception environment are input, the input signal level adjusting means is provided for each of the plurality of series of signals. By providing, it is possible to adjust the signal level of each signal and adjust the signal level ratio to an optimum ratio.

  As a result, the multiplexed signal generating means can generate an optimally adjusted multiplexed signal. Therefore, in the second up-conversion means, it is possible to up-convert the optimally adjusted multiplexed signal above the substantially microwave band, so that the input signal is transmitted as a radio signal above the approximately microwave band. It is possible to satisfactorily perform frequency conversion into a suitable radio multiplexed signal.

  In the radio transmission apparatus of the present invention, the first up-conversion means is provided for each of the plurality of series of input signals, and third up-conversion is performed using the reference signal for each of the plurality of series of input signals. Preferably, the multiplexed signal generating means generates power by combining the signals output from the third up-converting means and the reference signal to generate the multiplexed signal.

  According to said structure, by providing said 3rd up-conversion means for every input signal of several series, according to the bandwidth of the frequency of each signal, each signal is up-converted separately. As a result, it is possible to suppress the second-order distortion or the like generated in the output signal when up-converting a plurality of series of input signals and up-convert.

  Therefore, the multiplexed signal generated from each signal with reduced distortion and the reference signal is output to the second up-conversion means. Therefore, since it becomes possible to up-convert a multiplex signal adjusted more optimally to approximately the microwave band or higher, a radio multiplex signal suitable as a radio signal to be transmitted at approximately the microwave band or higher, It becomes possible to perform frequency conversion better.

  In order to solve the above-described problem, the wireless receiver of the present invention includes a first down-converting unit that down-converts a wireless multiplexed signal including a received reference signal to an intermediate frequency using a local oscillation signal, and the first down-converting unit. And a second down-conversion means for down-converting the intermediate frequency multiplexed signal output from the means to a frequency to be demodulated using the reference signal, and outputting a demodulated signal output from the second up-conversion means The second down-conversion unit includes a first distribution unit that distributes the intermediate frequency multiplexed signal output from the first down-conversion unit to a plurality of paths according to the number of signals to be demodulated, and the first down-conversion unit. The first path, which is one of the plurality of paths distributed by the distributing means, includes the reference signal from the intermediate frequency multiplexed signal. A first extraction means for extracting one intermediate frequency signal; a second distribution means for distributing a signal output from the first extraction means to a second path and a third path; and the reference to the second path. A third down-converting means for down-converting the first intermediate frequency signal including the signal to a frequency to be demodulated using the reference signal, and the reference signal from the first intermediate frequency signal including the reference signal to the third path. A second extraction means for extracting only the second intermediate frequency signal, which is provided for each of paths other than the first path distributed by the first distribution means and which is demodulated from the intermediate frequency multiplexed signal. 3 extraction means and a reference that is provided for each second intermediate frequency signal output from the third extraction means and that is output from the second extraction means to the second intermediate frequency signal output from the third extraction means. And a second intermediate frequency signal including the reference signal output from the power combining means, provided for each of the second intermediate frequency signals including the reference signal output from the power combining means. And fourth down-converting means for down-converting to a frequency to be demodulated using the reference signal.

  According to the above configuration, after the first intermediate frequency signal including the reference signal is extracted by the first extraction unit, the first intermediate frequency signal including the reference signal is extracted by the third down-conversion unit. Directly downconverted. Therefore, even if the frequency of the first intermediate frequency signal to be demodulated and the frequency of the reference signal are close to each other, it can be down-converted to the frequency to be demodulated, and a demodulated signal that has been successfully frequency-converted is generated. It becomes possible.

  Further, only the reference signal is extracted by the second extraction means. Thereby, since the extracted reference signal passes through the first extraction means and the second extraction means, it is possible to extract a high-purity reference signal with less unnecessary wave components.

  On the other hand, by providing the third extraction means, a second intermediate frequency signal that is a signal to be demodulated from the intermediate frequency multiplexed signal is extracted. Then, the power combining means combines the reference signal with the second intermediate frequency signal output from the third extraction means, and outputs it to the fourth down-conversion means, thereby demodulating the second intermediate frequency signal. It is possible to generate a demodulated signal that is down-converted to a frequency and is well frequency-converted.

  As a result, the received radio multiplexed signal can be frequency-converted to each demodulated signal corresponding to the frequency, so that the input signal can be demodulated to the original frequency, and the device on which the radio receiving device is mounted. It becomes possible to perform better frequency conversion to the demodulated signal used.

  Moreover, in the second down-conversion means, the first distribution means distributes the intermediate frequency multiplexed signal to a plurality of paths according to the number of signals to be demodulated, so that the first extraction means demodulates from the intermediate frequency multiplexed signal. And a third extraction means provided for each path other than the first path distributed by the first distribution means becomes a signal to be demodulated from the intermediate frequency multiplexed signal. By extracting each of the two intermediate frequency signals, the signals to be demodulated are individually separated and down-converted by the third down-conversion means and the fourth down-conversion means, respectively. Therefore, it is possible to reduce the second-order distortion of the output signals of the third down-conversion means and the fourth down-conversion means, and it is possible to ensure good transmission characteristics.

  In the radio reception apparatus of the present invention, it is preferable that the second extraction means is composed of one amplifier and one narrow band filter.

  According to the above configuration, the reference signal can be extracted with a small and simple configuration. The third path is connected to the third down-converting means via the second distributing means and the fourth down-converting means via the power coupling means. However, since the second extraction means is composed of one amplifier and one narrow band filter, it is possible to realize unidirectional and narrow band simultaneously on the third path. As a result, it is possible to reduce the leakage of the input signals of the third down-conversion unit and the fourth down-conversion unit, and it is possible to perform good frequency conversion. Furthermore, since the second extraction means is composed of one amplifier and one narrow band filter, it is possible to reduce power consumption.

  In the radio reception apparatus of the present invention, it is preferable that the first distribution unit has isolation between distribution ports, and the power coupling unit has isolation between coupling ports.

  According to the above configuration, since each of the means has isolation between the distribution port and the coupling port, even if one amplifier enters the line loop formed by the distribution and coupling, the amplifier Is smaller than the sum of the isolation of the first distribution means and the isolation of the power coupling means, the line loop can be a negative feedback loop, which can prevent unnecessary and parasitic oscillations. It becomes possible.

  In the radio reception apparatus of the present invention, it is preferable that the first distribution unit is a Wilkinson type power divider, and the power coupling unit is a Wilkinson type power combiner.

  According to the above configuration, since the first distribution unit and the power coupling unit can be provided with the isolation by the absorption resistance, it is easy to configure the line loop with a wider band and a lumped constant line. It becomes possible to configure in a small size.

  Therefore, since the line length of the line loop can be further reduced, the latent oscillation frequency region when the line loop is formed can be further increased. Therefore, the loop gain formed by the amplifier and the line loop can be reduced. Furthermore, since the first distribution unit and the power coupling unit have isolation over a wide band, the potential loop gain region can be reduced.

  In the wireless receiver of the present invention, the sum of the isolation between the distribution ports and the isolation between the coupling ports is larger than the sum of the gains of the amplifiers in the intermediate frequency band of the reception system. Is preferred.

  According to the above configuration, the total sum of the isolation is prevented from becoming smaller than the sum of the amplifiers at the operating frequency. That is, since negative gain is present in the line loop, it is possible to prevent positive feedback, so that it is possible to realize a good characteristic in which unnecessary and parasitic oscillations are suppressed.

  In the wireless reception apparatus of the present invention, the second down-conversion unit includes a first amplification unit that amplifies and adjusts the signal output from the first down-conversion unit before the first distribution unit. Is preferred.

  According to the above configuration, by providing the first amplifying unit, it is possible to enhance the frequency conversion gain accompanying the frequency conversion in the first down-converting unit and suppress the influence of noise from the subsequent stage. . Furthermore, not only to reduce the influence of frequency mismatch of input / output impedance, but also to suppress the sudden increase in frequency conversion loss accompanying the frequency conversion from the first amplifying means to the subsequent stage, and to realize characteristics with excellent sensitivity characteristics. Is possible.

  In the radio receiving apparatus of the present invention, it is preferable that the first amplifying unit is an amplifier configured by an auto gain control circuit or a self-bias circuit.

  In the wireless receiver, when the wireless transmission distance is short, the output signal of the first amplifying unit provided in the second down-converting unit may be easily distorted due to excessive input. On the other hand, when the transmission distance is increased, the transmitted transmission signal is attenuated, and the signal level may be rapidly decreased. Therefore, according to the above configuration, the second down-conversion means uses the intermediate frequency multiplexed signal whose signal level has been adjusted, so that the transmission quality can be kept more constant with respect to the transmission distance. As a result, it is possible to widen the dynamic range as a wireless receiver.

  In the radio reception apparatus of the present invention, it is preferable that the third down-conversion means and the fourth down-conversion means are frequency mixers configured by microwave transistors driven by self-bias.

  In the wireless receiver, when the wireless transmission distance is short, the output signals of the third down-converter and the fourth down-converter provided in the second down-converter may be easily distorted due to excessive input. On the other hand, when the transmission distance is increased, the transmitted transmission signal is attenuated, and the signal level may be rapidly decreased.

  Therefore, according to the above configuration, for example, the third down-conversion means and the fourth down-conversion means are configured by the base injection mixer, so that even a smaller reference signal transmitted is driven as a local oscillation signal of the frequency mixer. It becomes possible. Therefore, it is possible to configure the third down-conversion means and the fourth down-conversion means with higher linearity than a normal diode mixer.

  Further, by using a self-bias circuit, the current flowing through the frequency mixer (for example, the collector / emitter of the microwave transistor) can be made constant. Therefore, frequency conversion with a wide dynamic range is possible, and transmission quality can be kept more constant with respect to the wireless transmission distance.

  In particular, by using together with the auto gain control circuit or the self-bias circuit of the first amplifying means, it becomes possible to widen the dynamic range as a wireless receiver, and the transmission signal quality becomes more constant with respect to the transmission distance. It becomes possible to do.

  In order to solve the above-described problem, the wireless communication system of the present invention is configured by the wireless transmission device and the wireless reception device.

  According to the above configuration, a radio transmission apparatus that transmits a radio multiplexed signal that has been frequency-converted well so as to be suitable as a radio signal, and a radio multiplexing signal that is transmitted from the radio transmission apparatus are received and frequency-converted satisfactorily Thus, it is possible to realize a wireless communication system that is configured by a wireless reception device that generates a demodulated signal and that supports broadband wireless transmission in a substantially microwave or millimeter wave region.

  According to another aspect of the present invention, there is provided an electronic device including the wireless reception device or the wireless communication system, wherein the electronic device includes the wireless reception device or the wireless communication system. A radio receiving apparatus is characterized in that a demodulated signal generated by frequency down-conversion is recorded, output, or both recorded and output.

  According to the above configuration, since the wireless receiving device is provided, the wireless communication system and the wireless receiving device itself are compatible with broadband wireless transmission such as a substantially microwave and millimeter wave region. There is no need to perform digital signal processing. Further, in the wireless reception device or the wireless communication system, since up-conversion and down-conversion are performed based on one reference signal, the frequency of the local oscillator in the wireless transmission device or the wireless reception device is changed. There is no need for an automatic frequency controller that adjusts the deviation. Therefore, the electronic device can be reduced in size and cost.

  Further, in the electronic device having the above-described configuration, in addition to simplifying the wiring by directly recording, outputting, or recording and outputting the demodulated signal by the wireless reception device, for example, the demodulated signal is a broadcast signal. In the case of multi-channel broadcasting, since multi-channel broadcasting signals can be transmitted wirelessly at a time, a plurality of electronic devices can display and record different channels independently.

  As described above, in the wireless transmission device of the present invention, the first up-conversion means is provided for each input signal of a plurality of sequences, and before up-converting the input signals of the plurality of sequences, An input signal level adjusting means for adjusting the signal level is provided.

  As a result, the multiplex signal generation means can adjust the signal level by the input signal level adjustment means, and can generate an optimally adjusted multiplex signal from the up-converted signal and the reference signal. Therefore, in the second up-conversion means, it is possible to up-convert the optimally adjusted multiplexed signal above the substantially microwave band, so that the input signal is transmitted as a radio signal above the approximately microwave band. There is an effect that the frequency can be satisfactorily converted into a suitable radio multiplexed signal.

  Further, in the radio reception apparatus of the present invention, the second down-conversion unit includes a first distribution unit that distributes the intermediate frequency multiplexed signal output from the first down-conversion unit to a plurality of paths according to the number of signals to be demodulated. First extracting means for extracting a first intermediate frequency signal including a reference signal from the intermediate frequency multiplexed signal to a first path which is one of a plurality of paths distributed by the first distributing means; A second distribution unit that distributes the signal output from the first extraction unit to a second path and a third path; a first intermediate frequency signal that includes the reference signal in the second path; Third down-converting means for down-converting to a frequency to be demodulated, second extracting means for extracting only the reference signal from the first intermediate frequency signal including the reference signal in the third path, and the first distribution A third extraction unit that is provided for each path other than the first path distributed by the stage and extracts a second intermediate frequency signal that is a signal to be demodulated from the intermediate frequency multiplexed signal; and is output from the third extraction unit A power combining unit provided for each second intermediate frequency signal, for power-coupling a reference signal output from the second extracting unit with a second intermediate frequency signal output from the third extracting unit; and the power combining unit The second intermediate frequency signal including the reference signal output from the power combining means is downconverted to a frequency to be demodulated using the reference signal. And a fourth down-conversion means.

  As a result, it is possible to frequency-convert the received radio multiplexed signal into each demodulated signal corresponding to the frequency, so that the input signal is demodulated to the original frequency band and the radio receiver is mounted. In this case, the demodulated signal used in the above can be converted into a better frequency.

  In order to solve the above problems, the wireless communication system of the present invention includes the wireless transmission device and the wireless reception device.

  Therefore, a radio transmitting apparatus that transmits a radio multiplexed signal that has been frequency-converted well so as to be suitable as a radio signal, and a radio multiplexed signal that is transmitted from the radio transmitting apparatus are received, and the demodulated signal is converted to a satisfactory frequency. There is an effect that it is possible to realize a wireless communication system that is configured by a wireless reception device to be generated and that supports broadband wireless transmission such as a substantially microwave or millimeter wave region.

  According to another aspect of the present invention, there is provided an electronic device including the wireless reception device or the wireless communication system, wherein the electronic device includes the wireless reception device or the wireless communication system. A radio receiving apparatus that records and outputs a demodulated signal generated by down-converting the frequency performs both recording and output.

  As a result, the wireless communication system and the wireless receiver itself are accompanied by digital signal processing such as compression / decompression and frequency fluctuations of the local oscillator because the wireless communication system and the wireless reception device itself support broadband wireless transmission such as substantially microwave and millimeter wave regions. There is no need for an automatic frequency controller that adjusts the frequency deviation. As a result, the electronic device can be reduced in size and cost.

  Further, in the electronic device having the above-described configuration, in addition to simplifying the wiring by directly recording, outputting, or recording and outputting the demodulated signal by the wireless reception device, for example, the demodulated signal is a broadcast signal. With such multi-channel broadcasting, it is possible to wirelessly transmit a multi-channel broadcast signal at a time, so that a plurality of electronic devices can display and record different channels independently.

  An embodiment of the present invention will be described below with reference to the drawings.

  Hereinafter, as an embodiment of the present invention, a radio communication device, a radio reception device, a radio communication system, and an electronic device having a radio communication function in the millimeter wave band will be described, but the invention is not limited to the millimeter wave band. In addition, the millimeter wave band shown here shows a frequency band including a microwave band. The frequency is in the range of approximately 3 GHz to 300 GHz.

[Embodiment 1]
In the present embodiment, a wireless transmission device 100 will be described as an example of a millimeter-wave band wireless transmission device.

  FIG. 1 is a schematic diagram illustrating a configuration example of a wireless transmission device 100 according to the present embodiment.

  As shown in FIG. 1, radio transmitting apparatus 100 according to the present embodiment includes an input unit 101, an intermediate frequency (hereinafter referred to as IF) up-conversion unit 200 (first up-conversion means), and a millimeter-wave frequency up-conversion unit 300. (Second up-conversion means) and a transmission antenna 400 are provided. That is, in the radio transmission apparatus 100, the signal input from the input unit 101 is first frequency converted by the IF up-conversion unit 200 and second frequency converted by the millimeter wave frequency up-conversion unit 300, and the transmission antenna 400 is output.

  The input unit 101 is an input terminal that inputs a modulated wave signal input to the wireless transmission device 100. The signal input to the input unit 101 is input to the IF up-conversion unit 200 as it is. The signal input to the input unit 101 will be described in detail later. Further, in the wireless transmission device 100, one input unit 101 is provided as a configuration for inputting one series of signals. However, the configuration is not limited thereto, and two input terminals are provided as a configuration for inputting two sequences of signals. Also good.

  The IF up-conversion unit 200 is a part that up-converts the input modulated wave signal from the frequency band of the modulated wave signal to the frequency band of the IF signal. The IF up-conversion unit 200 includes a duplexer 210, an IF up-converter 220 (third up-conversion unit), an IF up-converter 230 (third up-conversion unit), a reference signal adding unit 240, and a power combiner 250 ( Multiple signal generation means).

  Here, in the IF up-conversion unit 200, frequency up-conversion to the frequency band of the IF signal means that modulation that has been input to a frequency that is larger than the frequency of the input signal and smaller than the millimeter-wave band frequency to be transmitted. This means raising the frequency of the wave signal. That is, an IF modulated wave signal may be input. In this case, the IF signal is up-converted to an IF higher than the IF of the input modulated wave signal.

  The duplexer 210 demultiplexes the modulated wave signal input via the input unit 101 according to the frequency band. For example, broadcast radio waves are taken out separately for each broadcast that needs them. The duplexer 210 outputs the demultiplexed signal to the IF up converter 220 and the IF up converter 230, respectively.

  The IF up-converter 220 includes a variable amplifier 221 (input signal level adjusting means), a mixer 222, a bandpass filter 223, and an amplifier 224.

  The variable amplifier 221 receives the modulated wave signal output from the duplexer 210, amplifies the signal, and outputs the amplified signal to the mixer 222. The variable amplifier 221 has a variable gain function or a self-bias function. Therefore, the variable amplifier 221 can adjust the level of the signal when the modulated wave signal is amplified.

  The mixer 222 multiplies a signal output from the variable amplifier 221 and a reference signal output from a reference signal source 241 to be described later, thereby generating an IF signal whose frequency is up-converted to IF. Further, the mixer 222 outputs the IF signal subjected to frequency up-conversion to the bandpass filter 223.

  The band pass filter 223 suppresses unnecessary waves from the signal output from the mixer 222 and allows only a signal having a desired frequency to pass. For the desired frequency, the frequency used as the IF may be determined according to the design.

  The amplifier 224 amplifies the signal that has been reduced by passing through the band-pass filter 223, and outputs the amplified signal to the power combiner 250.

  IF up-converter 230 inputs a modulated wave signal having a frequency band different from the signal input to IF up-converter 220. The IF up-converter 230 includes a variable amplifier 231 (input signal level adjusting means), a mixer 232, a bandpass filter 233, and an amplifier 234. The functions are the variable amplifier 221, the mixer 222, and the bandpass filter 223. , And the amplifier 224, respectively.

  The reference signal adding unit 240 includes a reference signal source 241, a variable amplifier 242, and an output unit 243.

  The reference signal source 241 oscillates a reference signal at a predetermined frequency (fLO1) and outputs the oscillated reference signal to the mixer 222 and the mixer 232. That is, the mixer 222 and the mixer 232 share the reference signal source 241 and use the same reference signal. The reference signal source 241 also outputs the reference signal to the variable amplifier 242.

  The variable amplifier 242 receives the signal output from the reference signal source 241, amplifies the signal, and outputs the amplified signal to the output unit 243. The variable amplifier 242 has a gain variable function or a self-bias function. Therefore, the variable amplifier 242 can adjust the level of the signal when amplifying the reference signal.

  The output unit 243 outputs the signal output from the variable amplifier 242 to the power combiner 250 together with the signal output from the IF up converter 230. Further, the output unit 243 outputs only the signal output from the variable amplifier 242 to the local oscillator 304.

  The power combiner 250 combines the signals output from the IF up converter 220, the IF up converter 230, and the reference signal adding unit 240. Specifically, the power combiner 250 combines the signals that have been amplified and level-adjusted by the amplifiers 224 and 234 together with the reference signal that has been level-adjusted by the variable amplifier 242. As a result, the power combiner 250 generates a series of IF multiplexed signals obtained by combining the signals, and outputs the IF multiplexed signals to the millimeter wave frequency up-conversion unit 300.

  The millimeter wave frequency up-conversion unit 300 is a part that performs frequency up-conversion of the IF multiplexed signal frequency up-converted to IF by the IF up-conversion unit 200 from the IF frequency band to the millimeter wave frequency band. The millimeter wave frequency up-conversion unit 300 includes a mixer 301, a band pass filter 302, an amplifier 303, and a local oscillator 304.

  The mixer 301 multiplies the signal output from the power combiner 250 and the local oscillation signal output from the local oscillator 304, thereby generating a radio multiplexed signal that is up-converted to a millimeter wave frequency. Further, the mixer 301 outputs the radio multiplexed signal whose frequency has been up-converted to the bandpass filter 302.

  The band pass filter 302 suppresses unnecessary waves among the signals output from the mixer 301 and allows only signals having a desired frequency to pass therethrough. The desired frequency may be determined according to the design frequency used in the millimeter wave band wireless communication.

  The amplifier 303 amplifies the signal that has passed through the bandpass filter 302 and outputs the amplified signal to the transmission antenna 400.

  The local oscillator 304 oscillates a local oscillation signal with a predetermined frequency (fLO2), and outputs the oscillated local oscillation signal to the mixer 301. The local oscillator 304 is preferably configured with a frequency multiplier. As a result, a local oscillation signal obtained by multiplying the frequency of the reference signal 3b can be output.

  That is, the local oscillator 304 is driven by inputting the reference signal oscillated from the reference signal source 241. Therefore, the local oscillator 304 does not need to directly generate a millimeter wave oscillation signal. Therefore, it is possible to use an oscillator that can stably oscillate at a low frequency, and it is possible to configure the wireless transmission device 100 that is stable and highly reliable.

The transmitting antenna 400 transmits a signal output from the amplifier 303, that is, a radio multiplexed signal frequency-converted to the millimeter wave band. Thus, the transmission signal is output from the wireless transmission device 100 as a signal suitable for millimeter wave band wireless communication. ,
Next, with reference to FIGS. 1 to 3, a description will be given of signal transition in the wireless transmission device 100 from when a modulated wave signal is input until the signal is frequency-converted and transmitted.

  First, the configuration of an antenna wiring that receives a modulated wave signal input to the wireless transmission device 100 will be described with reference to FIG.

  The antenna wiring includes a terrestrial broadcast antenna 51 that receives a terrestrial broadcast signal, a satellite broadcast antenna 52 that receives a satellite broadcast signal, an amplifier 53, an amplifier 54, and a power combiner 55. ing. As a result, a modulated wave signal for terrestrial broadcasting and a modulated wave signal for satellite broadcasting are input to the wireless transmission device 100.

  Here, it is assumed that modulated wave signal A (frequency is set to fIF1a) is received by terrestrial broadcast antenna 51, and modulated wave signal B (frequency is set to fIF1b) is received by satellite broadcast antenna 52. Further, the frequency band of terrestrial broadcasting is approximately 470 MHz to 770 MHz, and the IF frequency band of satellite broadcasting is approximately 1.0 GHz to 2.1 GHz.

  The received signals at each antenna are signals of a plurality of channels (for example, signal components are f1, f2,...). The modulated wave signal A is not limited to terrestrial broadcasts, but may be other broadcasts, for example, signal waves of a cable TV or the like.

  The power levels of modulated wave signal A from terrestrial broadcast antenna 51 and modulated wave signal B from satellite broadcast antenna 52 are adjusted by amplifiers 53 and 54, respectively.

  Thereafter, the signals output from the amplifiers 53 and 54 are combined by the power combiner 55 to generate a series of modulated wave signals C (fIF1a, fIF1a). Then, the modulated wave signal C is output to the wireless transmission device 100.

  Here, since each frequency band is different between the frequency band of the terrestrial broadcast and the IF frequency band of the satellite broadcast, the modulated wave signal A and the modulated wave signal B are synthesized by the power combiner 55 as they are. For example, if the modulated wave signal A and the modulated wave signal B are signals of a plurality of satellite broadcast waves, one of the signals is converted into a different frequency band. After that, power combining may be performed by the power combiner 55 and output to the wireless transmission device 100 as a series of signals.

  As described above, a series of modulated wave signals C are input to the wireless transmission device 100 according to the configuration of the antenna wiring. Note that the configuration of the antenna wiring is a configuration of an existing antenna wiring. Therefore, the signal levels of the modulated wave signal A and the modulated wave signal B are not adjusted to the optimum levels for the microwave / millimeter wave radio system, as will be described later.

  Next, signal transition in the wireless transmission device 100 will be described.

  The modulated wave signal C input to the wireless transmission device 100 is first input to the duplexer 210. In the demultiplexer 210, the modulated wave signal C (fIF1a, fIF1a) is again demultiplexed into two series of modulated wave signal 1a (fIF1a) and modulated wave signal 2a (fIF1b).

  FIG. 2A shows a frequency arrangement in which the modulated wave signal 1a and the modulated wave signal 2a are shown on the frequency axis. FIG. 2A shows that the frequency increases as it goes to the right along the axis. Moreover, the arrows shown in the modulated wave signal 1a and the modulated wave signal 2a indicate the arrangement direction of the signals. Furthermore, the dotted lines drawn three vertically along the width of the modulated wave signal 1a and the modulated wave signal 2a indicate that the frequency fIF1a of the modulated wave signal 1a and the frequency fIF1b of the modulated wave signal 2a do not overlap. Is shown.

  Modulated wave signal 1 a is output to IF up-converter 220. On the other hand, modulated wave signal 2 a is output to IF up-converter 230. Next, modulated wave signal 1a and modulated wave signal 2a are adjusted to optimum levels for the radio transmission system by IF up-converter 220 and IF up-converter 230, respectively.

  In the IF up-converter 220, the level of the input modulated wave signal 1a is adjusted by the variable amplifier 221 so that the signal level becomes a predetermined level. For example, when the signal level of terrestrial broadcasting is extremely high, it is possible to lower the amplification level and adjust the level so that the signal level is substantially equal to the signal level of satellite broadcasting waves.

  Furthermore, since there is an optimum required CN (carrier-to-noise) ratio for demodulation after reception depending on the bandwidth and modulation method of each channel of the modulated wave signals 1a and 2a, the signals of the modulated wave signals 1a and 2a It also includes that the level needs to be adjusted.

  Thereafter, in the mixer 222, the modulated wave signal 1a is multiplied with the reference signal 3a (fLO1), and the frequency is up-converted to IF. Then, an unnecessary wave of the IF signal whose frequency is up-converted is suppressed by the band pass filter 223.

  FIG. 2 shows the frequency arrangement of the IF signal 1b on the frequency axis when the frequency is up-converted by the mixer 222 and only the desired signal is filtered by the band-pass filter 223, and the frequency characteristics of the band-pass filter 223. Shown in (b). In the present embodiment, the IF signal frequency up-converted to the IF is selected as a lower sideband signal with respect to the reference signal 3a. Therefore, the frequency of the IF signal 1b is configured as shown below. The

IF signal 1b: fLO1-fIF1a
Thereafter, the IF signal 1 b output from the bandpass filter 223 is amplified by the amplifier 224 and output to the power combiner 250.

  On the other hand, in the IF up-converter 230, the level of the input modulated wave signal 2a is adjusted by the variable amplifier 231 so that the signal level becomes a predetermined level. Thereafter, in the mixer 232, the modulated wave signal 2a is multiplied with the reference signal 3a, and the frequency is up-converted to IF. Then, an unnecessary wave is suppressed in the band-pass filter 233 from the IF signal that has been frequency up-converted.

  FIG. 2 shows the frequency arrangement of the IF signal 2b on the frequency axis when the frequency is up-converted by the mixer 232 and only the desired signal is filtered by the band-pass filter 233, and the frequency characteristics of the band-pass filter 233. Shown in (b). In the present embodiment, the IF signal frequency up-converted to the IF is selected as a lower sideband signal with respect to the reference signal 3a. Therefore, the frequency of the IF signal 2b is configured as shown below. The

IF signal 2b: fLO1-fIF1b
Thereafter, IF signal 2 b output from bandpass filter 233 is amplified by amplifier 234 and output to power combiner 250.

  The reference signal 3a (fLO1) output from the reference signal adding unit 240 is preferably set to a frequency band of 4 GHz to 10 and several GHz. As a result, it is possible to use a broadband signal in which the frequency regions of the modulated wave signal 1a (fIF1a) and the modulated wave signal 2a (fIF1b) are 0.2 GHz to 2.5 GHz.

  In the reference signal adding unit 240, the reference signal 3 a oscillated from the reference signal source 241 is also output to the variable amplifier 242. The level of the reference signal 3a is adjusted by the variable amplifier 242 as necessary, and is output to the power combiner 250 as the reference signal 3b.

  In power combiner 250, IF signal 1b, IF signal 2b, and reference signal 3a are combined to form a series of IF multiplexed signals 4a. FIG. 3A shows a frequency arrangement in which the IF multiplex signal 4a is shown on the frequency axis. The IF multiplexed signal 4a is output to the millimeter wave frequency up-conversion unit 300.

  In the millimeter wave frequency up-conversion unit 300, the IF multiplexed signal 4a is frequency up-converted to the millimeter wave band. Specifically, the up-conversion of the IF multiplex signal 4 a to the millimeter wave band is frequency up-converted by the mixer 301 using the local oscillation signal (fLO 2) oscillated from the local oscillator 304.

  In the radio multiplexed signal whose frequency is up-converted, unnecessary waves are suppressed by the bandpass filter 302. Thereafter, the radio multiplexed signal 5 a output from the bandpass filter 302 is amplified by the amplifier 303 and output to the transmission antenna 400.

  FIG. 3B shows a frequency arrangement in which the radio multiplexed signal 5a output to the transmission antenna 400 at this time is shown on the frequency axis. In the present embodiment, at the time of frequency up-conversion to a millimeter wave, the bandpass filter 302 passes the upper side band to configure the radio multiplexed signal 5a.

  The radio multiplexed signal 5a is composed of a radio signal 1c, a radio signal 2c, and a radio reference signal 3c described below. The radio signal 1c, the radio signal 2c, and the radio reference signal 3c are signals when the IF signal 1b, the IF signal 2b, and the reference signal 3b are frequency up-converted to the millimeter wave band.

Wireless signal 1c: (fLO1 + fLO2) −fIF1a
Wireless signal 2c: (fLO1 + fLO2) −fIF1b
Wireless reference signal 3c: fLO1 + fLO2
Thereafter, the radio multiplexed signal 5a is radiated from the transmitting antenna 400.

  As described above, the radio multiplex signal 5a frequency-converted to be suitable for millimeter wave band radio communication is transmitted from the radio transmission device 100.

  In radio transmitting apparatus 100 of the present embodiment, modulated wave signal C is input as a signal composed of various signal levels according to the reception environment, but is distributed by providing variable amplifiers 221 and 231. It is possible to adjust the signal levels of the modulated wave signal 1a and the modulated wave signal 2a so as to become predetermined levels.

  Specifically, the modulated wave signal 1a and the modulated wave signal 2a are signals obtained by receiving the modulated wave signal A with the terrestrial broadcast antenna 51 and the modulated wave signal B with the satellite broadcast antenna 52. The signal level of the modulated wave signal 2a and the signal level of the modulated wave signal 2a are various signal levels depending on the reception environment. Therefore, by providing the variable amplifiers 221 and 231, it is possible to adjust the signal levels of the modulated wave signal 1 a and the modulated wave signal 2 a and to adjust the signal level ratio to an optimum ratio.

  The modulated wave signal 1a and the modulated wave signal 2a are IF upconverted, and then the reference signal 3b adjusted by the variable amplifier 242 is added by the power combiner 250, and the IF multiplexed signal 4a is converted into a millimeter wave frequency upconverter. 300 is output. Thereafter, the IF multiplexed signal 4a is up-converted to a wireless multiplexed signal 5a and transmitted.

  Here, the radio multiplexed signal 5a of the radio transmitting apparatus 100 has an upper limit by the radio wave law. Therefore, an optimum ratio exists in the power ratio between the reference signal and the transmission signal at a limited transmission signal output level. Therefore, the power ratio between the transmission signal (that is, the IF signal 1b and the IF signal 2b) and the reference signal 3b can be adjusted to the optimum power ratio by adjusting the level of the reference signal 3a with the variable amplifier 242. Become.

  For example, in radio transmitting apparatus 100 according to the present embodiment, IF multiplexed signal 4a including modulated wave signal 1a and modulated wave signal 2a is generated, but either modulated wave signal 1a or modulated wave signal 2a is generated. There is also a case of one-way transmission.

  Therefore, by providing the variable amplifier 242, it is possible to adjust the level of the reference signal 3a according to the total bandwidth of the input signal wave (for example, in the case of only fIF1a + fIF1b or fIF1a).

  As a result, the IF multiplexed signal 4a can be generated optimally. Therefore, it is possible to frequency-convert the optimally adjusted IF multiplex signal 4a into the millimeter wave radio frequency band, so that the input modulated wave signal C is suitable as a transmission signal for radio transmission in the millimeter wave band. It is possible to satisfactorily frequency convert the radio multiplexed signal 5a.

  Further, in radio transmitting apparatus 100 according to the present embodiment, modulated wave signal A and modulated wave signal B are broadband signals each having a total sum of broadcast wave signals ranging from several hundred MHz to 1 GHz. For this reason, frequency conversion is not performed at once, and the signals are divided into two frequency band signals (modulated wave signal 1a and modulated wave signal 2a), and mixer 222 of IF up converter 220 and mixer 232 of IF up converter 230 Each up-converts.

  Therefore, when a series of modulated wave signals C are collectively up-converted to an intermediate frequency, second-order distortion or the like generated in the output signal is suppressed, and the input modulated wave signal 1a and modulated wave signal 2a are, for example, , F1, f2,... Second-order distortion characteristics such as 2xf1, 2xf2, 3xf1, 3xf2 harmonic characteristics and f1-f2, f1 + f2 distortion components can be reduced. It is possible to ensure good transmission characteristics.

  In the wireless transmission device 100, the case where the modulated wave signal 1a and the modulated wave signal 2a are included in one series of modulated wave signals C has been described. A signal may be included. In this case, for example, a configuration similar to that of the IF up-converter 230 is added, the modulated wave signal demultiplexed from the demultiplexer 210 is input, and the up-converted IF signal is output to the power combiner 250. .

[Embodiment 2]
The following will describe another embodiment of the present invention with reference to the drawings. Configurations other than those described in the present embodiment are the same as those in the first embodiment. For convenience of explanation, members having the same functions as those shown in the drawings of the first embodiment are given the same reference numerals, and explanation thereof is omitted.

  In the present embodiment, a wireless reception device 500 will be described as an example of a millimeter-wave band wireless reception device.

  FIG. 4 is a schematic diagram illustrating a configuration example of the wireless reception device 500 of the present embodiment.

  As shown in FIG. 4, radio receiving apparatus 500 according to the present embodiment includes reception antenna 600, IF down-conversion unit 700 (first down-conversion unit), modulated signal frequency down-conversion unit 800 (second down-conversion unit), An output unit 501 and an output unit 502 are provided. That is, in radio receiving apparatus 500, the signal input from receiving antenna 600 is first frequency converted by IF down-conversion unit 700, second frequency converted by modulated signal frequency down-conversion unit 800, and output unit 501 and the output part 502 are output.

  Receiving antenna 600 receives a radio multiplexed signal including a reference signal transmitted from any radio transmitting apparatus having a radio communication function in the millimeter wave band, and outputs the received signal to IF down-conversion unit 700.

  The IF down-conversion unit 700 is a part that performs frequency down-conversion of the received radio multiplexed signal from the millimeter wave frequency band to the IF frequency band. The IF down conversion unit 700 includes an amplifier 701, a band pass filter 702, a frequency mixer 703, and a local oscillator 704.

  The amplifier 701 amplifies the signal output from the receiving antenna 600 and outputs the amplified signal to the bandpass filter 702.

  The bandpass filter 702 removes unnecessary noise added by communication or the like, filters only a desired signal, and outputs it to the frequency mixer 703.

  The frequency mixer 703 multiplies the signal output from the bandpass filter 702 and the local oscillation signal oscillated from the local oscillator 704, thereby generating an IF multiplexed signal down-converted to IF. Further, the frequency mixer 703 outputs the generated IF multiplexed signal to the modulation signal frequency down-conversion unit 800.

  Here, as an example, the frequency mixer 703 is desirably an N-order harmonic mixer (N is a natural number of 2) such as an even harmonic mixer. Thereby, the local oscillation frequency of the local oscillator 704 can be set to 1 / N.

  Specifically, the local oscillation frequency of the local oscillator 704 can be halved by making the frequency mixer 703 a second-order harmonic mixer. Therefore, the radio receiving device 500 with high frequency stability can be easily manufactured by easy mounting such as wire bonding.

  The local oscillator 704 oscillates a local oscillation signal at a predetermined frequency (referred to as fLO3) and outputs it to the frequency mixer 703.

  Modulation signal frequency down-conversion section 800 is a section for frequency down-converting the IF multiplexed signal IF down-converted by IF down-conversion section 700 from the IF frequency band to the frequency band of the original modulation wave signal in the wireless transmission device. It is. As a result, the received radio multiplexed signal is returned to the original modulated wave signals input to the radio transmission apparatus. Hereinafter, the returned modulated wave signal is referred to as a demodulated signal.

  As shown in FIG. 4, the modulation signal frequency down-conversion unit 800 includes a first filter 801, a variable amplifier 802 (first amplification means), a first power distributor 803 (first distribution means), and a second filter. 804 (first extraction means), third filter 805 (third extraction means), second power distributor 806 (second distribution means), fourth filter 807 (second extraction means), amplifier 808, power A coupler 809 (power coupling unit), a frequency mixer 810 (third down-conversion unit), a low-frequency filter 811, a frequency mixer 812 (fourth down-conversion unit), and a low-frequency filter 813 are provided.

  The first filter 801 receives the signal output from the IF down-conversion unit 700, specifically the frequency mixer 703, suppresses unnecessary waves, and passes only a signal having a desired frequency. The desired frequency is determined according to the frequency including the frequency of the IF that generates the demodulated signal by down-conversion and the frequency of the reference signal.

  The variable amplifier 802 amplifies the signal that has passed through the first filter 801 and outputs the amplified signal to the first power distributor 803. The variable amplifier 802 is configured by an auto gain control circuit or a self-bias circuit. Therefore, the variable amplifier 802 can adjust the signal level of the IF multiplexed signal when amplifying the IF multiplexed signal.

  The first power distributor 803 distributes the input signal to two paths. That is, signals distributed to the second filter 804 and the third filter 805 are output.

  The second filter 804 receives the signal output from the first power distributor 803, suppresses unnecessary waves, and passes only a signal having a desired frequency. The desired frequency is determined according to the frequency including the frequency of one IF signal and the frequency of the reference signal to be down-converted to generate one demodulated signal.

  The third filter 805 receives the signal output from the first power distributor 803, suppresses unnecessary waves, and passes only a signal having a desired frequency. The desired frequency is an IF signal having a frequency different from that of the IF signal passed through the second filter 804, and is determined according to the frequency of one IF signal to be down-converted to generate another demodulated signal. Is done.

  The second power distributor 806 distributes the input signal to two paths. That is, the signals distributed to the frequency mixer 810 and the fourth filter 807 are output.

  The fourth filter 807 receives the signal output from the second power distributor 806, suppresses unnecessary waves, and passes only a signal having the frequency of the reference signal. The fourth filter 807 has a narrow band characteristic in order to pass only the reference signal.

  The amplifier 808 amplifies the reduced signal by passing through the fourth filter 807 and outputs the amplified signal to the power combiner 809.

  The power combiner 809 combines two input signals. That is, the signal output from the third filter 805 and the signal output from the amplifier 808 are combined. The power combiner 809 outputs the combined signal to the frequency mixer 812.

  The frequency mixer 810 generates a demodulated signal obtained by down-converting the signal output from the second power distributor 806 from the IF frequency band to the original frequency band input to the transmission device. Specifically, the signal output from the second power distributor 806 includes an IF signal and a reference signal, as will be described later. Accordingly, the frequency mixer 810 generates a demodulated signal that is down-converted to the original frequency band by multiplying the IF signal and the reference signal. Further, the frequency mixer 810 outputs the demodulated signal whose frequency is down-converted to the low frequency filter 811.

  The low frequency filter 811 suppresses unnecessary waves among the signals output from the frequency mixer 810, passes only a signal having a desired frequency, and outputs the passed signal to the output unit 501. The desired frequency may be determined based on the frequency of the signal to be extracted.

  The frequency mixer 812 generates a demodulated signal obtained by down-converting the signal output from the power combiner 809 from the IF frequency band to the original frequency band input to the transmission device. Specifically, the signal output from the power combiner 809 includes an IF signal and a reference signal as will be described later. Thus, the frequency mixer 812 generates a demodulated signal that is down-converted to the original frequency band by multiplying the IF signal and the reference signal. Further, the frequency mixer 812 outputs the frequency down-converted signal to the low frequency filter 813.

  The low frequency filter 813 suppresses unwanted waves from the signal output from the frequency mixer 812, passes only a signal having a desired frequency, and outputs the passed signal to the output unit 502. The desired frequency may be determined based on the frequency of the signal to be extracted.

  The output unit 501 is an output terminal for sending the demodulated signal output from the low-frequency filter 811 to the outside of the wireless reception device 500. The output unit 501 is connected to a TV receiver 72 including a satellite / terrestrial broadcast tuner 71 and a video recorder 74 including a satellite / terrestrial broadcast tuner 73 via a duplexer. It is connected.

  The output unit 502 is an output terminal for transmitting the demodulated signal output from the low frequency filter 813 to the outside of the wireless reception device 500. The output unit 502 also includes a TV receiver 72 including a satellite broadcast / terrestrial broadcast tuner 71 and a video recorder 74 including a satellite broadcast / terrestrial broadcast tuner 73 via a duplexer. And connected to.

  As a result, the demodulated signals output from the output unit 501 and the output unit 502 are output to an appropriate tuner.

  Next, with reference to FIGS. 4 to 7, signal transition in the wireless reception device 500 from when a signal is received until the signal is demodulated to the original signal will be described. Note that the signal received by radio receiving apparatus 500 is radio multiplexed signal 5a transmitted from radio transmitting apparatus 100 of the first embodiment.

  First, when radio receiving apparatus 500 receives radio multiplexed signal 5 a by receiving antenna 600, radio multiplexed signal 5 a is output to IF down-conversion unit 700.

  In IF down-conversion unit 700, radio multiplexed signal 5 a is amplified by amplifier 701, unnecessary waves are suppressed by bandpass filter 702, and input to frequency mixer 703.

  In the frequency mixer 703, the radio multiplexed signal 5a is frequency down-converted from a millimeter wave band to an IF band by a local oscillation signal (fLO3) oscillated from the local oscillator 704. For example, in this embodiment, the frequency is down-converted from a 60 GHz band to a 4 GHz to 2 GHz band.

  FIG. 5A shows a frequency arrangement in which the radio multiplexed signal 5a before frequency conversion is shown on the frequency axis at this time, and a frequency arrangement in which the frequency-converted IF multiplexed signal 6a is shown on the frequency axis. FIG. 5B shows the frequency characteristics of the filter 801. The IF multiplex signal 6a includes an IF signal 1d, an IF signal 2d, and an IF reference signal 3d shown below. That is, IF signal 1d, IF signal 2d, and IF reference signal 3d are signals when radio signal 1c, radio signal 2c, and radio reference signal 3c are frequency down-converted to the IF band.

IF signal 1d: fIF2a = (fLO1 + fLO2-fLO3) -fIF1a
IF signal 2d: fIF2b = (fLO1 + fLO2-fLO3) -fIF1b
IF reference signal 3d: fLO4 = fLO1 + fLO2-fLO3
Thereafter, IF multiplexed signal 6 a is output to modulated signal frequency down-converter 800.

  In the modulation signal frequency down-conversion unit 800, first, the IF multiplexed signal 6a is amplified by the first filter 801, the unnecessary wave generated in the IF down-conversion unit 700 is suppressed, and amplified and level-adjusted by the variable amplifier 802.

  Thereafter, the IF multiplexed signal 6a is distributed by the first power distributor 803 into a path on the side where the second filter 804 is provided and a path on the side where the third filter 805 is provided. .

  Further, a path on the side where the second filter 804 is provided is referred to as a first path (first path), and a path on the side where the third filter 805 is provided is referred to as a second path. Further, the signal distributed to the first path is referred to as IF signal 7a, and the signal distributed to the second path is referred to as IF signal 8a. Since IF signal 7a and IF signal 8a are simply distributed signals, the signal configuration is the same as IF multiplexed signal 6a.

  In the first path, only the IF signal 1d and the IF reference signal 3d are extracted from the IF signal 7a by the second filter 804. That is, the second filter 804 is band-set so as to extract only the IF signal 1d and the IF reference signal 3d.

  Thereafter, the IF signal 7b including the IF signal 1d and the IF reference signal 3d is divided into a path on the side where the frequency mixer 810 is provided and a side on which the fourth filter 807 is provided by the second power distributor 806. To each of the routes.

  In addition, a path on the side where the frequency mixer 810 is provided is a third path (second path), and a path on the side where the fourth filter 807 is provided is a fourth path (third path). . Further, a signal distributed to the third path is an IF signal 7c, and a signal distributed to the fourth path is an IF signal 9a. Since the IF signal 7c and the IF signal 9a are simply distributed signals, the signal configuration is the same as that of the IF signal 7b.

  In the third path, the IF signal 7c is down-converted to the original frequency band demodulated from the IF band. Here, FIG. 6A shows the frequency arrangement of the IF signal 7c immediately before the frequency down-conversion and the frequency characteristics of the second filter 804 and the fourth filter 807 in the third path. The pass characteristic of the second filter 804 is a wideband characteristic that passes the IF signal 1d and the IF reference signal 3d.

  The IF signal 7c is frequency down-converted by the frequency mixer 810 using the IF reference signal 3d. Thereafter, the frequency down-converted signal is freed from unnecessary waves by the low-frequency filter 811 and output as a demodulated signal 7d. FIG. 7A shows the frequency arrangement of the demodulated signal 7d after frequency down-conversion and the frequency characteristics of the low-frequency filter 811 in the third path. As shown in FIG. 7A, the low frequency filter 811 is set with a pass characteristic that allows the demodulated signal 7d to pass therethrough.

  Here, the frequency down-conversion process in the third path is summarized as follows.

Demodulated signal 7d:
fLO4-fIF2a = (fLO1 + fLO2-fLO3)
-[(FLO1 + fLO2-fLO3) -fIF1a]
= FIF1a
Thereafter, the demodulated signal 7d is transmitted from the output unit 501 to the outside. Note that the demodulated signal 7d is a signal similar to the modulated wave signal 1a (fIF1a) input by the wireless transmission device 100.

  On the other hand, in the fourth path, the IF signal 9 a distributed by the second power distributor 806 is input to the fourth filter 807. In the fourth filter 807, only the IF reference signal 3d is extracted from the IF signal 9a. The extracted IF reference signal 3 d is amplified by the amplifier 808 and output to the power combiner 809.

  In the second path, only the IF signal 2 d is extracted from the IF signal 8 a distributed by the first power distributor 803 by the third filter 805 and output to the power combiner 809. That is, the band of the third filter 805 is set so as to extract only the IF signal 2d.

  As a result, the IF signal 2d and the IF reference signal 3d are combined in the power combiner 809 provided at the point where the second path and the fourth path merge. Then, a series of IF signals 10 a is output to the frequency mixer 812. Here, a path from the power combiner 809 to the frequency mixer 812 is defined as a fifth path.

  FIG. 6B shows the frequency arrangement of the IF signal 10a immediately before frequency down-conversion and the frequency characteristics of the second filter 804, the third filter 805, and the fourth filter 807 in the fifth path. . The pass characteristic of the third filter 805 is a narrow band characteristic that passes the IF signal 2d.

  The IF signal 10a is frequency down-converted by the frequency mixer 812 using the IF reference signal 3d. Thereafter, the frequency down-converted signal is freed from unnecessary waves by the low frequency filter 813 and is output as the demodulated signal 10b. FIG. 7B shows the frequency arrangement of the demodulated signal 10 b after frequency down-conversion and the frequency characteristics of the low-frequency filter 813 in the fifth path. As shown in FIG. 7A, the low frequency filter 813 is set with a pass characteristic that allows the demodulated signal 10b to pass therethrough.

  Here, the frequency down-conversion process in the fifth path is summarized as follows.

Demodulated signal 10b:
fLO4-fIF2b = (fLO1 + fLO2-fLO3)
-[(FLO1 + fLO2-fLO3) -fIF1b]
= FIF1b
Thereafter, the demodulated signal 10b is transmitted to the outside from the output unit 502. Note that the demodulated signal 10b is a signal similar to the modulated wave signal 2a (fIF1b) input by the wireless transmission device 100.

  As described above, the demodulated signal 7d and the demodulated signal 10b are transmitted from the wireless reception device 500 via the output unit 501 and the output unit 502 to the satellite / terrestrial broadcast tuner 71 of the TV receiver 72 and the video recorder 74. The data is output to a satellite / terrestrial broadcast tuner 73.

  Here, in the third path, the IF signal 7 b including the IF signal 1 d and the IF reference signal 3 d simultaneously divided by the second filter 804 is input to the frequency mixer 810. In the frequency mixer 810, the IF reference signal 3d becomes a local oscillation signal, and the frequency down-conversion is directly performed.

  Therefore, in the third path, since it is not necessary to separate the IF signal 1d and the IF reference signal 3d, even if the frequency of the IF signal 1d to be demodulated and the frequency of the IF reference signal 3d are close to each other, it is satisfactory. Frequency down-conversion is possible. As a result, a terrestrial broadcast signal, which is an example of the modulated wave signal 1a, is extracted as the demodulated signal 7d.

  In the fourth path, the IF reference signal 3d extracted by the fourth filter 807 has passed through the wideband second filter 804 and the narrowband fourth filter 807. Therefore, not only the unwanted wave component is suppressed over a wide band, but also the nearby noise around the IF reference signal 3d is removed in a narrow band, so that the IF reference signal 3d with high purity can be extracted.

  Further, the extracted IF reference signal 3d is amplified by the amplifier 808 and then output to the frequency mixer 812 together with the IF signal 2d. Moreover, in the second path, the IF signal 2d separated by the third filter 805 is separated from the IF reference signal 3d in frequency as shown in FIG. 6B.

  Therefore, the extracted / amplified IF reference signal 3d becomes a local oscillation signal of the frequency mixer 812, so that a good frequency down-conversion can be performed in the fifth path. As a result, a satellite broadcast wave signal, which is an example of the modulated wave signal 2a, is extracted as the demodulated signal 10b.

  Furthermore, since the IF signal 2d is narrowed by the third filter 805, the IF signal 1d is not included. Therefore, the frequency mixer 812 can perform high-quality frequency down-conversion with less secondary distortion in the output signal.

  Further, when the IF multiplexed signal 6a is down-converted, if the specific bandwidth (transmission bandwidth / transmission frequency) is large, a secondary distortion characteristic occurs in the output signal of the frequency mixer along with the down-conversion.

  On the other hand, modulation signal frequency down-conversion unit 800 generates down-converted signal 7d and demodulated signal 10b using IF reference signal 3d as a local oscillation signal in accordance with distributed IF signal 7a and IF signal 8a. Is done.

  As a result, the modulation signal frequency down-conversion unit 800 includes the frequency mixer 810 and the frequency mixer 812, respectively, and reduces the second-order distortion characteristics of the output signal of each mixer by down-converting into at least two bands. Is possible. Therefore, it is possible to ensure good transmission characteristics in the wireless reception device 500. The secondary distortion characteristics are distortion components such as fIF2a-fIF2b and 2x (fIF2a-fIF2b).

  In the fourth path, the IF reference signal 3d is extracted with a small and simple configuration by including one narrow band filter (fourth filter 807) and one amplifier 808. It is possible.

  Furthermore, the first demodulated signal 7d and demodulated signal 10b can be taken out (down-converted) from the two frequency mixers 810 and 812 at the same time.

  In the modulation signal frequency down-conversion unit 800, the fourth path is connected to the frequency mixer 810 via the second power distributor 806 and to the frequency mixer 812 via the power combiner 809. For this reason, the second power distributor 806 and the power combiner 809 between the two local oscillation terminals are connected.

  However, the flow path of the IF reference signal 3d in the fourth path connecting the local oscillation terminals is configured by one line without being divided, and is configured by the fourth filter 807 and the amplifier 808. It becomes possible to achieve unidirectionalization and narrow band simultaneously.

  As a result, it is possible to reduce the leakage of the input signal between the local oscillation terminals to each other's mixer (frequency mixer 810 and frequency mixer 812). Further, the extraction / amplification of the IF reference signal 3d can be constituted by a single amplifier 808, so that the power consumption can be reduced.

  Therefore, in radio receiving apparatus 500 of the present embodiment, three filters (second filter 804, third filter 805, and fourth filter 807) are effectively arranged to improve the degree of suppression of unnecessary waves. Therefore, when extracting a high-purity reference signal with few unnecessary wave components and performing down-conversion to generate a plurality of demodulated signals, signal leakage between local oscillation terminals is reduced, and the number of amplifiers is reduced. Since it is reduced, it is possible to reduce power consumption.

  Also, in the modulation signal frequency down-conversion unit 800, as shown in FIG. 4, the first power distributor 803, the second filter 804, the second power distributor 806, the fourth filter 807, the amplifier 808, A line loop L is formed by the coupler 809 and the third filter 805.

  Therefore, the first power distributor 803 and the power combiner 809 have isolation between the distribution ports 821 and the coupling ports 822, so that one amplifier is added to the line loop L. If the gain of the added amplifier is smaller than the sum of the gain of the first power distributor 803 and the power combiner 809, the line loop L can be a negative feedback loop. It becomes. Therefore, unnecessary / parasitic oscillation can be prevented.

  For example, if the gain of 20 dB of the added amplifier is smaller than the sum (26 dB) of the isolation 13 dB of the first power distributor and the isolation 13 dB of the power combiner 809 in the intermediate frequency band of the receiving system. The line loop L can be a negative feedback loop, and unnecessary / parasitic oscillation can be prevented.

  Further, the first power divider 803 and the power combiner 809 are respectively a Wilkinson type power divider and a Wilkinson type power combiner, so that the absorption resistance of the Wilkinson type power combiner and the Wilkinson type power divider can be reduced. It is possible to provide isolation.

  Therefore, it is easy to configure the line loop L with a wider band and a lumped constant line, and it is possible to reduce the size, that is, the size of the line loop L. Thereby, when the line loop L is formed, the potential oscillation frequency region in the line loop L and the amplifier 808 can be further increased.

  Since the oscillation frequency is increased, the gain of the amplifier 808 is reduced as the frequency is increased. Therefore, the loop gain formed by the line loop L and the amplifier 808 can be reduced. In addition, since the first power distributor 803 and the power combiner 809 have isolation over a wide band, the potential loop gain region can be further reduced.

  In addition, the wireless reception device 500 includes a variable amplifier 802 at the subsequent stage of the IF down-conversion unit 700, specifically, at the previous stage of the first power distributor 803. The variable amplifier 802 not only enhances the frequency conversion gain accompanying the frequency conversion in the IF down-conversion unit 700, suppresses the influence of noise from the subsequent stage, and further reduces the influence of the frequency mismatch of the input and output impedances, The following effects are brought about.

  That is, the modulation signal frequency down-conversion unit 800 is configured to frequency-convert a signal wave using the wireless reference signal 3c from the wireless signal 1c, the wireless signal 2c, and the wireless reference signal 3c that are originally wirelessly transmitted. It is. For this reason, when the transmission distance is increased and the transmission signal is also weakened, the radio signal 1c, the radio signal 2c, and the radio reference signal 3c transmitted by radio are attenuated.

  In the above phenomenon of attenuation, it is known that in a normal heterodyne receiver, when the transmission distance is doubled, the transmitted signal is reduced by 6 dB. On the other hand, a reference signal is also transmitted to radio receiving apparatus 500 of the present embodiment. For this reason, when the transmission distance is increased and the reference signal is attenuated, the wireless reception device 500 attenuates 12 dB with respect to the transmission distance when the local oscillation signals (reference signals) of the frequency mixers 810 and 812 are not sufficiently transferred. It has characteristics.

  Therefore, rapid conversion loss increases. For this reason, the subsequent stage circuit connected to the frequency mixers 810 and 812 and the tuner unit in the TV receiver 72 and the video recorder 74 connected to the wireless reception device 500 are significantly susceptible to noise.

  Therefore, by providing the variable amplifier 802 after the IF down-conversion unit 700, the variable amplifier 802 reduces the influence of the sudden conversion loss of the modulation signal frequency down-conversion unit 800. It can be realized. That is, it is possible to suppress a rapid increase in frequency conversion loss associated with frequency conversion at the subsequent stage from the variable amplifier 802.

  Further, in radio receiving apparatus 500 of the present embodiment, where the radio transmission distance is short, the output signals of variable amplifier 802 of modulation signal frequency down-conversion unit 800, amplifier 808, and frequency mixers 810 and 812 are excessively input. May be distorted easily. On the other hand, when the transmission distance is increased, both the reference signal and the radio signal which are transmission signals are attenuated, and the level may be rapidly decreased.

  Therefore, by providing the variable amplifier 802 with an auto gain control circuit or a self-bias circuit, the transmission quality can be kept more constant with respect to the transmission distance. Furthermore, it is possible to widen the dynamic range as the wireless reception device 500.

  Specifically, for example, it is assumed that the variable amplifier 802 and the frequency mixers 810 and 812 are configured by microwave transistors driven by self-bias.

  Therefore, the output levels of the variable amplifier 802 and the frequency mixers 810 and 812 are rapidly increased by configuring the variable amplifier 802 and the frequency mixers 810 and 812 with a self-bias circuit that makes the collector (drain) current substantially constant. And a rapid drop can be suppressed.

  8A is a circuit diagram showing one configuration example, and FIG. 8B is a circuit diagram showing another configuration example.

  In FIG. 8A, the self-bias circuit includes an input matching circuit unit 910 including a bias circuit, a microwave transistor 920, and an output matching circuit unit 930. The microwave transistor 920 may be an FET or a bipolar transistor. The base (gate) terminal is connected to the input matching circuit unit 910, the collector (drain) terminal is connected to the output matching circuit unit 930, and the emitter (source) terminal. Is grounded. In the input matching circuit unit 910, a high resistance 911 of about 20 kΩ, for example, is inserted in series with the connection terminal of the power supply in the bias circuit.

  In this case, for a high level input signal, the collector current increases and the base current also increases. Therefore, the resistor 911 generates an electromotive voltage in the base-emitter voltage of the microwave transistor 920, and substantially lowers the base-emitter voltage applied to the microwave transistor 920.

  This makes it possible to reduce the base current of the microwave transistor 920 and prevent an increase in the collector current. Further, the amplification degree and conversion gain of the microwave transistor 920 can be reduced, and an increase in the output signal level can be suppressed.

  In FIG. 8B, in addition to the configuration of FIG. 8A, the self-bias circuit is configured such that the emitter terminal of the microwave transistor 920 is grounded via the resistor 921 and grounded via the capacitor 922. Yes. The high-frequency signal output from the output matching circuit unit 930 is grounded by the capacitor 922 with approximately impedance of 0Ω. The resistor 921 has a resistance value of approximately several Ω to several tens Ω.

  In this case, when a large signal of a high-frequency signal is input to the collector current of the microwave transistor 920, an electromotive voltage is generated by the resistor 921 connected to the emitter terminal and should be substantially applied to the microwave transistor 920. Since the source-emitter voltage is reduced, the collector current can be reduced.

  Therefore, in the variable amplifier 802 and the frequency mixers 810 and 812, it is possible to reduce the amplification degree and the conversion gain, and to suppress a rapid increase in the output signal level.

  Therefore, by using the variable amplifier 802 and the frequency mixers 810 and 812 as self-bias circuits, a wide dynamic range is maintained in which the transmission quality is kept more constant with respect to the wireless transmission distance from a short section to a long section of the wireless transmission distance. The wireless reception device 500 can be realized.

  In particular, by configuring the variable amplifier 802 and the frequency mixers 810 and 812 at the same time as a self-bias (or auto gain control) circuit, it is possible to further widen the dynamic range of the radio receiving apparatus 500. Therefore, the transmission signal quality with respect to the transmission distance can be made more constant.

  When the frequency mixers 810 and 812 are configured as shown in FIGS. 8A and 8B, they are configured as active mixers.

  An active mixer is a mixer circuit using active elements such as transistors and FETs, and frequency conversion is performed using the nonlinear characteristics of each semiconductor element. Since the active mixer uses active elements, amplification can be performed simultaneously with frequency conversion. Further, the active mixer can obtain a conversion gain. Furthermore, since the active mixer is not configured to be driven by the local oscillation signal power unlike a passive mixer using a diode, generally, the local oscillation signal power may be small.

  By configuring the frequency mixer 810, 812 as an active mixer and a base injection mixer (a gate injection mixer in the case of FET), the frequency mixer 810, 812 can be used even with a smaller reference signal transmitted due to the gain of the active mixer. It is possible to drive by using as a local oscillation signal. Therefore, it is possible to configure the frequency mixers 810 and 812 that have higher linearity and lower conversion loss than a passive mixer such as a normal diode mixer.

  That is, since the reference signal is also wirelessly transmitted from the wireless transmission device 100 of the first embodiment, the reference signal that becomes the local oscillation signal of the frequency mixers 810 and 812 becomes weaker as the transmission distance increases. turn into.

  Therefore, by configuring the frequency mixers 810 and 812 with an active mixer using a microwave transistor, a reference signal serving as a local oscillation signal can be input at a lower level (for example, about −10 dBm to 0 dBm). It is possible to make the input / output relationship operate in a substantially linear region. Therefore, it is possible to avoid as much as possible the characteristic of 12 dB attenuation with respect to the transmission distance.

  Here, by configuring the wireless transmission device 100 of the first embodiment and the wireless reception device 500 of the second embodiment, a wireless communication system capable of performing broadband wireless transmission in the microwave / millimeter wave region. Can be formed.

  The wireless transmission device 100 includes a variable amplifier 242 that adjusts the signal level of the reference signal 3 a output from the reference signal source 241. As a result, the reference signal 3b whose level is adjusted by the variable amplifier 242 can be added to the radio multiplexed signal 5a. Therefore, it is possible to correct the variation of the circuits constituting the wireless transmission device 100 by adjusting the signal level of the reference signal with the variable amplifier 242, and to make the transmission output constant.

  In addition, the wireless reception device 500 can receive more constant signals, and can configure the wireless transmission device 100 and the wireless reception device 500 that are excellent in yield characteristics. Therefore, a wireless communication system having more stable transmission characteristics can be configured.

[Embodiment 3]
Another embodiment of the present invention will be described as follows. Configurations other than those described in the present embodiment are the same as those in the first and second embodiments. For convenience of explanation, members having the same functions as those shown in the drawings of the first and second embodiments are given the same reference numerals, and explanation thereof is omitted.

  In this embodiment, an electronic device including a wireless communication system configured by the wireless reception device 500 of the second embodiment or the wireless transmission device 100 of the first embodiment and the wireless reception device 500 will be described. .

  The electronic apparatus according to the present embodiment includes the wireless reception device 500 or the communication system. Therefore, the wireless transmission device 100 and the wireless reception device 500 can perform broadband wireless transmission in the microwave / millimeter wave region.

  In the electronic device of this embodiment, the radio reception device 500 or the radio reception device in the radio communication system records, outputs, or records and outputs a demodulated signal generated by frequency down-conversion. Do. Here, the output includes video display and audio output, and the electronic device refers to a device that performs recording, video recording, video display, and / or audio output.

  For example, when the electronic device is the TV receiver 72 shown in FIG. 4, the TV receiver 72 may include the wireless reception device 500. In this case, the wireless reception device 500 displays a demodulated signal generated by frequency down-conversion, that is, a video signal / audio signal or the like, on the display screen of the TV receiver 72 or performs audio output.

  When the electronic device is the video recorder 74 shown in FIG. 4, the video receiver 74 may include the wireless reception device 500. In this case, the wireless reception device 500 records, records, and records a demodulated signal generated by frequency down-conversion, that is, a broadcast signal, in the recording unit of the video recorder 74.

  Furthermore, when the electronic device includes the wireless communication system, for example, an electronic device in which an antenna receiver including the wireless transmission device 100 and a video reproduction / recording device including the wireless reception device 500 are set is configured.

  Since this wireless communication system is broadband wireless transmission in the microwave / millimeter wave region, the wireless communication system and the wireless reception device 500 itself do not need to be equipped with digital signal processing such as compression / decompression.

  In addition, this wireless communication system is a system that performs up-conversion and down-conversion based on one reference signal. In the wireless communication system that includes the wireless transmission device 100 and the wireless reception device 500, each local oscillator This eliminates the need for an AFC (automatic frequency control) unit that adjusts frequency fluctuations associated with frequency fluctuations. Therefore, the electronic device can be reduced in size and cost.

  Furthermore, since the electronic device having the above configuration can output or record a video signal or the like wirelessly, the cable wiring of the antenna is simplified. For example, if the video signal is a multi-channel broadcast of a broadcast signal, the multi-channel broadcast signal can be wirelessly transmitted at a time. Therefore, different channels can be simultaneously displayed and recorded on a plurality of electronic devices, for example, the TV receiver 72 and the video recorder 74.

  The present invention is not limited to the above-described embodiments, and various modifications are possible within the scope shown in the claims, and the present invention can be obtained by appropriately combining technical means disclosed in different embodiments. Such embodiments are also included in the technical scope of the present invention.

  The present invention can be used for a microwave / millimeter wave wireless transmission device, a wireless reception device, a wireless communication system, and an electronic device capable of wirelessly communicating a communication data signal, a broadcast data signal, and the like. The present invention can be applied to other fields as well. For example, it can be applied to the field of radar sensing technology such as in-vehicle radar.

It is a schematic diagram which shows one Embodiment of the radio | wireless transmitter in this invention. It is a figure which shows the frequency arrangement | positioning of each signal in the said radio | wireless transmitter, (a) shows a modulated wave signal, (b) shows the IF signal after up-converting a modulated wave signal to IF. It is a figure which shows the frequency arrangement | positioning of each signal in the said radio | wireless transmitter, (a) shows IF signal before up-converting to a millimeter wave band, (b) after IF signal is up-converted to a millimeter wave band A wireless signal is shown. It is a schematic diagram which shows one Embodiment of the wireless receiver in this invention. It is a figure which shows the frequency arrangement | positioning of each signal in the said radio | wireless receiver, (a) shows the radio signal before downconverting to IF, (b) shows the IF signal after downconverting the radio signal to IF. . It is a figure which shows the frequency arrangement | positioning of each signal in the said radio | wireless receiver, (a) shows IF signal before down-converting to the original frequency, (b) is after down-converting IF signal to the original frequency. A demodulated signal is shown. It is a figure which shows the frequency arrangement | positioning of each signal in the said radio | wireless receiver, (a) shows the demodulated signal output from the output part 501, (b) shows the demodulated signal output from the output part 502. It is a circuit diagram which shows one structural example of the variable amplifier 802 and the frequency mixer 810 * 812 in the said radio | wireless receiver. It is a schematic diagram which shows the structure of the conventional transmitter and receiver.

Explanation of symbols

51 Antenna for Terrestrial Broadcasting 52 Antenna for Satellite Broadcasting 71, 73 Tuner for Satellite Broadcasting / Terrestrial Broadcasting 72 TV Receiver (Electronic Equipment)
74 Video recorder (electronic equipment)
DESCRIPTION OF SYMBOLS 100 Radio transmission apparatus 101 Input part 200 IF up-conversion part (1st up-conversion means)
210 duplexer 220,230 IF upconverter (third upconversion means)
221, 231 Variable amplifier (input signal level adjusting means)
222, 232 Mixer 223, 233 Band pass filter 240 Reference signal adding unit 241 Reference signal source 242 Variable amplifier 250 Power combiner (Multiple signal generating means)
300 mm-wave frequency up-conversion unit (second up-conversion means)
400 transmitting antenna 500 wireless receiving device 501 output unit 502 output unit 600 receiving antenna 700 IF down-conversion unit (first down-conversion means)
800 Modulation signal frequency down-conversion unit (second down-conversion means)
801 First filter 802 Variable amplifier (first amplification means)
803 First power distributor (first distribution means)
804 Second filter (first extraction means)
805 Third filter (third extraction means)
806 Second power distributor (second distribution means)
807 Fourth filter (second extraction means)
808 Amplifier 809 Power combiner (Power combining means)
810 Frequency mixer (third down-conversion means)
811 Low frequency filter 812 Frequency mixer (fourth down-conversion means)
813 Low frequency filter 821 Distribution port 822 Coupling port 910 Input matching circuit 920 Microwave transistor 930 Output matching circuit

Claims (12)

A first up-converting unit that up-converts a plurality of series of input signals using a reference signal, and a multiplexed signal that generates a multiplexed signal by combining power of the signal output from the first up-converting unit and the reference signal Generating means, and second up-converting means for up-converting the multiplexed signal output from the multiplexed signal generating means to approximately the microwave band or more using a local transmission signal, and output from the second up-converting means A wireless transmission device for transmitting a wireless multiplexed signal,
The first up-conversion means includes
Radio transmission characterized by comprising input signal level adjusting means provided for each of the plurality of series of input signals and for adjusting a signal level of the plurality of series of input signals before up-converting the plurality of series of input signals. apparatus. The first up-conversion means includes
A third up-conversion unit that is provided for each of the plurality of series of input signals and performs up-conversion using the reference signal for each of the plurality of series of input signals;
2. The radio transmission apparatus according to claim 1, wherein the multiple signal generation unit generates the multiple signal by combining the power of each signal output from the third up-conversion unit and the reference signal. 3. . First down-converting means for down-converting a radio multiplexed signal including the received reference signal using a local oscillation signal, and a frequency for demodulating the intermediate frequency multiplexed signal output from the first down-converting means using the reference signal A second down-converting means for down-converting the signal to the radio receiver, and outputting a demodulated signal output from the second up-converting means,
The second down-conversion means includes
First distributing means for distributing the intermediate frequency multiplexed signal output from the first down-converting means to a plurality of paths according to the number of signals to be demodulated;
First extraction means for extracting a first intermediate frequency signal including a reference signal from the intermediate frequency multiplexed signal into a first path that is one of a plurality of paths distributed by the first distribution means;
Second distribution means for distributing the signal output from the first extraction means to the second path and the third path;
Third down-converting means for down-converting the first intermediate frequency signal including the reference signal into the second path to a frequency demodulated using the reference signal;
Second extraction means for extracting only the reference signal from the first intermediate frequency signal including the reference signal in the third path;
A third extraction unit that is provided for each path other than the first path distributed by the first distribution unit and extracts a second intermediate frequency signal to be demodulated from the intermediate frequency multiplexed signal;
Provided for each second intermediate frequency signal output from the third extraction means and power-couples the reference signal output from the second extraction means to the second intermediate frequency signal output from the third extraction means. Power coupling means;
A frequency which is provided for each second intermediate frequency signal including the reference signal output from the power combining means and demodulates the second intermediate frequency signal including the reference signal output from the power combining means using the reference signal. And a fourth down-converting means for down-converting to the radio receiving apparatus.   4. The radio reception apparatus according to claim 3, wherein the second extraction unit is configured by one amplifier and one narrow band filter. The first distribution means has isolation between distribution ports;
The radio receiving apparatus according to claim 4, wherein the power coupling means has isolation between coupling ports. The first distribution means is a Wilkinson power distributor,
6. The wireless receiver according to claim 5, wherein the power coupling means is a Wilkinson power coupler.   The total sum of the isolation between the distribution ports and the isolation between the coupling ports is larger than the sum of the gains of the amplifiers in an intermediate frequency band of a reception system. Wireless receiver. The second down-conversion means includes
4. The radio receiving apparatus according to claim 3, further comprising a first amplifying unit that amplifies and adjusts the signal output from the first down-converting unit before the first distributing unit.   9. The wireless receiver according to claim 8, wherein the first amplifying means is an amplifier configured by an auto gain control circuit or a self-bias circuit.   10. The radio receiving apparatus according to claim 3, wherein the third down-conversion unit and the fourth down-conversion unit are frequency mixers configured by microwave transistors driven by self-bias.   A wireless communication system comprising the wireless transmission device according to claim 1 and the wireless reception device according to any one of claims 3 to 11. An electronic device comprising the wireless reception device according to any one of claims 3 to 11, or the wireless communication system according to claim 11.
An electronic device characterized in that the radio reception device or the radio reception device configured in the radio communication system records, outputs, or both records and outputs a demodulated signal generated by frequency down-conversion. machine.

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