JP4138639B2 - Microwave wireless communication system and electronic device - Google Patents

Description

The present invention, microwave band to wireless communication systems and electronic devices, particularly, a microwave band radio transmission apparatus and a microwave-band radio receiver and microwave-band radio communication system for wirelessly transmitting a plurality of broadcast waves in a microwave band And electronic devices.

  Conventionally, as shown in FIG. 13, a microwave band wireless communication system includes a high-frequency wireless transmission device and a high-frequency wireless reception device (see, for example, Japanese Patent Laid-Open No. 2001-53640 (Patent Document 1)). . Here, the microwave band refers to a frequency band including a millimeter wave band.

  In the high-frequency radio transmission apparatus, an intermediate frequency signal 1080a (frequency fIF) modulated by the IF modulation signal source 1000 is generated, and a local oscillation signal 1060b (frequency fLO) is generated by the millimeter wave band local oscillator 1050, and the local oscillation signal is generated. The intermediate frequency signal 1080a is frequency upconverted by the frequency converter 1001 using the signal 1060b (frequency fLO). Then, the radio signal 1070 (frequency fRF) whose frequency is up-converted is extracted by the bandpass filter 1020 in the high frequency band, and multiplexed with the local oscillation signal 1060b by the signal synthesizer 1140, and the local oscillation signal 1060b (frequency fLO) is obtained. Radio signal 1070 is amplified to an appropriate level by transmission amplifier 1003 and radiated by transmission antenna 1500.

  In the high frequency radio receiving apparatus on the receiving side, the radio signal 1070 and the local oscillation signal 1060b are received by the receiving antenna 2000 and amplified to an appropriate level by the low noise amplifier 1110. The signal amplified by the low noise amplifier 1110 is divided into two, and the unmodulated carrier is filtered by the band pass filter 1200, and the unmodulated carrier is regenerated by the injection locking oscillator 1400 (or a single tuning amplifier). An IF band modulated wave signal 1080b is obtained from the radio modulated signal by multiplier 1300 and demodulated by intermediate frequency band demodulation circuit 1310.

  However, the microwave band wireless communication system has the following problems.

  (1) On the transmitting side, a multiplexed signal is generated by combining with a reference signal in the millimeter wave band, and the frequency arrangement relationship in the millimeter wave band is uniquely determined, so a high frequency local oscillation signal (frequency fLO) And it is difficult to strictly control the output level of radio signal (frequency fRF) and unnecessary single sideband signal. In addition, it can only deal with a single modulated signal source.

  (2) Since the local oscillation signal is generated and synthesized directly in the radio frequency band on the transmitting side, it is necessary to generate a local oscillation signal having a frequency substantially equivalent to that of the millimeter wave radio frequency band. It is difficult to generate an oscillation wave in the millimeter wave band.

  (3) In frequency down-conversion on the receiving side, the received amplified signal is band-filtered as it is with a millimeter-wave bandpass filter (bandpass filter), and an unmodulated carrier signal is generated by an injection locking oscillator (or a single tuning amplifier). Due to the generated configuration, the bandpass filter cannot have sufficient steepness and includes not only the unmodulated carrier signal component but also the radio modulated signal component, and the frequency conversion efficiency of the frequency down-conversion by the multiplier is poor. Therefore, there is a problem that the transmission distance is shortened.

  (4) On the receiving side, after being amplified by a millimeter-wave amplifier, the radio modulated signal is input to the multiplier without being filtered by the bandpass filter. As a result, the multiplier is easily distorted, and efficient frequency conversion (frequency down-conversion) cannot be performed, resulting in a short transmission distance.

  (5) Furthermore, there is a problem that the receiving side does not have a defense capability against the invasion of unnecessary wave signals other than the bandpass filter pass band from the antenna and is extremely vulnerable to noise.

  (6) In frequency down-conversion on the receiving side, the received amplified signal is filtered as it is in the millimeter wave band, and the frequency of the signal from the injection locked oscillator (or single tuning amplifier) that reproduces the unmodulated carrier and the radio modulated signal. It is a configuration to obtain an IF modulation signal by conversion (multiplication), and it is difficult to obtain a sufficient gain in terms of transistor performance and IC isolation because only a millimeter wave band low noise amplifier has a high frequency. Therefore, it is difficult to obtain a sufficient conversion gain as a receiving apparatus, and it is difficult to secure a wireless transmission distance.

  (7) An injection locked oscillator (or a single tuned amplifier) for regenerating an unmodulated signal on the receiving side cannot obtain a sufficient (synchronous) gain due to its high frequency, causing a loss of synchronization or multiplication. It is difficult to ensure stable operation by ensuring the level of the unmodulated carrier signal for sufficiently driving the detector.

  In particular, with respect to the above problem (1), the local oscillation signal 1060b used for frequency up-converting the intermediate frequency signal 1080a to the radio signal 1070 in the high frequency band is directly added by the signal synthesizer 1140, so that the radio signal 1070 and the local oscillation are The radio multiplexed signal 1150, which is the transmission wave of the signal 1060b, is generated. In this case, the frequency fRF of the radio signal 1070 and the frequency of the intermediate frequency signal 1080a are locally oscillated if the frequency fIF 1080a of the input modulation wave signal is determined. The relationship between the frequency fLO is uniquely determined. The radio signal 1070 (frequency fRF) is difficult to set arbitrarily in the radio frequency band due to problems in the radio law, and the IF frequency band of the intermediate frequency signal 1080a is, for example, the frequency of a TV signal. For example, the frequency is already determined, and usually about 0.1 GHz to 2 GHz is used.

  FIG. 14 shows the relationship of the frequency spectrum of the conventional microwave radio communication system. As shown in FIG. 14, if the radio frequency fRF and the intermediate frequency fIF are fixed by the radio frequency fRF (= fLO + fIF or fLO−fIF), the local oscillation frequency fLO cannot be freely set. Further, since the local oscillation signal 1060b (frequency fLO) is also a transmission signal, the level of the local oscillation signal 1060b (frequency fLO) needs to be accurately controlled simultaneously with the radio signal 1070 (frequency fRF). Further, in the case of using a single sideband signal (for example, the upper sideband) as the radio signal 1070 (frequency fRF), the radio multiplexed signal 1150 normally has a lower sideband fLO-fIF component as an unnecessary signal, and a bandpass filter. It is necessary to suppress by 1020 (shown in FIG. 13).

  However, when the intermediate frequency signal 1080a (frequency fIF) is a frequency in the UHF band (for example, fIF = 0.5 GHz to 1.0 GHz), the frequency of the radio signal is set to the millimeter wave band (for example, fRF = 60.0 GHz to 60 GHz). .5 GHz), as shown in FIG. 14, the fLO + fIF component, fLO component, and fLO-fIF component are 60 GHz to 60.5 GHz, 59 GHz, 58.0 GHz to 58.5 GHz, respectively, and the frequency intervals are close to each other. Therefore, in this frequency band, it is difficult to suppress the fLO-fIF signal of the lower sideband signal, which is an unnecessary signal, with a normal millimeter-wave bandpass filter (planar circuit filter or waveguide filter). Furthermore, the local oscillation frequency fLO is also in the attenuation band of the millimeter wave band-pass filter, and it is extremely difficult to control the level to be constant.

  Further, as the problem of (2) above, it is very difficult to directly generate the 59 GHz component that is the local oscillation signal 106b (frequency fLO).

Furthermore, the above-mentioned microwave band radio communication system has a problem that the radio transmission bandwidth cannot be expanded so as to be compatible with a plurality of modulated wave signals (for example, a plurality of broadcast waves).
JP 2001-53640 A

Accordingly, an object of the present invention is to control each level of a transmitted radio signal, a local oscillation signal, and an unnecessary suppression signal with high accuracy, and expand a wireless transmission bandwidth to support communication of a plurality of modulated wave signals. The object is to provide a waveband radio communication system .

Another object of the present invention is to increase the frequency conversion efficiency on the receiving side to expand the wireless transmission distance, and to provide a defense capability against unwanted waves, while expanding the wireless transmission bandwidth so that a plurality of modulated wave signals can be transmitted. An object of the present invention is to provide a microwave radio communication system that can handle communication.

Another object of the present invention can lower the oscillation frequency of the local oscillator easy single configuration is to provide a microwave-band radio communication system capable stable operation.

Another object of the present invention is to provide a child device electrodeposition using at least one of said microwave-band radio communication system.

In order to achieve the above object, a microwave band wireless transmission device of the present invention includes:
A frequency arrangement means for converting a plurality of input modulated wave signals to an intermediate frequency band and arranging them on a frequency axis, and generating an intermediate frequency multiplexed signal by adding a reference signal to the signals arranged on the frequency axis; A transmission-side frequency conversion means for frequency-converting the intermediate frequency multiplexed signal generated by the frequency arrangement means to a microwave band, and a multiplexed signal frequency-converted to the microwave band by the transmission-side frequency conversion means A microwave band wireless transmission device having transmission means for transmitting as a signal ;
Receiving means for receiving a radio multiplexed signal transmitted from the microwave radio transmitting apparatus; first receiving side frequency converting means for frequency down-converting the radio multiplexed signal received by the receiving means to an intermediate frequency band; Filter means for extracting a reference signal and a desired intermediate frequency signal from the intermediate frequency multiplexed signal converted by the first receiving side frequency conversion means, and the desired signal by the reference signal extracted by the filter means. Microwave band radio reception having second reception side frequency conversion means for regenerating at least one of the plurality of input modulation wave signals input on the transmission side by frequency down-converting the intermediate frequency signal Equipment and
With
A microwave radio communication system using a plurality of the microwave radio receivers,
The above-mentioned plurality of microwave band wireless receivers are installed on a flat panel display,
The outputs from the plurality of microwave band wireless receivers are combined and input to the flat panel display .

  According to the microwave radio transmitting apparatus having the above-described configuration, it is possible to expand the transmission bandwidth by arranging and multiplexing a plurality of input modulated wave signals on the frequency axis, and the microwave band ( It becomes possible to control the level ratio between the reference signal added at the stage of the intermediate frequency band before the frequency up-conversion to the frequency including the millimeter wave band and the multiplexed modulated wave signal. Therefore, the ratio between the reference signal added by frequency up-converting to the microwave band and the level of the multiplexed modulated wave signal can be controlled, and can be determined almost constant.

  Therefore, a microwave band radio transmission apparatus capable of accurately controlling each level of a radio signal to be transmitted, a local oscillation signal, and an unnecessary suppression signal, and expanding the radio transmission bandwidth to support communication of a plurality of modulated wave signals. realizable.

Further , the first receiving side frequency conversion means performs frequency down-conversion from a microwave band to a lower frequency in the intermediate frequency band. The reference signal and the desired signal added on the transmission side are extracted from the intermediate frequency multiplexed signal thus obtained by the filter means. This is because at a lower frequency, the dielectric loss of the material / physical property is increased, and a band pass filter having a high Q value can be configured. By extracting only the signal and the desired signal, after removing unwanted wave signals and interference signals, the reference signal component and intermediate frequency signal component are frequency down-converted by a nonlinear device such as a microwave transistor. The input modulation wave signal on the transmission side can be regenerated in a state where there are few wave signals and interference wave signals and high purity.

  In addition, from the above intermediate frequency on the transmission side to the microwave band that is the transmission radio frequency, the influence of the frequency fluctuation and phase noise of the local oscillator used for frequency up-conversion, the reception side receives the radio multiplexed signal, and the microwave When the frequency is converted from the band to the first reception side, the local oscillator used for frequency up-conversion to the intermediate frequency band on the transmission side and the influence of the frequency fluctuation of the local oscillation and the phase noise during the first frequency conversion on the reception side Is included in both the reference signal and the desired signal extracted by the filter means, so that the signal contained in the intermediate frequency multiplexed signal by the extracted reference signal is converted into the second receiving side frequency conversion. By performing frequency down-conversion by means, it is possible to cancel the influence of frequency fluctuations and phase noise of the local oscillator.

Further , although the distances of the radio transmission paths of the radio multiplexed signals input to a plurality of microwave radio receivers are different, the intermediate frequency band stage of the microwave radio receivers, that is, reference signal reproduction / frequency separation In the stage, since the reproduced reference signal and intermediate frequency signal contain the same phase information regarding the transmission distance, the second frequency conversion means downconverts the intermediate frequency signal with the reference signal. At this time, since the distance information is canceled in the radio transmission interval in the frequency-converted signal, the reception output of the plurality of microwave band radio reception devices is the output line of the output of the microwave band radio reception device. If they are the same, they can be synthesized in phase. As a result, the reception output can be increased, the frequency conversion efficiency on the reception side can be increased and the wireless transmission distance can be increased, and in addition, the antenna portion in the microwave radio receiver is blocked by a human body, an object, etc. However, as long as at least one microwave band radio receiving apparatus receives a signal from the transmission side without being blocked, a desired signal can be received and a spatial diversity effect can be obtained.

  Moreover, in one embodiment, it is set as the structure by which each output from the said several microwave band radio | wireless receiver is synthesize | combined via the output line of the same length.

  In one embodiment, a DC voltage is supplied to each of the plurality of microwave band radio receiving apparatuses via the output line.

Further, in one embodiment, the DC voltage, a structure in which the plurality of microwave-band radio receiver is supplied from the connected electronic equipment.

  An electronic apparatus according to the present invention includes at least one of the microwave band wireless transmission device and the microwave band wireless reception device.

  In addition, an electronic device according to an embodiment includes a hard disk recorder or a DVD recorder and a digital television tuner.

  According to the electronic device of the above-described embodiment, TV viewing or the like can be performed while back-recording a multi-channel transmitted signal.

  Furthermore, the electronic device of one embodiment is a portable device that is small and portable. This makes it possible to carry it indoors.

As is apparent from the above, according to the microwave band wireless communication system and an electronic apparatus, it is possible to expand the wireless transmission bandwidth corresponding to the communication of the plurality of modulated-wave signals, a plurality of indoors, such as e.g. Broadcast wave signals can be transmitted wirelessly at once.

  In addition, on the transmission side, an intermediate frequency multiplexed signal can be generated with the intermediate frequency of the desired signal and the level-controlled reference signal, and the intermediate frequency band before frequency up-conversion to the microwave band (including the millimeter wave band) can be generated. It is possible to control the level ratio of the modulated wave signal multiplexed with the additional signal at the stage to control the optimum ratio. For this reason, frequency conversion efficiency (reception sensitivity) at the time of the second frequency down-conversion (detection) in which the desired signal is frequency-converted with the reference signal on the receiving side can be increased, and the transmission distance can be increased. it can.

  In addition, the pseudo-heterodyne operation configuration widens the linear operation region and makes it possible to secure a sufficient transmission distance.

  In addition, the frequency stability of the local oscillation signal and the influence of phase noise can be canceled, and the antenna directivity can be fully utilized, and the input level on the transmission side does not require strict level control, and performance stability It can also be expected to improve the ease of use.

Hereinafter will be described in detail by embodiments thereof microwave band illustrates a wireless communication system and electronic equipment of the present invention.

(First embodiment)
FIG. 1 shows a schematic block diagram of a microwave radio communication system according to the first embodiment of the present invention.

  First, a millimeter-wave band radio transmission apparatus as an example of a transmission-side microwave band radio transmission apparatus includes a reference signal addition / frequency multiplexing circuit 2 as an example of frequency arrangement means, and a frequency as an example of transmission-side frequency conversion means. A conversion / transmission circuit 3, a local oscillator 7, and a transmission antenna 4 are provided.

  In the millimeter wave band radio transmission apparatus, the input modulated wave signal 5a from the terrestrial broadcast antenna 1a and the input modulated wave signal 5b from the satellite broadcast antenna 1b are input to the reference signal addition / frequency multiplexing circuit 2 and input. At the same time as the reference signals are added to the modulated wave signals 5a and 5b, they are arranged on the frequency axis by frequency conversion to generate two series of frequency array signals (intermediate frequency signals). The two series of frequency array signals are added as one series of frequency array signals, and a level-controlled reference signal is added to generate an intermediate frequency multiplexed signal 71d at the stage of the first intermediate frequency band. Input to the conversion / transmission circuit 3. Then, the intermediate frequency multiplexed signal 71d is frequency-converted to the millimeter wave band by the frequency conversion / transmission circuit 3 and amplified, and each frequency-converted radio multiplexed signal 72 is transmitted as a radio signal by the transmitting antenna 4. The

  On the other hand, the millimeter wave band radio receiving apparatus as an example of the microwave band radio receiving apparatus receives the radio multiplex signal from the transmission side and the radio multiplex signal 73 from the reception antenna 14 to reduce the frequency. A frequency conversion / reception circuit 11 as an example of a first reception-side frequency conversion means for conversion, a local oscillator 8 for supplying a local oscillation signal to the frequency conversion / reception circuit 11, and a second reception-side frequency conversion means. As an example, an IF amplification / reference signal reproduction / frequency separation circuit 12 is provided.

  In the millimeter-wave band radio receiver, the frequency conversion / reception circuit 11 is converted into the second intermediate frequency band at one end to generate the intermediate frequency multiplexed signal 74. The intermediate frequency multiplexed signal 74 demultiplexes each signal into a plurality of intermediate signals and a reference signal by a filter, and the demultiplexed reference signal is amplified. Thereafter, a plurality of intermediate frequency signals are converted by the reference signal. By performing frequency conversion, input modulated wave signals 5a and 5b, which are a plurality of broadcast wave signals input on the transmission side, are reproduced, and a plurality of satellite broadcast / terrestrial broadcast tuners 30 in the TV receiver 31 are reproduced. Connected to.

  In the configuration of such a microwave band radio communication system, the radio transmission bandwidth can be expanded so as to support a plurality of input modulated wave signals.

In addition, 1) On the receiving side, the frequency is down-converted to the intermediate frequency band, the reference signal is reproduced and amplified in the IF band, and the frequency is down-converted by the reference signal. That is, the receiving side also reproduces the local oscillation signal. A pseudo-heterodyne operation is performed. Therefore, it is not necessary to strictly control the output levels of the local oscillation signal (frequency fLO), the radio signal (frequency fRF), and the unnecessary single sideband signal on the transmission side.

  2) Since the IF band down converter on the receiving side operates linearly with pseudo-heterodyne operation, the second harmonic component of the mixer does not become a problem, and a plurality of broadcast wave signals which are desired signals in the intermediate frequency band Are demultiplexed and frequency-converted by a plurality of frequency converters using the reference signal as a local oscillation signal, thereby further widening the wireless transmission bandwidth.

3) In addition, on the receiving side, the pseudo-heterodyne operation configuration in which the receiving side performs frequency down-conversion to the intermediate frequency band, and the desired signal is frequency-converted with the reference signal in the intermediate frequency band, thereby increasing the linear operation region and the transmission distance. Can be secured sufficiently.
It can bring about the effect.

  FIG. 2 shows a detailed configuration diagram of the microwave band radio communication system according to the embodiment of the present invention.

  As shown in FIG. 2, a millimeter-band radio transmission apparatus 9 as an example of a microwave band radio transmission apparatus includes two series of frequency conversion circuits 2a and 2b as an example of intermediate frequency conversion means, a reference signal source 2c, A reference signal addition circuit 2d as an example of a multiplexed signal generation unit and a millimeter wave frequency conversion circuit 3a as an example of a transmission side frequency conversion unit are provided.

  The two series of frequency conversion circuits 2a and 2b, the reference signal source 2c, and the reference signal addition circuit 2d constitute the reference signal addition / frequency multiplexing circuit 2 as an example of the frequency arrangement means shown in FIG. Two types of input signals, for example, two types of input modulation wave signals 5a and 5b of broadcast waves, are frequency-converted to an intermediate frequency, and at the same time, frequency multiplexed and a reference signal are added.

  The frequency conversion circuits 2a and 2b include a variable amplifier 200 for amplifying and maintaining an input level to a desired level, a frequency mixer 201, band-pass filters 202a and 202b, and a first IF (intermediate frequency) amplifier. 203. The two series of frequency modulation circuits 2a and 2b are mainly different in the pass bands of the bandpass filters 202a and 202b. This is because the two series of input modulated wave signals 5a (frequency fIF1a) and 5b (frequency fIF1b) are amplified to a certain level by the variable amplifier 200, respectively, and then the intermediate frequency mixer using the reference signal source 2c (frequency FLO1). When converting to the first intermediate frequency band in 201, as shown in FIGS. 3A and 3B, the band-pass filters 202a and 202b are arranged as an upper side band with respect to the reference signal in the system of the input modulated wave signal 5a. In the other input modulated wave signal 5b system, it is arranged as a lower sideband with respect to the reference signal.

The arranged first intermediate frequency signals are:
Input modulation wave signal 5a series: FLO1 + fIF1a
Input modulation wave signal 5b series: FLO1-fIF1b
It becomes. The signals arranged in the first intermediate frequency band are added with the reference signal fLO1 by the reference signal addition circuit 2d at the stage of the first intermediate frequency band, and the two series of signals are synthesized as they are. It becomes composition. The level of the reference signal is controlled by a level controller 95 such as an attenuator or an amplifier. The level controller 95 may be provided between the reference signal source 2c and the intermediate frequency mixer 201. As an example of the first embodiment, the level controller 95 includes a T-type attenuator or a π-type attenuator with the resistance of a chip component. The reference signal adding circuit 2d is composed of two microwave synthesizers 204a and 204b, but a three-signal input microwave synthesizer may be used. The input ports of these two-input and three-input synthesizers are preferably Wilkinson synthesizers that have isolation characteristics. As a result, signals leaking into each input port can be suppressed and each functional circuit can be operated normally.

  FIG. 4 (a) shows a frequency-synthesized signal array. Centering on the reference signal 71c, the upper sideband signal 71a (FLO1 + fIF1a) of the terrestrial broadcast wave and the lower sideband signal 71b (FLO1-fIF1b) of the satellite broadcast wave are arranged to generate an intermediate frequency multiplexed signal 71d. Is done. The desired signal (71a, 71b) and the reference signal 71c in the intermediate frequency multiplex signal 71d can be controlled at respective power levels at the intermediate frequency stage. This is because the input signal is controlled by the variable amplifier 203 and the reference signal is controlled by the level controller 95. As a result, the power level of the desired signal (71a, 71b) in the intermediate frequency multiplexed signal 71d and the reference signal 71c. In the second frequency conversion on the receiving side, when the desired intermediate frequency signal (75a, 75b) is frequency down-converted (detected) with the reference signal 75c, the desired intermediate frequency level can be controlled. It is possible to match the optimal distribution ratio between the frequency and the reference signal, and it is possible to increase the frequency conversion efficiency (reception sensitivity) and extend the wireless transmission distance.

  This intermediate frequency multiplexed signal 71d is then input to the millimeter wave frequency conversion circuit 3a (shown in FIG. 2), and frequency up-converted to a microwave band (in this embodiment, the millimeter wave band) by the local oscillator 7 and the frequency mixer 301. Then, a desired multiplexed signal is filtered by the band pass filter 302. Then, after the multiplexed signal is amplified by the millimeter wave amplifier 303, it is emitted to the space as a wireless multiplexed signal 72 in the millimeter wave band (shown in FIG. 4B) by the transmitting antenna 4. Here, the transmission antenna 4 and the millimeter wave amplifier 303 constitute transmission means. As a preferred embodiment, the frequency mixer 301 uses an N (N is a natural number of 2 or more) order harmonic mixer such as an even harmonic mixer, and the local oscillation frequency of the local oscillator 7 is 1 / N. Can do. Specifically, in the first embodiment, by using a second-order harmonic mixer, the local oscillation frequency of the local oscillator 7 can be halved, and a transmitter with high frequency stability can be obtained by wire bonding. It can be easily manufactured with easy mounting.

The millimeter-wave radio multiplexed signal 72 has the following signal frequency arrangement as shown in FIG.
Reference signal: FLO1 + FLO2
Upper sideband signal: FLO1 + FLO2 + fIF1a
Lower sideband signal: FLO1 + FLO2-fIF1b

  Next, the receiving side will be described.

  As shown in FIG. 2, the millimeter-band radio receiver 10 as an example of the microwave-band radio receiver includes a receiving antenna 14, a frequency conversion circuit 11, a local oscillator 8, a signal distribution circuit 160, and a duplexer. 170, frequency mixers 12a and 12b, an amplifier 180, and amplifiers 195 and 195.

  In the millimeter-band radio receiver 10, the millimeter-wave radio multiplexed signal 73 received by the receiving antenna 14 is input to the frequency conversion circuit 11, amplified once by the low-noise amplifier 110, and then the millimeter-wave band-pass filter. The desired signal filtered by 111 is frequency-converted to the second intermediate frequency band by the frequency mixer 112 using the local oscillation signal (frequency FLO3) from the local oscillator 8 to obtain an intermediate frequency multiplexed signal 74. Here, the receiving means 14 and the low noise amplifier 110 constitute receiving means. As a preferred embodiment, the frequency mixer 112 uses an N (N is a natural number of 2 or more) order harmonic mixer such as an even harmonic mixer, and the local oscillation frequency of the local oscillator 8 is 1 / N. Can do. Specifically, in the first embodiment, by using a second-order harmonic mixer, the local oscillation frequency of the local oscillator 8 can be halved, and a receiving device with high frequency stability can be obtained by wire bonding. It can be easily manufactured with easy mounting.

As shown in FIG. 5A, the intermediate frequency multiplexed signal 74 has the following signal frequency arrangement.
Reference signal: FLO1 + FLO2-FLO3
Upper sideband signal: (FLO1 + FLO2-FLO3) + fIF1a
Lower sideband signal: (FLO1 + FLO2-FLO3) -fIF1b

The intermediate frequency multiplexed signal 74 is amplified at one end by the intermediate frequency amplifier 150 and is divided into three by the signal distribution circuit 160. The signal distribution circuit 160 is preferably distributed by two Wilkinson type two dividers 161 and 162 or Wilkinson type three dividers having isolation characteristics between the output ports. As a result, unnecessary leakage signals can be suppressed at each output port, and each circuit can be operated normally. Each distributed third IF signal is demultiplexed by demultiplexer 170 to only the desired frequencies of the upper sideband signal, the reference signal, and the lower sideband signal. As shown in FIG. 5B, the bandpass filter 171 filters (FLO1 + FLO2−FLO3) + fIF1a which is the upper sideband signal 75a, and the bandpass filter 172 outputs (FLO1 + FLO2−FLO3) which is the reference signal 75c. In the band pass filter 173, the lower sideband signal 75b (FLO1 + FLO2-FLO3) -fIF1b is filtered. The reference signal 75c is amplified and divided into two by the one-end amplifier 180, and becomes a local oscillation signal of the frequency mixers 190a and 190b. The demultiplexed upper sideband signal 75a and lower sideband signal 75b are frequency down-converted by the frequency mixers 190a and 190b using the reference signal 75c to reproduce the input modulation wave signals 5a and 5b on the transmission side. To do. The reproduced input modulated wave signals 76a and 76b are once amplified by an amplifier 195 and connected to the satellite / terrestrial broadcast tuner 30 in the TV receiver 31 via output terminals 500a and 500b. . Here, a signal obtained by reproducing a plurality of broadcast waves from the second intermediate frequency signal is obtained in the following process.
-Reproduction of input modulation wave 5a (terrestrial broadcast wave) from upper sideband signal (frequency conversion):
((FLO1 + FLO2-FLO3) + fIF1a))-(FLO1 + FLO2-FLO3) to fIF1a
-Reproduction of input modulated wave 5b (satellite broadcast wave) from lower sideband signal (frequency conversion):
(FLO1 + FLO2-FLO3)-((FLO1 + FLO2-FLO3) -fIF1b) to fIF1b

  Since a plurality of input modulated wave signals of broadcast waves are obtained from the above process, the frequency mixers 12a and 12b can be linearly operated by increasing the power level with the amplifier 180 that amplifies the reference signal 75c. It is more desirable that the amplifier 180 is an amplifier having an ALC (automatic level control function) or AGC (automatic variable gain function), an injection amplifier realizing a constant level output, or an amplifier with a limiter.

here,
1) At the receiving side, the frequency is down-converted at one end, the reference signal is reproduced and amplified in the IF band, and the frequency is further down-converted by the reference signal. That is, a local oscillation signal is also reproduced at the receiving side, Strict control of the output level of the oscillation signal (frequency fLO), radio signal (frequency fRF) and unnecessary single sideband signal at 1 dB level is not required.

  2) Further, since the IF band down converter on the receiving side performs frequency down-conversion with a plurality of frequency converters that have undergone frequency demultiplexing, the radio transmission bandwidth can be further widened.

3) In addition, on the receiving side, the configuration of the pseudo-heterodyne operation in which the frequency is down-converted to the IF band at one end, and the desired signal is frequency-converted in the IF band with the reference signal, thereby widening the linear operation region and increasing the transmission distance. It is possible to ensure enough.
The effect is also produced.

  Furthermore, since frequency conversion is performed using the reference signal 75c reproduced on the receiving side, it is possible to cancel the frequency stability and phase noise components of the local oscillator 7 on the transmitting side of the millimeter wave and the local oscillator 8 on the receiving side. Further, there is a merit that a local oscillator having strictly frequency stabilization accuracy is not required.

  In addition, the reference signal is reproduced by frequency down-conversion at the final stage on the receiving side, and the frequency conversion is performed using a local oscillation signal having a sufficiently large power level, and the change in output level becomes a gradual characteristic with linear operation. Therefore, the level fluctuation due to the directivity of the antenna also becomes moderate, and the directivity characteristics of the antenna can be sufficiently exhibited. This is greatly different from the case where the output level is a square operation characteristic, even if the reception level of the antenna slightly changes, the output level changes greatly, and the directional characteristic of the antenna becomes equivalently narrow. .

  In the above-described embodiment, the terrestrial broadcast wave and the satellite broadcast wave have been described as the input modulated wave signal. However, a combination of two satellite broadcast waves or a satellite broadcast wave and a CATV (Cable Television) signal may be used. Alternatively, other modulated wave signals may be used as input modulated wave signals.

  In the above embodiment, the millimeter wave band wireless transmission device and the millimeter wave band wireless reception device provided separately from other electronic devices have been described. However, a TV, a video recorder, a DVD (Digital Versatile Disc) player, a personal An electronic device such as a computer (PC) or a refrigerator may be provided with at least one of the microwave band wireless transmission device and the microwave band wireless reception device of the present invention.

  In addition, an electronic device including at least one of the microwave band wireless transmission device and the microwave band wireless reception device of the present invention includes an HDD (hard disk drive) recorder or a DVD recorder and a digital TV tuner. This makes it possible to perform backside recording while watching TV.

  Desirably, the microwave band radio receiver of the present invention is carried in a small electronic device such as a notebook personal computer or a portable terminal so that it can be carried and wirelessly passed through the electronic device. Multi-channel TV viewing and back recording are possible.

  In the above-described embodiment, the radio communication system that transmits and receives a millimeter-wave band radio signal has been described. However, the radio signal is not limited to the millimeter-wave band, and the present invention is applied to the microwave frequency band including the millimeter-wave band. Can be applied.

  In the above embodiment, the reference signal adding circuit 2d as the multiple signal generating means is configured to synthesize the two series of signals from the frequency conversion circuits 2a and 2b and the reference signal. A leak signal leaking from the oscillation signal input terminal to the output terminal side may be used as a reference signal. In this case, since the leakage signal of the frequency converter becomes the reference signal as it is, a separate reference signal addition circuit is not required and the transmission circuit can be simplified.

(Second embodiment)
FIG. 6 shows a schematic configuration diagram of a microwave band radio communication system according to the second embodiment of the present invention. Only the differences from the microwave band wireless communication system of the first embodiment will be described below. The millimeter band wireless transmission device 9 as an example of the microwave band wireless transmission device has the same configuration as the millimeter band wireless transmission device 9 of the first embodiment.

  On the other hand, the millimeter band radio receiver 10 as an example of the microwave band radio receiver is different in the configurations of the frequency conversion receiver circuit 11 and the IF amplification / reference signal reproduction / frequency separation circuit 12. A millimeter-wave band radio multiplexed signal 73 (shown in FIG. 7A) is received by the receiving antenna 14, amplified by the low noise amplifier 110, and then frequency-converted to the second intermediate frequency band by the frequency mixer 112. Until the intermediate frequency multiplexed signal 74 is generated, this is equivalent to the first embodiment. The intermediate frequency multiplexed signal 74 down-converted to the second intermediate frequency band is divided into two by the two dividers 161, and the desired signal becomes the reference signal by the band pass filter 271 and the band pass filter 273 of the branching circuit 270. It is demultiplexed in the state of inclusion.

  This demultiplexing will be described with reference to FIG. Since the intermediate frequency multiplex signal 74 includes a plurality of modulation signals and a reference signal, a pair of composites of the reference signal 75c and the desired signal (upper sideband signal 275a) is obtained by the bandpass filter 271 and the bandpass filter 273. The signal is demultiplexed into a pair of composite signals of a reference signal 75c and a desired signal (lower sideband signal 275b). On the other hand, the composite signal divided into two is composed of a reference signal and desired signals (275a, 275b), and includes a reference signal 75c and a lower sideband signal 275b as an example of a lower side composite signal, and an upper side signal. The reference signal 75c and the upper sideband signal 275a as an example of the composite signal are frequency down-converted by a non-linear device such as a microwave transistor. In the first embodiment, the frequency conversion is performed by the three-terminal frequency mixer having the RF terminal, the LO terminal, and the IF terminal. However, in the second embodiment, the RF terminal and the LO terminal are shared on the input side, Two-terminal frequency mixers 212a and 212b having IF terminals on the output side are configured, and the frequency is down-converted by converting the desired signal in the composite signal with the reference signal. That is, in this configuration, (1) the reference signal 75c and the upper sideband signal 275a, and (2) the reference signal 75c and the lower sideband signal 275b, which are divided and filtered by the two parts, The desired signals (275a, 275b) input to the mixers 212a, 212b are frequency down-converted with the reference signal 75c, and the input modulated wave signals 76a, 76b input on the transmission side can be regenerated.

  The operation of frequency down-conversion by the two-terminal frequency mixers 212a and 212b is the same as that of the three-terminal type frequency mixer of the first embodiment, and the effect obtained by this configuration is almost the same as that of the first embodiment. It is. However, from the stage of the intermediate frequency signal 74, in the stage of frequency down-conversion in order to regenerate the input modulated wave signal, the linearity of the input / output characteristics regarding the frequency down-conversion is the three-terminal configuration of the first embodiment. The mixer operating characteristic in FIG. 4 is somewhat superior in linear operating characteristics because it generates a local oscillation signal in a pseudo manner and drives the mixer with a large signal. However, the configuration is the second intermediate frequency stage, and the configuration is the reference signal 75c. Therefore, the second embodiment can be configured with a simpler configuration and a smaller number of parts.

  The two-terminal frequency mixer used here is composed of non-linear devices such as HEMTs (High Electron Mobility Transistors) and HBTs (Heterojunction Bipolar Transistors). By configuring a gate mixer that inputs the composite signal from the gate of the HEMT, frequency conversion with low loss becomes possible. In this frequency conversion, since the millimeter-wave radio multiplexed signal 73 is converted into an upper sideband signal and a lower sideband signal in the intermediate frequency band by the first frequency down-conversion, the frequency entering the two-terminal frequency mixer is the intermediate frequency. It becomes a signal and the frequency is low. Therefore, the gain of a microwave transistor such as HEMT can be used, high-efficiency frequency conversion characteristics can be obtained, and high reception sensitivity characteristics can be obtained.

(Third embodiment)
FIG. 8 shows a schematic configuration diagram of the microwave radio communication system according to the third embodiment of the present invention. A millimeter-band wireless transmission device 9 as an example of a microwave-band wireless transmission device and a millimeter-band wireless reception device 10 as an example of a microwave-band wireless reception device have the same configuration as that of the second embodiment. In the millimeter-band wireless transmission device 9, the pass characteristics of the filter 202b in the two series of frequency conversion circuits 2b are different.

  FIGS. 9 (a) and 9 (b) show the difference in frequency arrangement due to two series of intermediate frequency conversions. That is, both of the input modulated wave signals 5a and 5b are arranged to use the upper wave with respect to the reference signal fLO1. That is, in the third embodiment, the frequency of the reference signal fLO1 is converted to the upper sideband signals 71a and 71b in the upper intermediate frequency band. At this time, the frequencies of the input modulated wave signals 5a and 5b are converted. The belt is different. As an example, the input modulated wave signal 5a is a terrestrial broadcast wave signal of 470 MHz to 770 MHz, while the input signal 5b is assigned a satellite broadcast wave (intermediate frequency) signal of 1000 MHz to 2100 MHz. Here, the input modulated wave signal 5a and the input modulated wave signal 5b do not overlap in frequency, and the upper sideband signals 71a and 71b, which are signals subjected to intermediate frequency conversion by the reference signal fLO1, do not overlap in frequency. Both are arranged in frequency as the upper side band with respect to the reference signal fLO1, and then added to the reference signal fLO to generate an intermediate frequency multiplexed signal 71d (shown in FIG. 8). The intermediate frequency multiplex signal 71d is frequency up-converted to the millimeter wave band, and the arrangement of the radio multiplex signals 72 transmitted from the transmission antenna 4 is also the upper reference signal fLO1 + fLO2. The arrangement is arranged as fLO1 + fLO2 + fIF1a and fLO1 + fLO2 + fIF1b.

  The input reference signal addition / frequency multiplexing circuit 2 of the millimeter-band wireless transmission device 9 has been described as two series of frequency conversion circuits 2a and 2b in this embodiment, but in the case of this third embodiment, the reference signal fLO1 Therefore, the input signals 5a and 5b are signals before the input reference signal addition / frequency multiplexing circuit 2 because of the configuration using either the upper sideband or the lower sideband (in the description, the upper sideband is used). A configuration may be employed in which a frequency multiplex signal is obtained by synthesizing each signal using a synthesizer (not shown), frequency-converted by only one series of frequency conversion circuits 2a, and a reference signal 71c is added. However, in this case, since the input signal is frequency-multiplexed into a wideband signal, it is desirable that the frequency conversion circuit 2a be configured to reduce distortion with a balanced mixer or the like.

  On the other hand, in the millimeter band radio receiver 10, the difference from the second embodiment is that the radio multiplexed signal 72 is input to the receiving antenna 14 (here, the radio multiplexed signal input to the receiving side is 73 (shown in FIG. 10A) and the characteristics of the filter 373 of the branching circuit 370 are different. In the third embodiment, the band elimination filter 373 is used to form a pair of composite signals of the reference signal 75c and the desired signal (375b). That is, the intermediate frequency multiplexed signal 74 is divided into two by the distributor 160, and a pair of composite signals obtained by combining the reference signal 75c and the upper sideband signal 375a are obtained by the band pass filter 371 as shown in FIG. On the other hand, the upper band signal 375a is removed by the band elimination filter 373, and a pair of composite signals combining the reference signal 75c and the upper band signal 375b are extracted as shown in FIG. 10 (c). Is different.

  The first frequency down-conversion and the second frequency down-conversion are the same as in the second embodiment.

  In the third embodiment, in addition to the merit of the second embodiment, as shown in FIG. 10, the wireless reference signal and a plurality of desired signals can be efficiently arranged, and the frequency bandwidth utilization efficiency is further improved. It becomes possible to make it higher.

  In the description of the third embodiment, the frequency arrangement using the upper sideband signal with respect to the reference signal fLO1 has been described. However, the frequency arrangement using the lower sideband may be used for the reference signal fLO1. In this case, the frequency bands of the filters 202a, 202b, 371, and 373 are appropriately changed.

(Fourth embodiment)
FIG. 11 shows a schematic configuration diagram of a microwave radio communication system according to the fourth embodiment of the present invention. Only differences from the first to third embodiments will be described. A receiving apparatus is configured by using two identical millimeter-wave band radio receiving apparatuses 10a and 10b used in the first to third embodiments. The outputs 15aa and 15ab from the millimeter-wave band radio receivers 10a and 10b are synthesized by the high-frequency synthesizer 82a via the output lines 80a and 80b having the same length, and then output via the output line 83 to the TV. The receiver 31 is connected to the satellite / terrestrial broadcast tuner 30. On the other hand, the respective outputs 15ba and 15bb from the millimeter wave band wireless receiver are similarly synthesized by the high frequency synthesizer 82b via the output lines 81a and 81b having the same length, and the output line 84 is then synthesized. Via the satellite broadcast / terrestrial broadcast tuner 30 of the TV receiver 31. Here, the TV receiver 31 (for example, the satellite broadcast / terrestrial broadcast tuner 30) supplies power to the two millimeter-wave band radio receivers 10a and 10b via either of the output lines 83 or 84. Is supplied. FIG. 11 shows a case where DC (direct current) power is supplied from the output line 84.

Next, the operation of the microwave band wireless communication system will be described. A radio multiplex signal 72 is transmitted from one transmitter 9 and received as a radio multiplex signal 73 by the millimeter wave band radio receivers 10a and 10b. Here, the radio multiplexed signal 73 includes a radio reference signal 73c and radio reference signals 73a and 73b. The radio multiplexed signal 73 received by the millimeter wave band radio receivers 10a and 10b has different radio transmission distances from the transmitter 9, and considering the difference in phase angle with respect to the millimeter wave band radio receiver 10a, the above two millimeters. The phase of the radio multiplexed signal 73 input to the waveband radio receiver is, for example, Δθ compared to the phase of the radio multiplexed signal 73 input to the millimeter wave band radio receiver 10b compared to the millimeter wave radio receiver 10a. Only different. Therefore, the phase information of the radio multiplexed signal input to each of the millimeter wave band radio receivers 10a and 10b is as follows. Here, the transmission time from the millimeter wave band wireless transmission device 9 is t.
The input phase to the receiving antenna 14a of the millimeter wave band radio receiving apparatus 10a:
Reference signal: 2π (fLO1 + fLO2) t
Wireless signal (upper side wave): 2π (fLO1 + fLO2 + fIF1a) t
Radio signal (lower side wave): 2π (fLO1 + fLO2-fIF1b) t
Furthermore, the phase information changes as follows by the first receiving side frequency conversion. Here, the frequency fLO3a and the phase information of the local oscillator used for the first frequency conversion of the millimeter wave band radio receiving apparatus 10a are θrxa.
Change in input phase angle associated with the first frequency conversion of the millimeter wave band radio receiver 10a:
Reference signal: 2π (fLO1 + fLO2-fLO3a) t-θrxa
Radio signal (upper side wave): 2π (fLO1 + fLO2 + fIF1a−fLO3a) t−θrxa
Radio signal (lower side wave): 2π (fLO1 + fLO2-fIF1b-fLO3a) t-θrxa
Furthermore, in the second receiving side frequency conversion, the reference signal extracted by the filter means is used as a local oscillation source, and the intermediate frequency radio signal is frequency converted. Therefore, the upper side wave and the lower side wave of the intermediate frequency signal are Can be expressed as:
・ Radio signal (upper side):
[2π (fLO1 + fLO2 + fIF1a−fLO3a) t−θrxa]
− [2π (fLO1 + fLO2−fLO3a) t−θrxa] = ( fIF1a ) · 2πt
・ Radio signal (lower side):
[2π (fLO1 + fLO2-fLO3a) t-θrxa]
− [2π (fLO1 + fLO2−fIF1b−fLO3a) t−θrxa] = ( fIF1b ) · 2πt
Thus, a radio signal (upper side wave) ( fIF1a ) · 2πt is obtained at the receiving side output unit 15aa, and a radio signal (lower side wave) ( fIF1b ) · 2πt is obtained at the receiving side output unit 15ab.

On the other hand, the change in the phase angle on the millimeter wave band radio receiving apparatus 10b side changes to the above-mentioned change in the phase angle, and the phase angle changes as follows when the difference in transmission distance is uniformly Δθ1.
The input phase to the receiving antenna 14a of the millimeter wave band radio receiving apparatus 10a:
Reference signal: 2π (fLO1 + fLO2) t + θ1
Wireless signal (upper side wave): 2π (fLO1 + fLO2 + fIF1a) t + θ1
Wireless signal (lower side wave): 2π (fLO1 + fLO2-fIF1b) t + θ1
Further, the phase information changes as follows by the first receiving side frequency conversion. Here, the frequency fLO3b and the phase angle of the local oscillator used for the first frequency conversion of the millimeter wave band radio receiving apparatus 10b are θrxb. .
Change in input phase angle associated with the first frequency conversion of the millimeter wave band radio receiving apparatus 10b:
Reference signal: 2π (fLO1 + fLO2-fLO3a) t + θ1-θrxb
Radio signal (upper side wave): 2π (fLO1 + fLO2 + fIF1a-fLO3b) t + θ1−θrxb
Wireless signal (lower side wave): 2π (fLO1 + fLO2-fIF1b-fLO3b) t + θ1-θrxb
Further, in the second reception side frequency conversion, the intermediate frequency radio signal is frequency converted using the reference signal extracted by the filter means as the local oscillation source. Here, the change in the reference signal input phase angle after the first frequency conversion of the millimeter wave band radio receiving apparatus 10b is as follows:
2π (fLO1 + fLO2-fLO3b) t + θ1-θrxb
Therefore, the upper side wave and the lower side wave of the intermediate frequency signal can be expressed as follows.
・ Radio signal (upper side):
[2π (fLO1 + fLO2 + fIF1a-fLO3b) t + θ1−θrxb]
− [2π (fLO1 + fLO2−fLO3b) t + θ1−θrxb] = ( fIF1a ) · 2πt
・ Radio signal (lower side):
[2π (fLO1 + fLO2-fLO3b) t + θ1-θrxb]
− [2π (fLO1 + fLO2−fIF1b−fLO3b) t + θ1−θrxb] = ( fIF1b ) · 2πt
Thus, the receiving-side output unit 15ab obtains a radio signal (upper side wave) ( fIF1a ) · 2πt , and the receiving-side output unit 15bb obtains a radio signal (lower side wave) ( fIF1b ) · 2πt. The output phase by the device 10b is the same as the output phase of the millimeter wave band radio receiving device 10a.

  Therefore, the in-phase synthesis can be easily performed by synthesizing the outputs of the millimeter wave band radio receiving apparatuses 10a and 10b via the output lines having the same length. Therefore, the reception output level can be increased and the spatial diversity effect can also be obtained.

  In the microwave radio communication system according to the fourth embodiment, the length of the radio transmission path of the radio multiplexed signal input to a plurality of millimeter wave radio receivers is different. In the intermediate frequency band stage, that is, the reference signal reproduction / frequency separation stage, the reproduced reference signal and the intermediate frequency signal contain the same phase information regarding the transmission distance. That is, in the second frequency conversion means, when the intermediate frequency signal is down-converted with the reference signal, distance information is canceled in the radio transmission interval in the frequency converted signal. The reception output of the millimeter wave band wireless reception device can be synthesized in phase if the output lines of the output of the millimeter wave band wireless reception device have the same length. As a result, the reception output can be increased, and as a result, the frequency conversion efficiency (reception sensitivity) at the second frequency conversion can be increased on the reception side, and the transmission distance can be increased. In addition, even if the antenna portion in the millimeter wave band wireless receiver is blocked by a human body, an object, etc., if at least one millimeter wave band wireless receiver receives a signal without being blocked from the transmission side, A desired signal can be received, and a spatial diversity effect can be easily obtained.

  In the microwave band wireless communication system shown in the fourth embodiment, as shown in FIG. 12, a distance of at least one wavelength (1 · λ) or more is provided on both sides of a flat panel display 40 such as a TV or a personal computer. By installing the millimeter wave band wireless receivers 10b and 10b and receiving the radio multiplexed signal from the millimeter band wireless transmitter 9, a more efficient diversity effect can be obtained. For example, even if a human body or an object is obstructed by setting the size of the flat panel display 40 to about 15 inches, the transmission side is not blocked by at least one millimeter-wave band radio receiving device, so that continuous reception is possible. It is possible to obtain continuous video, data, and the like.

FIG. 1 is a schematic configuration diagram of a microwave band radio communication system of the present invention. FIG. 2 is a block diagram of the microwave radio communication system according to the first embodiment of the present invention. FIG. 3 is a diagram showing a frequency arrangement in a plurality of input modulated wave signals on the transmission side / reception side and each sequence in the first and second intermediate frequency bands in the first embodiment. FIG. 4 is a diagram showing the frequency arrangement of the intermediate frequency multiplexed signal and the frequency arrangement of the radio multiplexed signal in the first intermediate frequency band on the transmission side in the first embodiment. FIG. 5 is a diagram showing the frequency arrangement of the radio multiplexed signal received on the receiving side of the first embodiment, the frequency arrangement of the intermediate frequency multiplexed signal in the second intermediate frequency band, and the filter characteristics. FIG. 6 is a configuration diagram of a microwave band radio communication system according to the second embodiment of the present invention. FIG. 7 is a diagram showing the frequency arrangement of radio multiplexed signals received on the receiving side of the second embodiment, the frequency arrangement of intermediate frequency multiplexed signals in the second intermediate frequency band, and the filter characteristics. FIG. 8 is a block diagram of a microwave radio communication system according to the third embodiment of the present invention. FIG. 9 is a diagram showing a frequency arrangement in a plurality of input modulated wave signals on the transmission side / reception side and each series in the first and second intermediate frequency bands in the third embodiment. FIG. 10 is a diagram showing the frequency arrangement of the radio multiplexed signal received on the receiving side of the third embodiment, the frequency arrangement of the intermediate frequency multiplexed signal in the second intermediate frequency band, and the filter characteristics. FIG. 11 is a block diagram of a microwave radio communication system according to the fourth embodiment of the present invention. FIG. 12 is a diagram showing a usage pattern of the microwave band wireless communication system of the fourth embodiment. FIG. 13 is a configuration diagram of a conventional microwave radio communication system. FIG. 14 is a diagram showing a frequency arrangement of multiplexed signals in the radio frequency band of the microwave band radio communication system.

Explanation of symbols

DESCRIPTION OF SYMBOLS 1a ... Terrestrial broadcast antenna 1b ... Satellite broadcast antenna 2 ... Reference signal addition / frequency multiplexing circuits 2a, 2b ... Frequency conversion circuit 2c ... Reference signal source 2d ... Reference signal addition circuit 3 ... Frequency conversion / transmission circuit 4 ... Transmission Antennas 5a, 5b ... Input modulated wave signals 7, 8 ... Local oscillator 9 ... Millimeter wave radio transmitter 10 ... Millimeter wave radio receiver 11 ... Frequency converter / receiver circuit 12 ... IF amplifier / reference signal regeneration / frequency separator circuit 12a, 12b ... frequency mixers 14, 14a, 14b ... receiving antennas 15a, 15b, 500a, 500b, 15aa, 15ab, 15ba, 15bb ... output terminal 30 ... satellite / terrestrial broadcast tuner 31 ... TV receiver 71a ... Upper sideband signal 71b ... Lower sideband signal 71c ... Reference signal 71d ... Intermediate frequency multiplexed signal 72 ... Radio multiplexed signal 73 ... Radio multiplexed signal 74 ... Intermediate frequency multiplexed signal 75a ... Upper sideband signal 75b ... Lower side Waveband signal 75c ... reference signals 76a, 76b ... input modulation wave signal (receiving side)
80a, 80b ... output lines 81a, 81b ... output lines 82a, 82b ... high frequency synthesizer 83 ... output line 84 ... output line 95 ... level controller 160 ... distribution circuit 170, 270, 370 ... branching circuit 171, 172, 173 ... Bandpass filter 180 ... Amplifier (Amplifier with two distribution functions)
DESCRIPTION OF SYMBOLS 200 ... Variable amplifier 201 ... Frequency mixer 202a, 202b ... Band pass filter 203 ... IF (intermediate frequency) amplifier 204a, 204b ... Microwave synthesizer 212a, 212b ... Frequency mixer 271, 273 ... Band pass filter 275a ... Upper side band signal 275b ... Lower sideband signal 301 ... Frequency mixer 302 ... Bandpass filter 303 ... Millimeter wave amplifier 371 ... Bandpass filters 375a, 375b ... Upper sideband signal 373 ... Band rejection filter

Claims (7)

A frequency arrangement means for converting a plurality of input modulated wave signals to an intermediate frequency band and arranging them on a frequency axis, and generating an intermediate frequency multiplexed signal by adding a reference signal to the signals arranged on the frequency axis; A transmission-side frequency conversion means for frequency-converting the intermediate frequency multiplexed signal generated by the frequency arrangement means to a microwave band, and a multiplexed signal frequency-converted to the microwave band by the transmission-side frequency conversion means A microwave band wireless transmission device having transmission means for transmitting as a signal ;
Receiving means for receiving a radio multiplexed signal transmitted from the microwave radio transmitting apparatus; first receiving side frequency converting means for frequency down-converting the radio multiplexed signal received by the receiving means to an intermediate frequency band; Filter means for extracting a reference signal and a desired intermediate frequency signal from the intermediate frequency multiplexed signal converted by the first receiving side frequency conversion means, and the desired signal by the reference signal extracted by the filter means. Microwave band radio reception having second reception side frequency conversion means for regenerating at least one of the plurality of input modulation wave signals input on the transmission side by frequency down-converting the intermediate frequency signal Equipment and
With
A microwave radio communication system using a plurality of the microwave radio receivers,
The above-mentioned plurality of microwave band wireless receivers are installed on a flat panel display,
The microwave band wireless communication system, wherein outputs from the plurality of microwave band wireless receivers are combined and input to the flat panel display. In the microwave radio | wireless communications system of Claim 1 ,
A microwave radio communication system, wherein outputs from the plurality of microwave radio receivers are combined via output lines having the same length. In the microwave radio | wireless communications system of Claim 2 ,
A microwave band radio communication system, wherein a DC voltage is supplied to each of the plurality of microwave band radio receivers via the output line. In the microwave radio | wireless communications system of Claim 3 ,
The DC voltage, microwave-band radio communication system, wherein a plurality of microwave-band radio receiver is supplied from the connected electronic equipment. An electronic apparatus characterized by comprising at least one of microwave-band radio communication system according to any one of claims 1 to 4. The electronic device according to claim 5 ,
An electronic device comprising a hard disk recorder or DVD recorder and a digital television tuner. The electronic device according to claim 5 or 6 ,
An electronic device characterized by being a portable device that is small and portable.

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