JP2006203998A - Uninterruptible power supply unit - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide an uninterruptible power supply unit where there is no fear of overcharge and its recovery charge time is short. <P>SOLUTION: This uninterruptible power supply unit, which charges a battery 6 while supplying output terminals C and D with power supplied to input terminals A and B and supplies the output terminals with power from the battery when the power supply to the input terminals is interrupted, is provided with a battery charge maximum power value control means so as to charge the battery with charge voltage higher than recommended charge voltage until a specified time passes after recovery from power failure. The battery charge power maximum value control means is equipped with a current detector 4 which detects an input current, a current detector 5 which detects a battery charge current, an A/D converter 1010 which generates a voltage value Vcset for setting the charge power maximum value, receiving the current value information Ii and Ic from these current detectors and the input voltage Vi information obtained based on input voltage, a CPU1011, and a D/A converter 1012. <P>COPYRIGHT: (C)2006,JPO&NCIPI

Description

  The present invention relates to an uninterruptible power supply, and more particularly to shortening the recovery charge time of the uninterruptible power supply.

  Various means are considered in order to improve the reliability and operability of information devices such as computers and information processing systems. The uninterruptible power supply is also one of the effective means, and the power supply is indispensable for the system operation, which greatly contributes to the improvement of system reliability and operability.

  An example of a conventional uninterruptible power supply having such a function is shown in FIG.

  The uninterruptible power supply 7 in FIG. 10 includes input terminals A and B, a filter circuit 2 connected to the input terminals A and B, an overcurrent protector 3 connected to the filter circuit 2, and an overcurrent protector 3 The high power factor rectifier circuit 30 connected to the inverter circuit 40, the inverter circuit 40 connected to the high power factor rectifier circuit 30, the output terminals C and D connected to the inverter circuit 40, the overcurrent protector 3 and the high power factor. At the connection point between the charging circuit 20 connected to the AC input terminals E and F, which are the connection points with the rectification circuit 30, the battery 6 connected to the charging circuit 20, the high power factor rectification circuit 30 and the inverter circuit 40. A booster circuit 50 connected between certain DC terminals G and H and battery voltage terminals I and J which are connection points of the charging circuit 20 and the battery 6, and a charging current flowing between the charging circuit 20 and the battery 6 A current detector 5 for detecting And a charger control circuit 60 connected to the current detector 5 and the battery voltage terminal I and connected to the charging circuit 20 (see, for example, Non-Patent Document 1. For the charger control circuit 60, for example, (Refer nonpatent literature 2.).

  In the uninterruptible power supply of FIG. 10, AC power input from the input terminals A and B is input to the high power factor rectifier circuit 30 via the filter circuit 2, the overcurrent protector 3, and the AC input terminals E and F. Is done.

  The high power factor rectifier circuit 30 includes, for example, a reactor and a high-speed switching element MOSFET (Metal Oxide Semiconductor Field Effect Transistor), and controls an AC power supply voltage input via the AC input terminals E and F by controlling the opening and closing of the MOSFET. DC power whose voltage is stabilized by boosting is supplied to the DC terminals G and H, and the input current waveform is controlled to be similar to the input voltage waveform, and as a result, power factor improvement control is performed. The DC power supplied from the high power factor rectifier circuit 30 to the DC terminals G and H is input to the inverter circuit 40.

  The AC power supplied to the AC input terminals E and F is also input to the charging circuit 20 whose output voltage (charging voltage) is stabilized and controlled by the charging control circuit 60.

  The charging circuit 20 includes, for example, a MOSFET 2009, a transformer 2008, rectifier diodes 2001 to 2004, 2007 and 2010 to 2011, reactors 2005 and 2012, and capacitors 2006 and 2013 as shown in the figure. Then, the charging circuit 20 opens and closes the MOSFET 2009 according to the control of the charger control circuit 60, converts the AC power supply voltage input via the AC input terminals E and F into a predetermined stabilized DC voltage, and serves as battery charging power. The battery 6 is supplied via battery voltage terminals I and J.

  The charger control circuit 60 includes, for example, error amplifiers 1001 and 1006, reference voltage sources 1005 and 6001, resistors 1002 and 1007, a comparator 1003, a sawtooth generator 1008, and a drive circuit 1004 as shown in the figure. Yes. The charger control circuit 60 controls the battery charging voltage value based on the charging current information from the current detector 5, and when the battery charging current is greater than or equal to a predetermined current value, the stabilized output voltage value from the charging circuit 20. Is controlled to be equal to or less than a predetermined amount (the charging current is equal to or less than a predetermined value), and as a result, the battery 6 is charged with constant current and constant voltage.

  The output of the charging circuit 20 is supplied to the battery 6 via the battery voltage terminals I and J as described above, and is also input to the booster circuit 50. The output of the booster circuit 50 is input to the inverter circuit 40 via the DC terminals G and H.

  The inverter circuit 40 to which the output of the high power factor rectifier circuit 30 and the output of the booster circuit 50 are supplied includes, for example, an AC filter including a MOSFET, a transformer, a reactor, and a capacitor. The DC power input via G and H is intermittent. A predetermined intermittent power induced on the secondary side of the transformer by the open / close control of the MOSFET is applied to the AC filter circuit. The AC filter circuit smoothes the intermittent power and supplies it to a load device (not shown) via the output terminals C and D as a predetermined AC output voltage Vo.

  When a power failure occurs in the above configuration, that is, when the AC power input between the input terminals A and B (or between the AC input terminals E and F) is interrupted, the output from the charging circuit 20 and the high power factor rectifier circuit 30, respectively. The predetermined DC power that is applied is cut off. At this time, the DC power from the battery 6 is boosted by the booster circuit 50 as necessary, and supplied to the inverter circuit 40 via the DC terminals G and H. As a result, even when a power failure occurs, the inverter circuit 40 can supply AC power of a predetermined AC output voltage Vo to the load device via the output terminals C and D for a predetermined time.

  The sum of the rated output power (larger is better) and the initial charging power (Pout + Pcha) corresponding to the recovery charge time (shorter is better) as a major factor that determines the superiority or inferiority of the performance of the uninterruptible power supply as described above is The input allowable minimum voltage (Viacmin) and the input current limit value (Iiaclim × α) are determined. That is, the input current is Iiac, the allowable output power is Pout, the charging initial power is Pcha, the overall efficiency is η, the overall power factor is ξ, the input allowable minimum voltage is Viacmin, the overcurrent detection current of the overcurrent protector 3 is Iiaclim, When the reduction rate of the overcurrent protector 3 is α, these relationships are expressed by Equation 1.

  Here, a general inverter type uninterruptible power supply apparatus having a high power factor rectifier circuit having an output capacity of about 945.6 [W], a battery backup time of about 6 minutes, and the like is generally considered. In such an uninterruptible power supply, the overall efficiency η, the overall power factor ξ and the like depend on the circuits and components used, but at present, the overall efficiency η is 0.85 for reasons such as economy. The overall power factor ξ is about 0.95 to 0.99. Here, the overall efficiency η = 0.87 and the overall power factor ξ = 0.97. The capacity of the battery 6 to be used is selected to be approximately 48V7Ah, and the overcurrent detection current Iiaclim of the overcurrent protector 3 is selected to be 15 [A], and the reduction rate α of the overcurrent protector 3 = α = About 0.95 is selected. Here, these values are adopted. Under such conditions, if the allowable input minimum voltage is Viacmin = 85 [V], the power that can be consumed for the initial charging power Pcha can be obtained by Equation 2.

  In addition, as a battery 6 having a capacity of 48V7Ah, a case where four 12V7Ah batteries widely distributed in the market are connected in series will be considered. Generally, for a 12V battery, the recommended charging voltage value provided by the battery manufacturer is about 13.65V, and the charging voltage when four such batteries are used in series is about 54.60V. Since the charging initial power that can be consumed as the battery charging power is equal to or less than 76.6 [W] as determined by the above formula 2, the charging initial current is 1.4 (= 76.6 (W) /54.6 (V )) [A]. In this case, the recovery charge time (100% charge) is 7.4 hours in the example shown in FIG. 3 (the graph of the charge voltage (V) and the recovery charge time (hours)). It becomes a constant value without depending on the output power used. In other words, the recovery charging time of the conventional uninterruptible power supply is uniquely determined by the charging voltage, and consequently the set voltage of the reference voltage source 6001 in the charging control circuit 60.

  In addition, as another conventional uninterruptible power supply device, there is one in which the charging current to the storage battery is controlled within the range of the rated current of the charger according to the fluctuation of the supply current to the load (for example, patent Reference 1).

Katsuya Hirachi, “Transition of Mini UPS Circuit System and Future Issues”, IEICE Technical Report, The Institute of Electronics, Information and Communication Engineers, February 2004, EE 2003-57, p. 1-6 (especially p.2-4) Akira Hasegawa, “Switching regulator design know-how”, CQ Publishing, April 10, 1985, p. 115-119 JP-A-7-170677

  As described above, the conventional uninterruptible power supply is configured to perform constant current and constant voltage charging. Therefore, the recovery charging time is constant regardless of the load factor of the actual load power of the uninterruptible power supply. It's time. However, the actual usage of the uninterruptible power supply is to use a load power lower than the rated output power of the uninterruptible power supply in consideration of a decrease in battery backup time at the end of the battery life (about 1/2). Often done. Thus, if the load power is lower than the rated output power, it should be possible to direct more power to charge the battery. That is, it should be possible to use more current for charging the battery within the limit current of the overcurrent protector 3 of the uninterruptible power supply, thereby shortening the recovery charge time. Nevertheless, the conventional uninterruptible power supply device takes a long recovery charge time that depends on a certain initial charge power that is limited from the rated output power. In other words, the conventional uninterruptible power supply takes longer than necessary to reach a fully charged state or 90% charged state that can guarantee a predetermined battery backup time, and as a result, the operability of the system is sufficiently improved. There is a problem that it is not possible.

  In addition, in the conventional uninterruptible power supply that controls the charging current according to the fluctuation of the supply current to the load, only the rated current of the charger is considered, so that there is a problem that overcharging may occur.

  SUMMARY OF THE INVENTION An object of the present invention is to provide an uninterruptible power supply apparatus that has no fear of overcharging and has a short recovery charging time.

  In order to achieve the above object, the present invention has the following features.

  According to the first aspect of the present invention, the battery is charged while supplying the power supplied from the outside to the input terminal to the output terminal, and when the supply of power to the input terminal is cut off, the battery In an uninterruptible power supply that supplies power to an output terminal, a battery charge maximum power value that controls a maximum charge power value of the battery until a predetermined time elapses after detection of restart of power supply to the input terminal Control means is provided.

  Moreover, according to the second aspect of the present invention, in the uninterruptible power supply, the battery charging maximum power value control means maintains the input current flowing through the input terminal below a predetermined input current limit value, The charging voltage of the battery is set higher than the recommended charging voltage.

  Furthermore, according to the third aspect of the present invention, in the uninterruptible power supply, the battery charge maximum power value control means is configured until the input current flowing through the input terminal exceeds a predetermined value or the charge voltage is set in advance. The charging voltage is increased stepwise until a set charging voltage setting maximum value is exceeded, and when the input current flowing through the input terminal exceeds the predetermined value, or the charging voltage is set in advance. When the set maximum value is exceeded, the charging voltage is lowered by one step.

  According to the present invention, the battery charging maximum power value control means for controlling the maximum charging power value of the battery until a predetermined time elapses after recovering from the power failure, there is no fear of overcharging. Therefore, it is possible to provide an uninterruptible power supply with high operability.

  Next, embodiments of the present invention will be described in detail with reference to the drawings.

  FIG. 1 is a circuit diagram showing an uninterruptible power supply 1-1 according to the first embodiment of the present invention. In the figure, the same reference numerals are given to the same components as in the prior art, and the description thereof is omitted.

  The uninterruptible power supply 1-1 shown in the figure detects current (input current) flowing between the overcurrent protector 3 and the AC input terminal E in addition to the conventional configuration, and input current information representing the magnitude thereof. It has a current detector 4 for generating Ii. Further, the uninterruptible power supply 1-1 has a charger control circuit 10 instead of the conventional charger control circuit 60. In addition to the input current information Ii from the current detector 4, the charging current information Ic from the current detector 5, and the battery charging voltage Vch from the battery voltage terminal I, the charger control circuit 10 includes an AC input terminal E, A voltage between F (input voltage) is input.

  In place of the conventional reference voltage source 6001, the charger control circuit 10 includes an input voltage detection circuit 1009 that generates input voltage information Vi from a voltage (input voltage) between AC input terminals E and F, and an input voltage detection circuit 1009. Input voltage information Vi, input current information Ii from current detector 4, and charging current information Ic from current detector 5, and A / D convert them to input voltage information Vid and input current information Iid, respectively. A / D converter 1010 that outputs charging current information Icd, and charging voltage setting value (target voltage value) based on input voltage information Vid, input current information Iid, and charging current information Icd from A / D converter 1010 A CPU (arithmetic unit) 1011 that generates Vcdset and a D / A converter 1012 that outputs a voltage value Vcset corresponding to the charging voltage setting value Vcdset are included. These input voltage detection circuit 1009, current detectors 4 and 5, A / D converter 1010, CPU 1011 and D / A converter 1012 function as a battery charge maximum power value control means.

  Hereinafter, the operation of the uninterruptible power supply 1-1 of FIG. 1 will be described focusing on differences from the conventional uninterruptible power supply 7.

  The AC power supplied to the input terminals A and B is supplied to the charging circuit 20 and the high power factor rectifier circuit 30 via the filter circuit 2, the overcurrent protector 3, the current detector 4, and the AC input terminals E and F. Then, the current detector 4 detects the current flowing between the overcurrent protector 3 and the AC input terminal E. Then, the current detector 4 outputs input current information Ii indicating the magnitude of the detected current. Further, the voltage (input voltage) between the AC input terminals E and F is converted into input voltage information Vi by the input voltage detection circuit 1009 in the charger control circuit 10.

  In the charger control circuit 10, the A / D converter 1010 outputs the input voltage information Vi output from the input voltage detection circuit 1009, the input current information Ii output from the current detector 4, and the current detector 5. The charging current information Ic is A / D converted and supplied to the CPU 1011.

  For example, the CPU 1011 operates as shown in FIG. That is, first, in step S2-1, the CPU 1011 presets an elapsed time H from power failure recovery based on the input voltage information Vid that is digitized via the input voltage detection circuit 1009 and the A / D converter 1010. A predetermined elapsed time set value Hset is compared. Here, the elapsed time setting value Hset is a predetermined value that can sufficiently charge the battery when the charging voltage setting value Vcdset is set to a predetermined value lower than the recommended charging voltage, and is higher than the recommended charging voltage. Even when it is set to (= Vcdmax), it can be arbitrarily set from the time when there is no burden on the battery (due to excessive charging voltage). The elapsed time set value Hset is input and set in advance from an input setting unit (not shown) and stored in a memory (not shown).

  If the CPU 1011 determines that H ≦ Hset is not satisfied as a result of step S 2-1, the CPU 1011 proceeds to step S 2-7 and holds the charging voltage setting value Vcdset at Vcd 0. Here, Vcd0 is a recommended charging voltage value presented by the battery manufacturer, is preset by an input setting unit (not shown), and is stored in a memory (not shown).

  On the other hand, if the CPU 1011 determines in step S2-1 that H ≦ Hset, the process proceeds to step S2-2, and the input current information Iid and the input current limit value Iidlimit quantified via the A / D converter 1010 are obtained. Compare. Here, the input current limit value Iidlimit can be arbitrarily set as long as it is smaller than the maximum value (<Iiaclim) determined based on the overcurrent detection current Iiaclim of the overcurrent protector 3. The input current limit value Iidlimit is previously set by an input setting unit (not shown) and stored in a memory (not shown).

  If the CPU 1011 determines that Iid <Iidlimit is not satisfied as a result of the comparison in step S2-2, the CPU 1011 proceeds to step S2-3 and decreases the charging voltage setting value Vcdset by, for example, a predetermined amount.

  On the other hand, if the CPU 1011 determines that Iid <Iidlimit as a result of the comparison in step S2-2, the CPU 1011 proceeds to step S2-4 and compares the charging voltage setting value Vcdset with the charging voltage setting maximum value Vcdmax. Here, the charging voltage setting maximum value Vcdmax is a charging voltage value used for cycle use charging of the battery, and is input and set in advance by an input setting unit (not shown) and stored in a memory (not shown).

  If the CPU 1011 determines that Vcdset <Vcdmax is not satisfied as a result of the comparison in step S2-4, the CPU 1011 proceeds to step S2-5 and decreases the charging voltage set value Vcdset by, for example, a predetermined amount.

  On the other hand, if the CPU 1011 determines that Vcdset <Vcdmax as a result of the comparison in step S2-4, the CPU 1011 proceeds to step S2-6 and increases the charging voltage setting value Vcdset by, for example, a predetermined amount.

  As described above, the CPU 1011 adjusts the charging voltage setting value Vcdset based on the input voltage information Vid, the input current information Iid, and the charging current information Icd.

  Note that FIG. 2 does not show the operation based on the charging current information Icd, but the charging current information Icd is used to limit the charging current as described later. Specifically, the CPU 1011 compares the charging current information Icd with the charging current limit value Icdlimit set in advance by the input setting unit. This comparison is performed, for example, between steps S2-2 and S2-4. If Icd <Icdlimit, the process proceeds to step S2-4. Otherwise, the process proceeds to step S2-3 or S2-5. Thus, the CPU 1011 adjusts the charging voltage setting value Vcdset so that the charging current does not exceed a predetermined value.

  Returning to FIG. 1, the charging voltage setting value Vcdset obtained through the processing as described above is supplied from the CPU 1011 to the D / A converter 1012. The D / A converter 1012 performs D / A conversion on the charging voltage setting value Vcdset, which is the charging voltage target voltage value, and outputs the converted voltage value Vcset to the inverting input terminal of the error amplifier 1006.

  The error amplifier 1006 receives the battery charging voltage Vch from the charging circuit 20 at its non-inverting input terminal. The error amplifier 1006 generates an output voltage corresponding to the difference between the battery charging voltage Vch from the charging circuit 20 and the charging voltage set value Vcset from the D / A converter 1012. That is, the error amplifier 1006 outputs an error amplification voltage Ev corresponding to βv times (= amplification factor of the error amplifier 1006) of the difference (Vch−Vcset) between the battery charging voltage Vch and the charging voltage setting value Vcset. The error amplification voltage Ev is applied to the other end of the resistor 1007 whose one end is connected to the connection point between the other end of the resistor 1002 connected to the output terminal of the error amplifier 1001 and the inverting input terminal of the comparator 1003. Supplied.

  On the other hand, the charging current information Ic (Ic is a voltage value) from the current detector 5 is input to the non-inverting input terminal of the error amplifier 1001, and the reference voltage Vref for setting the battery charging current is input to the inverting input terminal. 1005 is input. The error amplifier 1001 outputs an error amplification voltage Ei corresponding to βi times (= amplification factor of the error amplifier 1001) of the difference (Ic−Vref) between the charging current information Ic and the reference voltage Vref. The error amplification voltage Ei is supplied to the inverting input terminal of the comparator 1003 through the resistor 1002.

  The error amplification voltages Ei and Ev of the error amplifiers 1001 and 1006 added through the resistors 1002 and 1007 are input to the inverting input terminal of the comparator 1003 as the control signal E. The sawtooth wave signal S from the sawtooth wave generator 1008 is input to the non-inverting input terminal of the comparator 1003. The comparator 1003 compares the control signal E with the sawtooth wave signal S, and generates a pulse signal having a pulse width Δt corresponding to the level of the control signal E.

  The pulse signal generated by the comparator 1003 is supplied to the drive circuit 1004. The drive circuit 1004 generates a control pulse signal T1 in response to the pulse signal from the comparator 1003, and performs open / close control of the MOSFET 2009 of the charging circuit 20.

  As a result of the operation as described above, in the uninterruptible power supply 1-1 of FIG. 1, the battery charging current value becomes equal to or higher than the charging voltage setting value Vcset that is set in consideration of the input current limitation or the charging voltage limitation value of the battery. In this case, the MOSFET 2009 is controlled so as to lower the stabilized output voltage value (charge voltage Vch) supplied from the charging circuit 20 to the battery 6, and as a result, the battery 6 is charged with constant current and constant voltage. Therefore, in this embodiment, there is no fear of overcharging.

  Also in the uninterruptible power supply 1-1 of FIG. 1, the sum of the rated output power (larger is better) and the initial charge power that determines the recovery charge time (shorter is better) is the minimum allowable input voltage and input current. Determined from the limit value. That is, the input current Iiac is the allowable output power Pout, the charging initial power Pcha, the overall efficiency η, the overall power factor ξ, the input allowable minimum voltage Viacmin, the overcurrent detection current of the overcurrent protector 3 is Iiaclim, The reduction rate of the overcurrent protector 3 is represented by Equation 3 (= Equation 1), where α is α.

  Here, the output capacity is 945.6 [W], the battery backup time is 6 minutes, the overall efficiency η = 0.87, the overall power factor ξ = 0.97, the capacity of the battery used = 48V7Ah, the overcurrent protector 3 Overcurrent detection current Iiaclim = 15 [A], reduction rate α = 0.95 of the overcurrent protector 3, and input allowable minimum voltage Viacmin = 85 [V], the power that can be consumed for the initial charge power Pcha is It is given by Equation 4.

  Similarly, when the output capacity is 944.7 [W], 943.0 [W], 941.4 [W], 939.7 [W], 938.0 [W], it can be consumed as the charging initial power Pcha. The power is given by Equations 5 to 9, respectively.

  In the uninterruptible power supply 1-1 according to the present embodiment, by setting a value corresponding to the output capacity as the input current limit value Iidlimit, the magnitude of the charging voltage (charging power maximum value) can be changed. it can. Since the relationship between the charging voltage and the recovery charging time is as shown in FIG. 3, the recovery charging time can be shortened as compared with the conventional case by increasing the charging voltage. A specific example is shown in FIG.

  The example of FIG. 4 assumes a case where four 12V7Ah batteries widely distributed in the market are used in series as the batteries used. The recommended charging voltage (steady) suggested by the battery manufacturer for a 12V battery is about 13.65V, but in the case of cycle use that temporarily increases the charging voltage to shorten the charging time, charging is performed. By controlling the current to 0.25 CA or less, it can be increased to about 15.0V. FIG. 4 shows the initial charging power that can be consumed as the battery charging power, the charging voltage in that case, and the recovery charging time corresponding to the charging voltage (100% charging time, 110% charging) for each of the six types of output capacities described above. Time and 120% charging time).

  Thus, the uninterruptible power supply 1-1 according to the present embodiment is set by taking into account the input current limit value, the battery charge voltage limit value, and the battery charge current limit value at that time as the battery charge voltage value. The charging voltage value corresponding to the charging voltage setting value Vcdset to be set can be automatically set, and the recovery charging time corresponding to the output capacity can be shortened as shown in the table of FIG. Thereby, the operability of the uninterruptible power supply can be improved.

  Next, the uninterruptible power supply 1-2 according to the second embodiment of the present invention will be described in detail with reference to FIG. Hereinafter, differences from the uninterruptible power supply 1-1 according to the first embodiment will be mainly described.

  The uninterruptible power supply 1-2 of FIG. 5 is different from the uninterruptible power supply 1-1 of FIG. 1 in that the charger control circuit 10 and the charging circuit 20 are replaced with a two-quadrant chopper control circuit 11 and a two-quadrant chopper circuit 21, respectively. What is changed is that the input / output terminal of the two-quadrant chopper circuit 21 is connected to the DC terminals G and H, the booster circuit 50 is omitted, and the two-quadrant chopper control circuit 11 is connected to the DC terminals G and H. Is also connected.

  More specifically, the two-quadrant chopper circuit 21 of the uninterruptible power supply 1-2 in FIG. 5 is connected to the DC terminals G and H, which are connection points between the high power factor rectifier circuit 30 and the inverter circuit 40, and the battery 6 Are connected to battery voltage terminals I and J to which are connected. The two-quadrant chopper control circuit 11 is connected to AC input terminals E and F, DC terminals G and H, and a battery voltage terminal I, and is also connected to current detectors 4 and 5.

  Hereinafter, the operation of the uninterruptible power supply 1-2 of FIG. 5 will be described.

  AC power input from the input terminals A and B is input to the high power factor rectifier circuit 30 via the filter circuit 2, the overcurrent protector 3, the current detector 4, and the AC input terminals E and F. The high power factor rectifier circuit 30 boosts the input AC power supply voltage and supplies DC power whose voltage is stabilized to the DC terminals G and H. The DC power output from the high power factor rectifier circuit 30 to the DC terminals G and H is input to the inverter circuit 40, the two-quadrant chopper circuit 21, and the two-quadrant chopper control circuit 11.

  The two-quadrant chopper circuit 21 includes, for example, MOSFETs 2101 and 2102, a reactor 2103, and a capacitor 2104 as illustrated. The MOSFETs 2101 and 2102 are controlled to be opened and closed by gate drive signals T2 and T3 supplied from the two-quadrant chopper control circuit 11, respectively.

  When receiving AC input, the two-quadrant chopper circuit 21 performs step-down control (stabilization control) of the DC voltage from the high power factor rectifier circuit 30 and operates as a charger for the battery 6. In this case, the gate drive signal T3 output from the two-quadrant chopper control circuit 11 is always at the L level, so that the MOSFET 2102 is always in the OFF state. On the other hand, the gate drive signal T2 output from the two-quadrant chopper control circuit 11 alternately repeats the H level and the L level at this time.

  When the gate drive signal T2 is at the H level, the MOSFET 2101 is turned on, and the current flows through the path of the DC terminal G → MOSFET 2101 → reactor 2103 → current detector 5 → battery voltage terminal I → battery 6 → battery voltage terminal J → DC terminal H. As a result, energy is accumulated in the reactor 2103. Further, when the gate drive signal T2 output from the two-quadrant chopper control circuit 11 is at L level, the MOSFET 2101 is turned OFF, and the energy accumulated in the reactor 2103 is the reactor 2103 → current detector 5 → battery voltage terminal I → battery. Current is circulated through a path of 6 → battery voltage terminal J → body diode (not shown) of MOSFET 2102 → reactor 2103 and supplied to the battery 6.

  When the H level period of the gate drive signal T2 is made large and the L level period is made small, the output current and the output voltage supplied from the two-quadrant chopper circuit 21 to the battery 6 increase. Conversely, when the H level period of the gate drive signal T2 is reduced and the L level period is increased, the output current and output voltage supplied from the two-quadrant chopper circuit 21 to the battery 6 decrease.

  As described above, when AC input is received, the 2-quadrant chopper control circuit 11 supplies the battery 6 with the 2-quadrant chopper circuit 21 by appropriately controlling the time ratio between the H level and L level of the gate drive signal T2 of the MOSFET 2101. Output current and voltage, that is, battery charging current and voltage can be controlled to desired values.

  When a power failure occurs in the above configuration, the predetermined DC power output from the high power factor rectifier circuit 30 is cut off, but the two-quadrant chopper circuit 21 functions as a booster (stability control) for the battery voltage from the battery 6. The predetermined DC power is supplied to the inverter circuit 40 for a predetermined time. As a result, the inverter circuit 40 supplies AC power of a predetermined AC output voltage Vo to the load device via the output terminals C and D for a predetermined time.

  When a power failure occurs, the gate drive signal T2 output from the two-quadrant chopper control circuit 11 is always at L level, so that the MOSFET 2101 is always in the OFF state. On the other hand, the gate drive signal T3 output from the two-quadrant chopper control circuit 11 alternately repeats H level and L level.

  When the gate drive signal T3 output from the two-quadrant chopper control circuit 11 is at the H level, the MOSFET 2102 is turned on, and the battery 6 → the battery voltage terminal I → the current detector 5 → the reactor 2103 → the MOSFET 2102 → the battery voltage terminal J → the battery 6 The current flows through the path, and energy is accumulated in the reactor 2103. Further, when the gate drive signal T3 output from the two-quadrant chopper control circuit 11 is at L level, the MOSFET 2102 is turned OFF, and the energy accumulated in the reactor 2103 is the reactor 2103 → the body diode (not shown) of the MOSFET 2101 → DC. Load terminal (not shown) connected to terminal G → inverter circuit 40 and output terminals C and D → DC terminal H → battery voltage terminal J → battery 6 → battery voltage terminal I → current detector 5 → reactor 2103 path The current circulates and supplies uninterruptible power to the load equipment.

  When the H level period of the gate drive signal T3 is increased and the L level period is decreased, the output current and output voltage supplied from the two-quadrant chopper circuit 21 to the inverter circuit 40 and the load device increase. On the other hand, when the period when the gate drive signal T3 is at the H level is reduced and the period at the L level is increased, the output current and output voltage supplied from the two-quadrant chopper circuit 21 to the inverter circuit 40 and the load device are decreased. .

  As described above, by appropriately controlling the time ratio between the H level and the L level of the gate drive signal T3 of the MOSFET 2102 at the time of a power failure, the two-quadrant chopper control circuit 11 changes the inverter circuit 40 and the load from the two-quadrant chopper circuit 21. The output current and voltage supplied to the device can be controlled to desired values.

  Since the two-quadrant chopper control circuit 11 controls the two-quadrant chopper circuit 21 as described above, error amplifiers 1001 and 1006, resistors 1002 and 1007, a reference voltage source 1005, an input voltage detection circuit 1009, and an A / D converter 1010 , A CPU 1011, a D / A converter 1012, and a two-quadrant chopper voltage control circuit 1101.

  In the two-quadrant chopper control circuit 11, the input voltage detection circuit 1009 generates the input voltage information Vi based on the voltage (input voltage) between the AC input terminals E and F. The A / D converter 1010 receives the input voltage information Vi output from the input voltage detection circuit 1009, the input current information Ii output from the current detector 4, and the charging current information Ic output from the current detector 5, respectively. A / D converted and supplied to the CPU 1011. The CPU 1011 operates in the same manner as in the first embodiment (see FIG. 2), and the elapsed time H from power failure recovery calculated from the input voltage information Vid input, and the input current information Iid input The charging voltage setting value Vcdset is generated based on the charging current information Icd and output to the D / A converter 1012. The D / A converter 1012 converts the charging voltage setting value Vcdset, which is the processing result of the CPU 1011, and outputs it as a voltage value Vcset corresponding to the target charging voltage value to the inverting input terminal of the error amplifier 1006.

  The battery charging voltage information Vch from the battery voltage terminal I is input to the non-inverting input terminal of the error amplifier 1006. The error amplifier 1006 then calculates βv (error) of the difference (Vch−Vcset) between the battery charge voltage information Vch and the voltage value Vcset corresponding to the target charge voltage value input from the D / A converter 1012 to the inverting input terminal. An error amplification voltage Ev corresponding to a multiplication factor of the amplifier 1006 is generated. The error amplification voltage Ev output from the error amplifier 1006 is supplied to the other end of the resistor 1002 whose one end is connected to the output terminal of the error amplifier 1001 via the resistor 1007.

  On the other hand, the charging current information Ic (Ic is a voltage value) from the current detector 5 is input to the non-inverting input terminal of the error amplifier 1001, and the reference voltage Vref for setting the battery charging current is input to the inverting input terminal. 1005 is input. The error amplifier 1001 outputs an error amplification voltage Ei corresponding to βi (amplification factor of the error amplifier 1001) times the difference (Ic−Vref) between the charging current information Ic and the reference voltage Vref.

  The error amplification voltages Ei and Ev of the error amplifiers 1001 and 1006 added through the resistors 1002 and 1007 are input to the two-quadrant chopper voltage control circuit 1101 as a control signal E.

  The two-quadrant chopper voltage control circuit 1101 is supplied with potentials Vg and Vh from the DC terminals G and H in addition to the control signal E supplied from the error amplifiers 1001 and 1006 via the resistors 1002 and 1007. . The two-quadrant chopper voltage control circuit 1101 generates gate drive signals T2 and T3 to be given to the two-quadrant chopper circuit 21 by a known method based on these voltages E, Vg, and Vh.

  That is, the two-quadrant chopper voltage control circuit 1101 always keeps the gate drive signal T3 at L level and receives the voltage between the battery voltage terminals I and J, that is, the battery charging voltage for the battery 6 when receiving AC input (power supply voltage). , The time ratio between the H level and the L level of the gate drive signal T2 is controlled so as to stabilize the control. At this time, the two-quadrant chopper voltage control circuit 1101 determines the charging current information based on the control signal E which is the addition result of the error amplification voltages Ei and Ev of the error amplifiers 1001 and 1006 added through the resistors 1002 and 1007. The time ratio between the H level and the L level of the gate drive signal T2 is set so that the voltage indicated by the battery charging voltage information Vch matches the voltage indicated by the charging voltage setting value Vcdset within a range where the current value indicated by Ic does not exceed a predetermined value. Control. In this way, the two-quadrant chopper voltage control circuit 1101 can control the output current and voltage of the two-quadrant chopper circuit 21, that is, the battery charging current and voltage to desired values when receiving AC input.

  On the other hand, when a power failure occurs, the two-quadrant chopper circuit 21 functions as a booster with respect to the battery voltage from the battery 6 and always keeps the gate drive signal T2 at the L level and the voltage between the DC terminals G and H, that is, an inverter. The time ratio between the H level and the L level of the gate drive signal T3 is controlled so as to stabilize the input voltage of the circuit 40.

  As described above, in the uninterruptible power supply 1-2 according to the present embodiment, as in the uninterruptible power supply 1-1 according to the first embodiment, the input current limit is set as the battery charge voltage value. It is possible to automatically set the charging voltage value corresponding to the charging voltage setting value Vcdset that is set taking into account the value, the charging voltage limiting value of the battery, and the battery charging current limiting value at that time, and recovery corresponding to the output capacity The charging time can be shortened as shown in the table of FIG. Thereby, the operability of the uninterruptible power supply can be improved.

  Next, the uninterruptible power supply 1-3 according to the third embodiment of the present invention will be described in detail with reference to FIG. Hereinafter, differences from the uninterruptible power supply 1-1 according to the first embodiment will be mainly described.

  The uninterruptible power supply 1-3 of FIG. 6 differs from the uninterruptible power supply 1-1 of FIG. 1 in that the charger control circuit 10 and the charging circuit 20 of FIG. 1 are the bidirectional converter control circuit 12 and the bidirectional converter, respectively. The circuit 22 is changed, the input / output terminal of the bidirectional converter circuit 22 is connected to the AC input terminals E and F and the output terminals C and D, and the high power factor rectifier circuit of FIG. 30, the inverter circuit 40 and the booster circuit 50 are omitted.

  More specifically, in the uninterruptible power supply 1-3 of FIG. 6, the input terminals A and B are output terminals C through the filter circuit 2, the overcurrent protector 3, the current detector 4, and the AC input terminals E and F. And D. The bidirectional converter circuit 22 is connected to the AC input terminals E and F, and is connected to the battery voltage terminals I and J via the current detector 5. The bidirectional converter control circuit 12 is connected to the AC input terminals E and F and the battery voltage terminal I, and is also connected to the current detectors 4 and 5.

  Hereinafter, the operation of the uninterruptible power supply 1-3 of FIG. 6 will be described.

  The AC power input to the input terminals A and B is a load device (not shown) via the filter circuit 2, the overcurrent protector 3, the current detector 4, the AC input terminals E and F, and the output terminals C and D. ). AC power is input to the bidirectional converter circuit 22 and the bidirectional converter control circuit 12 from the AC input terminals E and F.

  The bidirectional converter circuit 22 includes, for example, a transformer 2201, capacitors 2202 and 2208, a reactor 2203, and MOSFETs 2204 to 2207 as illustrated. This bidirectional converter circuit 22 is controlled to open and close MOSFETs 2204 to 2207 by gate drive signals T4 to T7 given from the bidirectional converter control circuit 12, and operates as a charger for the battery 6 when receiving AC input (power supply voltage). .

  More specifically, the gate output from the bidirectional converter control circuit 12 during a period when the potential of the AC input terminal E is higher than the potential of the AC input terminal F (hereinafter referred to as “positive half cycle”) when receiving AC input. The drive signals T4, T6, and T7 are always at the L level, and the MOSFETs 2204, 2206, and 2207 are always in the OFF state. At this time, if the gate drive signal T5 output from the bidirectional converter control circuit 12 is at the H level, the MOSFET 2205 is turned on, and the current flowing through the path of the AC input terminal E → the transformer 2201 → the AC input terminal F The current induced on the secondary side flows through the path of the transformer 2201 → the reactor 2203 → the MOSFET 2205 → the body diode (not shown) of the MOSFET 2207 → the transformer 2201, and energy is accumulated in the reactor 2203.

  On the other hand, during the positive half cycle period, when the gate drive signal T5 output from the bidirectional converter control circuit 12 is at the L level, the MOSFET 2205 is turned OFF, and the energy stored in the reactor 2203 is the reactor 2203 → the body diode of the MOSFET 2204. (Not shown) → Current detector 5 → Battery voltage terminal I → Battery 6 → Battery voltage terminal J → Body diode of MOSFET 2207 (not shown) → Transformer 2201 → Reactor 2203 Supplied.

  In the positive half cycle period, when the H level period of the gate drive signal T5 output from the bidirectional converter control circuit 12 is lengthened (that is, when the ON period of the MOSFET 2205 is increased), the energy stored in the reactor 2203 is large. Thus, the charging current / voltage to the battery 6 increases. Conversely, when the L level period of the gate drive signal T5 output from the bidirectional converter control circuit 12 is lengthened (that is, when the OFF period of the MOSFET 2205 is increased), the energy stored in the reactor 2203 is reduced and the battery 6 is charged. The current / voltage decreases.

  Next, an operation during a period when AC input is received and the potential of the AC input terminal F is higher than the potential of the AC input terminal E (hereinafter referred to as “negative half cycle”) will be described.

  During the negative half cycle, the gate drive signals T4, T5, and T6 output from the bidirectional converter control circuit 12 are always at the L level, and the MOSFETs 2204, 2205, and 2206 are always in the OFF state. At this time, if the gate drive signal T7 output from the bidirectional converter control circuit 12 is at the H level, the MOSFET 2207 is turned on, and the secondary of the transformer 2201 is driven by the current flowing from the AC input terminal F → the transformer 2201 → the AC input terminal E. The current induced on the side flows through the path of the transformer 2201 → the MOSFET 2207 → the body diode (not shown) of the MOSFET 2205 → the reactor 2203 → the transformer 2201, and energy is accumulated in the reactor 2203.

  On the other hand, during the negative half cycle, when the gate drive signal T7 output from the bidirectional converter control circuit 12 is at L level, the MOSFET 2207 is turned OFF, and the energy stored in the reactor 2203 is changed from the reactor 2203 to the transformer 2201 → Battery 6 is obtained by circulating current through the path of body diode (not shown) of MOSFET 2206 → current detector 5 → battery voltage terminal I → battery 6 → battery voltage terminal J → body diode of MOSFET 2205 (not shown) → reactor 2203. To be supplied.

  In the negative half cycle period, if the H level period of the gate drive signal T7 output from the bidirectional converter control circuit 12 is lengthened (that is, the ON period of the MOSFET 2207 is long), the energy stored in the reactor 2203 becomes large, and the battery The charging current / voltage to 6 increases. On the contrary, during the negative half cycle period, if the L level period of the gate drive signal T7 output from the bidirectional converter control circuit 12 is lengthened (the OFF period of the MOSFET 2207 is long), the energy stored in the reactor 2203 is small. Thus, the charging current / voltage to the battery 6 decreases.

  As described above, uninterruptible power supply 1-3 according to the present embodiment appropriately controls the time ratio between the H level and L level of gate drive signal T5 of MOSFET 2205 during the positive half cycle during AC input power reception. By doing so, the bidirectional converter control circuit 12 controls the bidirectional converter circuit 12 by appropriately controlling the time ratio between the H level and the L level of the gate drive signal T7 of the MOSFET 2207 during the negative half cycle when receiving AC input. 22 output currents and voltages, that is, battery charging current and voltage can be controlled to desired values (stabilization control).

  Next, the operation of the uninterruptible power supply 1-3 when a power failure occurs, that is, when the AC power supply voltage is cut off, will be described.

  When a power failure occurs, the AC power input to the input terminals A and B and supplied to the bidirectional converter circuit 22 via the AC input terminals E and F is interrupted. At this time, the bidirectional converter circuit 22 operates as an inverter with respect to the battery voltage from the battery 6, and the AC power of the predetermined AC output voltage Vo is supplied to the load device (D) via the output terminals C and D for a predetermined time. (Not shown).

  The operation of the bidirectional converter circuit 22 as an inverter will be described below according to the potential of the AC input terminals E and F.

  First, a period in which the bidirectional converter circuit 22 generates an output voltage in which the potential of the AC input terminal F is higher than the potential of the AC input terminal E (hereinafter referred to as “positive half cycle”) will be described.

  When the MOSFET 2204 and the MOSFET 2207 are simultaneously turned on by the gate drive signals T4 and T7 output from the bidirectional converter control circuit 12, the battery voltage is applied to the secondary coil side of the transformer 2201 in the positive direction. Next, when the MOSFET 2204 and the MOSFET 2206 are simultaneously turned on by the gate drive signals T4 and T6 output from the bidirectional converter control circuit 12, the secondary coil voltage of the transformer 2201 becomes zero. That is, with the MOSFET 2204 turned on, the MOSFET 2206 and the MOSFET 2207 are alternately turned on / off, whereby a PWM wave that alternately repeats the battery voltage and the zero voltage is applied to the secondary coil side of the transformer 2201. . This PWM wave is smoothed by a reactor 2203 and a capacitor 2202 that constitute an AC filter, and a sine wave having a voltage corresponding to the turn ratio of the primary coil and the secondary coil is induced in the primary coil of the transformer 2201. Is applied between the AC input terminals E and F and output from the output terminals C and D.

  During the positive half-cycle period, if the period in which the MOSFET 2204 and the MOSFET 2207 are simultaneously turned on is increased and the period in which the MOSFET 2204 and the MOSFET 2206 are simultaneously turned on is reduced, the secondary side of the transformer 2201 has a longer period during which the battery voltage is applied and becomes zero. The period during which the voltage is applied becomes small. As a result, the average voltage of the sine wave induced on the primary side of the transformer 2201 increases, and the voltage generated between the AC input terminals E and F increases.

  Conversely, if the period in which the MOSFET 2204 and the MOSFET 2207 are simultaneously turned on is reduced and the period in which the MOSFET 2204 and the MOSFET 2206 are simultaneously turned on is increased, the average voltage of the sine wave induced on the primary side of the transformer 2201 is reduced. The voltage generated between F decreases.

  As described above, by appropriately controlling the time ratio between the period in which the MOSFET 2204 and the MOSFET 2207 are simultaneously turned on and the period in which the MOSFET 2204 and the MOSFET 2206 are simultaneously turned on, a desired amplitude is generated between the AC input terminals E and F. A positive half cycle of a sine wave can be generated.

  Next, a period in which the bidirectional converter circuit 22 generates an output voltage in which the potential of the AC input terminal F is lower than the potential of the AC input terminal E (hereinafter referred to as “negative half cycle”) will be described.

  When the MOSFET 2205 and the MOSFET 2206 are simultaneously turned on by the gate drive signals T5 and T6 output from the bidirectional converter control circuit 12, the battery voltage is applied to the secondary coil side of the transformer 2201 in the negative direction. When the MOSFET 2205 and the MOSFET 2207 are simultaneously turned on by the gate drive signals T5 and T7 output from the bidirectional converter control circuit 12, the secondary coil voltage of the transformer 2201 becomes zero. In other words, by alternately turning on / off the MOSFET 2206 and the MOSFET 2207 with the MOSFET 2205 turned on, a PWM wave that alternately repeats the battery voltage and the zero voltage is applied to the secondary coil side of the transformer 2201. . This PWM wave is smoothed by a reactor 2203 and a capacitor 2202 that constitute an AC filter, and a sine wave having a voltage corresponding to the turn ratio of the primary coil and the secondary coil is induced in the primary coil of the transformer 2201. Is applied between the AC input terminals E and F and output from the output terminals C and D.

  In the negative half cycle period, if the period in which the MOSFET 2205 and the MOSFET 2206 are simultaneously turned on is increased and the period in which the MOSFET 2205 and the MOSFET 2207 are simultaneously turned on is reduced, the secondary side of the transformer 2201 has a period during which the battery voltage is applied in the negative direction. The period during which the zero voltage is applied becomes smaller and becomes smaller. As a result, the average voltage of the sine wave induced in the negative direction on the primary side of the transformer 2201 increases, and the voltage generated between the AC input terminals E and F increases in the negative direction.

  Conversely, during the negative half cycle period, if the period in which the MOSFET 2205 and the MOSFET 2206 are simultaneously turned on is reduced and the period in which the MOSFET 2205 and the MOSFET 2207 are simultaneously turned on is increased, the battery voltage is applied to the secondary side of the transformer 2201 in the negative direction. The period during which the zero voltage is applied becomes longer, and as a result, the negative average voltage of the sine wave decreases, and the negative voltage generated between the AC input terminals E and F decreases.

  In this way, by appropriately controlling the time ratio between the period in which the MOSFET 2205 and the MOSFET 2206 are simultaneously turned on and the period in which the MOSFET 2205 and the MOSFET 2207 are simultaneously turned on, the AC input terminals E and F have a desired amplitude. A negative half cycle of a sine wave can be generated.

  As described above, in the uninterruptible power supply 1-3 according to the present embodiment, a desired amplitude is obtained by controlling the gate drive signals T4, T5, T6 and T7 output from the bidirectional converter control circuit 12. A sinusoidal output voltage can be obtained.

  Next, the operation of the bidirectional converter control circuit 12 will be described.

  The input voltage detection circuit 1009, the A / D converter 1010, the CPU 1011, the D / A converter 1012, the reference voltage source 1005, the error amplifiers 1001 and 1006, and the resistors 1002 and 1007 of the bidirectional converter control circuit 12 are the second implementation. The input voltage detection circuit 1009, the A / D converter 1010, the CPU 1011, the D / A converter 1012, the reference voltage source 1005, the error amplifiers 1001 and 1006, and the resistors 1002 and 1007 of the uninterruptible power supply 1-2 according to the embodiment It operates in the same way. That is, the input voltage detection circuit 1009 generates the input voltage information Vi based on the voltage (input voltage) between the AC input terminals E and F. The A / D converter 1010 receives the input voltage information Vi output from the input voltage detection circuit 1009, the input current information Ii output from the current detector 4, and the charging current information Ic output from the current detector 5, respectively. A / D converted and supplied to the CPU 1011. The CPU 1011 operates in the same manner as in the first embodiment (see FIG. 2), and the elapsed time H from power failure recovery calculated from the input voltage information Vid input, and the input current information Iid input The charging voltage setting value Vcdset is generated based on the charging current information Icd and output to the D / A converter 1012. The D / A converter 1012 converts the charging voltage setting value Vcdset, which is the processing result of the CPU 1011, and outputs it as a voltage value Vcset corresponding to the target charging voltage value to the inverting input terminal of the error amplifier 1006.

  The battery charging voltage information Vch from the battery voltage terminal I is input to the non-inverting input terminal of the error amplifier 1006. The error amplifier 1006 then calculates βv (error) of the difference (Vch−Vcset) between the battery charge voltage information Vch and the voltage value Vcset corresponding to the target charge voltage value input from the D / A converter 1012 to the inverting input terminal. An error amplification voltage Ev corresponding to a multiplication factor of the amplifier 1006 is generated. The error amplification voltage Ev output from the error amplifier 1006 is supplied to the other end of the resistor 1002 whose one end is connected to the output terminal of the error amplifier 1001 via the resistor 1007.

  On the other hand, the charging current information Ic (Ic is a voltage value) from the current detector 5 is input to the non-inverting input terminal of the error amplifier 1001, and the reference voltage Vref for setting the battery charging current is input to the inverting input terminal. 1005 is input. The error amplifier 1001 outputs an error amplification voltage Ei corresponding to βi (amplification factor of the error amplifier 1001) times the difference (Ic−Vref) between the charging current information Ic and the reference voltage Vref.

  The error amplification voltages Ei and Ev of the error amplifiers 1001 and 1006 added through the resistors 1002 and 1007 are input to the bidirectional converter voltage control circuit 1201 as a control signal E.

  In addition to the control signal E, the bidirectional converter voltage control circuit 1201 is based on the potentials Ve and Vf from the AC input terminals E and F, and supplies gate drive signals T4 and T5 to the bidirectional converter circuit 22 by a known method. , T6, T7 are generated.

  As described above, uninterruptible power supply 1-3 according to the present embodiment appropriately controls the time ratio between the H level and L level of gate drive signal T5 of MOSFET 2205 during the positive half cycle during AC input power reception. In the negative half cycle when receiving AC input, the bidirectional converter control circuit 12 controls the bidirectional converter circuit 22 by appropriately controlling the time ratio between the H level and L level of the gate drive signal T7 of the MOSFET 2207. The output current and voltage, that is, the battery charging current and voltage can be controlled to desired values. Note that the bidirectional converter voltage control circuit 1201 is based on the control signal E, which is the addition result of the error amplification voltages Ei and Ev of the error amplifiers 1001 and 1006 added via the resistors 1002 and 1007, and the charging current information Ic. The time ratio between the H level and the L level of the gate drive signal T2 so that the voltage value indicated by the battery charging voltage information Vch matches the voltage value indicated by the charging voltage setting value Vcdset within a range in which the current value indicated by is not larger than a predetermined value. There are restrictions on

  Further, the uninterruptible power supply 1-3 according to the present embodiment causes the bidirectional converter circuit 22 to act as an inverter for the battery voltage from the battery 6 when a power failure occurs, and the MOSFET 2205 and the MOSFET 2206 are simultaneously turned on. A sine wave output voltage having a desired amplitude can be obtained by appropriately controlling the time ratio of the time during which the MOSFET 2205 and the MOSFET 2207 are simultaneously turned on.

  As described above, in the uninterruptible power supply 1-3 according to this embodiment, the battery charge voltage value is similar to the uninterruptible power supply 1-1 and 1-2 according to the first and second embodiments. As a result, it is possible to automatically set a charging voltage value corresponding to a charging voltage setting value Vcdset that is set in consideration of an input current limiting value, a battery charging voltage limiting value, and a battery charging current limiting value at that time. The recovery charge time corresponding to the capacity can be shortened as shown in the table of FIG. Thereby, the operability of the uninterruptible power supply can be improved.

  Next, another processing example that can be employed in the CPU 1011 of the uninterruptible power supply according to the first, second, and third embodiments of the present invention will be described in detail with reference to the flowchart of FIG. In FIG. 7, the same steps as those in the flowchart of FIG.

  Referring to FIG. 7, the CPU 1011 first accepts manual setting of Iidlimit in step S7-1. That is, an input of Iidlimit from an input setting unit (not shown) is accepted. Here, a plurality of Iidlimit candidates I1, I2,... Are stored in the memory in advance, and are designated.

  When the Iidlimit candidate is designated in step S7-1, the CPU 1011 sets the designated Iidlimit candidate to Iidlimit in step S7-2.

  Thereafter, the same processing (steps S2-1 to S2-7) as in FIG. 2 is repeated to control Vcdset.

  According to the present embodiment, it is possible to use any battery as the battery 6 by manually setting the Iidlimit.

  In the above-described embodiment, the case where the Iidlimit candidates stored in the memory in advance is specified has been described. However, the Iidlimit may be set directly.

  Next, still another processing example that can be employed in the CPU 1011 of the uninterruptible power supply according to the first, second, and third embodiments of the present invention will be described in detail with reference to the flowchart of FIG. In FIG. 8 as well, as in FIG. 7, the same steps as those in the flowchart of FIG.

  Referring to FIG. 8, first, in step S 2-1, the CPU 1011 includes an elapsed time H from power failure recovery based on input voltage information Vid digitized via the input voltage detection circuit 1009 and the A / D converter 1010, A predetermined elapsed time set value Hset set in advance is compared. If the CPU 1011 determines that H ≦ Hset is not satisfied as a result of step S 2-1, the CPU 1011 proceeds to step 2-7 and holds the charging voltage setting value Vcdset at Vcd 0. If the CPU 1011 determines that H ≦ Hset in step S 2-1, the CPU 1011 proceeds to step S 2-2 and sets the input current information Iid and the input current limit value Iidlimit quantified via the A / D converter 1010. Compare.

  If the CPU 1011 determines that Iid <Iidlimit is not satisfied as a result of the comparison in step S2-2, the CPU 1011 proceeds to step S2-3 and decreases the charging voltage setting value Vcdset by, for example, a predetermined amount.

  On the other hand, if the CPU 1011 determines that Iid <Iidlimit as a result of the comparison in step S2-2, the CPU 1011 proceeds to step S8-1 and determines the type of the battery. This determination may be performed based on, for example, battery information stored in the memory at the time of initial setting, or may be performed based on a detection result by providing a detection unit that detects a battery type.

  Next, in step S8-2, the CPU 1011 sets Vcdmax according to the type of battery. This setting is performed, for example, by storing in advance a plurality of Vcdmax candidates corresponding to the battery type in a memory (not shown) and reading the Vcdmax candidates according to the determined battery type.

  The remaining steps are as described with reference to FIG.

  According to the present embodiment, since Vcdmax is set according to the type of battery, it is possible to easily use different types of batteries 6.

  Next, still another processing example that can be employed in the CPU 1011 of the uninterruptible power supply according to the first, second, and third embodiments of the present invention will be described in detail with reference to the flowchart of FIG. 9 is different from the flowchart in FIG. 8 in that step S9-1 is provided instead of step S8-1. Step S8-2 and step S9-2 are not substantially different.

  The uninterruptible power supply devices 1-1, 1-2, and 1-3 according to the present embodiment include a temperature detector (not shown) for detecting the ambient temperature in addition to the configurations shown in FIGS. )). It is assumed that the detection output from the temperature detector is given to the CPU 1011 (via the A / D converter 1010).

  Referring to FIG. 9, the CPU 1011 determines in which step the detected temperature from the temperature detector is included in a plurality of preset temperature ranges in step S9-1. Note that Vcdmax to be set is assigned to each of the plurality of temperature ranges, and the relationship is stored in a memory (not shown).

  Next, in step S9-2, the CPU 1011 reads and sets Vcdmax assigned to the range including the detected temperature from the memory.

  The remaining steps are the same as in FIG.

  According to the present embodiment, Vcdmax is automatically set according to the ambient temperature of the uninterruptible power supply, so that when the constant current and constant voltage charging is performed, the battery is overcharged as the ambient temperature increases. The tendency can be prevented.

  As mentioned above, although this invention was demonstrated according to some embodiment, this invention is not limited to the said embodiment. For example, regarding the configuration and control method of the uninterruptible power supply, the present invention can be applied to the case where the configuration, control method, processing flowchart, etc. of other uninterruptible power supply devices including the DC output uninterruptible power supply are used. In the above embodiment, the case where the input current is detected to control the maximum charging power has been described. However, the output current supplied from the output terminals C and D to the load may be detected. In this case, if the detected output current value is given to the CPU and the CPU converts the input current value based on the relationship with the load, the same control as in the above-described embodiment can be realized.

It is a circuit diagram which shows the structure of the uninterruptible power supply which concerns on the 1st Embodiment of this invention. It is a flowchart for demonstrating operation | movement of CPU contained in the uninterruptible power supply of FIG. It is a graph which shows the charge characteristic of a battery, Comprising: It is a graph which shows the relationship between charging voltage (V) and recovery | restoration charge time (hour). It is a table | surface which shows the relationship between the whole electric power, load electric power, the charge initial power of a battery, a charge voltage, the charge initial current, and charge time. It is a circuit diagram which shows the structure of the uninterruptible power supply which concerns on the 2nd Embodiment of this invention. It is a circuit diagram which shows the structure of the uninterruptible power supply which concerns on the 3rd Embodiment of this invention. It is a flowchart which shows the other process which can be employ | adopted in CPU each included in the uninterruptible power supply of FIG.1, FIG5 and FIG.6. It is a flowchart which shows the further another process employ | adoptable in CPU each included in the uninterruptible power supply of FIG.1, FIG5 and FIG.6. It is a flowchart which shows another process which can be employ | adopted in CPU each included in the uninterruptible power supply of FIG. It is a circuit diagram which shows one structural example of the conventional uninterruptible power supply.

Explanation of symbols

1-1, 1-2, 1-3 Uninterruptible power supply 2 Filter circuit 3 Overcurrent protector 4, 5 Current detector 6 Battery 10 Charger control circuit 11 2 Quadrant chopper control circuit 12 Bidirectional converter control circuit 20 Charging Circuit 21 2-quadrant chopper circuit 22 Bidirectional converter circuit 30 High power factor rectifier circuit 40 Inverter circuit 50 Booster circuit A, B Input terminal C, D Output terminal E, F AC input terminal G, H DC terminal I, J Battery voltage terminal 1001, 1006 Error amplifier (E-AMP)
1002, 1007 Resistor 1003 Comparator (CMP)
1004 Drive circuit 1005, 6001 Reference voltage source 1008 Sawtooth wave generator 1009 Input voltage detection circuit 1010 A / D converter 1011 CPU
1012 D / A converter 1101 Two-quadrant chopper voltage control circuit 1201 Bidirectional converter voltage control circuit 2001-2004, 2007, 2010, 2011 Diode 2005, 2012, 2103, 2203 Reactor 2006, 2013, 2104, 2202, 2208 Capacitor 2008, 2201 Transformer 2009, 2101, 1022, 2204-2207 MOSFET

Claims (11)

An uninterruptible power supply that charges a battery while supplying power supplied to the input terminal from the outside to the output terminal, and supplies power from the battery to the output terminal when power supply to the input terminal is interrupted In
An uninterruptible power supply comprising battery charge maximum power value control means for controlling a maximum charge power value of the battery until a predetermined time elapses after detection of resumption of power supply to the input terminal Power supply. In the uninterruptible power supply device according to claim 1,
The uninterruptible power supply characterized in that the battery charge maximum power value control means keeps the input current flowing through the input terminal below a predetermined input current limit value and makes the charge voltage of the battery higher than a recommended charge voltage. apparatus. In the uninterruptible power supply according to claim 2,
The battery charging maximum power value control means increases the charging voltage stepwise until an input current flowing through the input terminal exceeds a predetermined value or until the charging voltage exceeds a preset charging voltage setting maximum value. An uninterruptible power supply. In the uninterruptible power supply device according to claim 3,
When the input current flowing through the input terminal exceeds the predetermined value, or when the charging voltage exceeds a preset charging voltage setting maximum value, the battery charging maximum power value control means An uninterruptible power supply characterized by lowering the level by one step. In the uninterruptible power supply according to any one of claims 2 to 4,
The uninterruptible power supply, wherein the battery charge maximum power value limiting means includes an input current detector for detecting an input current flowing through the input terminal. In the uninterruptible power supply according to any one of claims 2 to 4,
The battery charge maximum power value limiting means includes an output current detector that detects an output current flowing through the output terminal, and a calculation unit that calculates the input current based on a detection result of the output current detector. An uninterruptible power supply. In the uninterruptible power supply according to any one of claims 1 to 6,
The battery charging maximum power control means includes an input voltage detection circuit that detects input voltage supplied to the input terminal and generates input voltage information, and supplies power to the input terminal based on the input voltage information. An uninterruptible power supply characterized by detecting disconnection and resumption. In the uninterruptible power supply according to any one of claims 1 to 7,
The battery charging maximum power control means includes a charging current detector for detecting the charging current of the battery, and controls the charging power maximum value of the battery so that the charging current becomes a predetermined value or less. An uninterruptible power supply. In the uninterruptible power supply according to any one of claims 2 to 6,
An uninterruptible power supply comprising an input setting unit for setting the input current limit value. In the uninterruptible power supply according to claim 3 or 4,
In order to change the charging voltage setting maximum value according to the type of the battery, an input setting unit for instructing and inputting the type of the battery or a battery type detecting unit for detecting the type of the battery is provided. An uninterruptible power supply. In the uninterruptible power supply according to claim 3 or 4,
In order to change the charging voltage setting maximum value according to the operating environment temperature of the battery, a temperature detector for detecting the operating environment temperature of the battery, and charging voltage setting maximum value candidates respectively corresponding to a plurality of temperature ranges An uninterruptible power supply comprising a memory for storage.

Images