JP2004104772A - Data receiver - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a data receiver having a simple constitution, for reducing a time for abstracting a plurality of partial band signals, and easily made to a large-scale-integration without using a plurality of analog circuits each having characteristics similar to one another. <P>SOLUTION: The data receiver 1 is composed of a first sampling unit 100 for outputting a sampled in-phase signal I(nT) after sampling an in-phase signal (t) in every constant sampling period, a second sampling unit 101 for outputting a sampled orthogonal signal Q(nT) after sampling an orthogonal signal Q(t) in every constant sampling period, and a complex filter. The data receiver 1 comprises: a partial band abstracting unit 102 for outputting partial band signals IB<SB>r</SB>, QB<SB>r</SB>from frequency components included in the sampled in-phase signal I(nT) and the sampled orthogonal signal Q(nT); and first and second delay detection calculating units 103, 104 for each outputting a detected signal after performing a delay detection based on the partial band signals. <P>COPYRIGHT: (C)2004,JPO

Description

The present invention relates to a data receiving apparatus for demodulating a modulated signal, and more particularly, to a data receiving apparatus for obtaining a detection signal by digital signal processing from a phase-modulated modulated signal.

Conventionally, as a device for extracting and demodulating at least one partial band signal from a received modulated signal, a data transmitting / receiving device described in Patent Document 1 and a device described in Non-Patent Document 1 have been known. .

FIG. 25 is a diagram showing a configuration of a data receiving device described in Patent Document 1. As shown in FIG. In FIG. 25, the data receiving apparatus includes a frequency mixer 1301, a band-pass filter (denoted as BPF in the drawing) 1302, a local oscillator 1303, a reception state determination unit 1304, a delay unit 1305, a multiplier 1306, , A low-pass filter (denoted as LPF in the drawing) 1307, and a decoder 1308.

Local oscillator 1303 outputs a local oscillation signal whose frequency can be changed at intervals of an integral multiple of the symbol frequency of the data to be received. The frequency mixer 1301 converts the input spread spectrum signal r (t) into a frequency band having a difference from the local oscillation signal from the local oscillator 1303, and outputs the same. Here, it is assumed that the spread spectrum signal r (t) is a phase-modulated signal that can be demodulated by extracting at least one partial band from the frequency band of the spread spectrum signal r (t).

The band-pass filter 1302 extracts and outputs an intermediate signal b (t) which is a partial frequency component of the spread spectrum signal r (t) frequency-converted by the frequency mixer 1301.

FIG. 26 is a diagram showing a spectrum of a signal in a main part of the data receiving apparatus shown in FIG. FIG. 26A is a schematic diagram of the spectrum of the received spread spectrum signal r (t). There are three frequencies of the local oscillation signal output from the local oscillator 1303. The frequency of each local oscillation signal is an integral multiple of the symbol frequency of the data to be received. The center frequency of each local oscillation signal is the center frequency of any of the partial bands indicated by B1, B2, and B3.

FIG. 26B is a schematic diagram of the spectrum of the intermediate signal b (t). The intermediate signal b (t) is a signal of any one of the partial bands B1, B2, and B3 obtained as a result of r (t) being frequency-converted and band-limited.

(4) The reception state determination unit 1304 outputs a band switching signal according to the data reception state, and switches the frequency of the local oscillation signal output from the local oscillator 1303. Local oscillator 1303 switches the frequency of the output local oscillation signal based on the band switching signal output from reception state determination section 1304. As a result, one of the partial bands B1, B2, and B3 is selected, and the band-pass filter 1302 outputs the intermediate signal b (t) corresponding to the partial band.

The multiplier 1306 multiplies the intermediate signal b (t) by the intermediate signal b (t) obtained by delaying the intermediate signal b (t) by the symbol period Ts by the delay unit 1305, and converts the output signal to a low band. Input to the pass filter 1307. The low-pass filter 1307 performs low-pass filtering of the input signal and outputs a detection signal c (t). The decoder 1308 determines the polarity of the detection signal c (t) and outputs data dat (t).

FIG. 27 is a block diagram schematically showing a configuration of a receiver in the wireless modem described in Non-Patent Document 1. In FIG. 27, the receiver includes a demultiplexer 1501, a first frequency mixer 1502, a second frequency mixer 1503, a first local oscillator 1504, a second local oscillator 1505, and a first , A second band-pass filter 1507, a first gain controller (shown as AGC1 in the figure) 1508, a second gain controller (shown as AGC2 in the figure) 1509, It includes a first quadrature detector 1510, a second quadrature detector 1511, and a baseband signal processing unit 1512.

受 信 This receiver takes a spread spectrum signal as an input signal, extracts two partial bands at the same time, and outputs received data according to the reception situation. This receiver has two reception systems having the same configuration from the first frequency mixer 1502 to the baseband signal processing unit 1512, and from the second frequency mixer 1503 to the baseband signal processing unit 1512. Hereinafter, the operation of the receiver shown in FIG. 27 will be described.

The demultiplexer 1501 demultiplexes the received spread spectrum signal r (t) into two signals, and inputs them to the first frequency mixer 1502 and the second frequency mixer 1503, respectively. The first local oscillator 1504 and the second local oscillator 1505 each output a local oscillation signal having a center frequency of a band having a different band characteristic. The local oscillation signal output from local oscillator 1504 is input to frequency mixer 1502. A local oscillation signal output from local oscillator 1505 is input to frequency mixer 1503.

The frequency mixer 1502 converts the demultiplexed spread spectrum signal r (t) into a signal in a frequency band having a difference from the local oscillation signal output from the local oscillator 1504 and inputs the signal to the first bandpass filter 1506. I do. The first band-pass filter 1506 extracts a partial band signal from the input signal and inputs the partial band signal to the first gain controller 1508 as a partial band signal b1 (t). The first gain controller 1508 controls the amplitude of the partial band signal b1 (t), and inputs the resultant signal to the first quadrature detector 1510. First quadrature detector 1510 outputs I1 (t), which is the in-phase component, and Q1 (t), which is the quadrature component, of the complex baseband signal from first gain controller 1508.

The other receiving system below the second frequency mixer 1503 operates in the same manner, and the second quadrature detector 1511 outputs the I2 (I2 (in-phase component) of the complex baseband signal from the second gain controller 1509. t) and Q2 (t) which is an orthogonal component. The baseband signal processing unit 1512 performs delay detection processing on the complex baseband signals I1 (t) and Q1 (t), and I2 (t) and Q2 (t) as a set. The received data of the receiving system determined to have fewer errors is output in accordance with the receiving status of the receiving system. Note that, other than the above method, a method of selecting a system using a reception level and obtaining reception data may be used.

FIG. 28 is a diagram illustrating an example of a configuration of a differential detection device provided inside the baseband signal processing unit 1512. In the baseband signal processing unit 1512, one delay detection device is provided for each quadrature detector. FIG. 28 shows only one differential detection device as a representative. 28, the delay detection apparatus includes a first sampler 1101, a second sampler 1102, a delay detection operation unit 1103, a first post-detection filter 1104, and a second post-detection filter 1105. And

The first sampler 1101 samples (samples) the in-phase component i (t) (I1 (t) or I2 (t) in FIG. 27) of the complex baseband signal, and obtains the in-phase component of the sampled baseband signal. The data sequence I (nT) is output and input to the differential detection operation unit 1103. Here, n is an integer (n =... -1, 0, 1,...), And T is a sampling period. Similarly, the second sampler 1102 samples the orthogonal component q (t) (Q1 (t) or Q2 (t) in FIG. 27) of the complex baseband signal, and The column Q (nT) is output and input to the differential detection operation unit 1103.

FIG. 29 is a diagram showing the configuration of the differential detection calculation unit 1103. In FIG. 29, the delay detection operation unit 1103 includes a first selector 1201, a second selector 1202, a delay unit 1203, a sign inverter 1204, a first multiplier 1205, and a second multiplier 1206. And The first selector 1201 alternately selects the data strings I (nT) and Q (nT) of the sampled baseband signal for each sampling period T, and outputs the result as S1 (nT). The second selector 1202 alternates the sign-inverted signals -I (nT) and Q (nT) of the sampled baseband signal in-phase component data sequence I (nT) output from the sign inverter 1204 at every sampling period T And output as S2 (nT).

間 While the first selector 1201 selects I (nT), the second selector 1202 is set to select Q (nT). In addition, while the first selector 1201 selects Q (nT), the second selector 1202 is set to select −I (nT).

The delay unit 1203 outputs a signal obtained by delaying S1 (nT) by one symbol time length kT with S1 (nT) as an input signal. Here, k is the number of samples per symbol. As a result, the first multiplier 1205 calculates, as F1 (nT), I (nT) I {(nk) T}, which is the product of the sampled baseband signal in-phase component data sequence for each sample period T. Q (nT) Q {(nk) T}, which is the product of the sampled baseband signal orthogonal component data sequence, is output alternately. The second multiplier 1206 calculates, as F2 (nT), for each sample period T, the product of the sampled baseband signal in-phase component and the sampled baseband signal orthogonal component, I ｛(nk) T｝ Q ( nT) and -I (nT) Q {(nk) T} are output alternately.

The first post-detection filter 1104 low-pass filters the input signal F1 (nT), and outputs I (nT) I {(nk) T} and Q (nT) Q {(nk) T. And outputs a signal D1 (nT) equivalent to the signal obtained by adding｝. Similarly, the second post-detection filter 1105 low-pass filters the input signal F2 (nT), and outputs I ｛(nk) T｝ Q (nT) and -I (nT) Q ｛(n -K) Output a signal D2 (nT) equivalent to a signal obtained by adding T｝.

D1 (nT) and D2 (nT) are complex numbers of A (nT) = I (nT) + jQ (nT) where I (nT) and Q (nT) are in-phase components and quadrature components, respectively, where j is Imaginary unit) and the complex conjugate of A {(nk) T} delayed from A (nT) by one symbol time length kT correspond to the in-phase and quadrature components of the multiplication result, respectively. ing. Therefore, since the phase represented by D1 (nT) and D2 (nT) represents the difference between the phase of A (nT) and the phase of A {(nk) T}, the determination circuit (not shown) ), Etc., demodulation can be performed using D1 (nT) and D2 (nT).

As described above, the receiver shown in FIG. 27 obtains a plurality of different complex baseband signals from partial band signals having mutually different frequency band characteristics in order to obtain demodulated signals for the plurality of partial band signals, Performs a differential detection operation on each of the complex baseband signals, obtains a plurality of demodulated signals, and outputs received data according to the reception status.

In FIG. 27, two cases are shown as the sub-bands to be extracted. However, when two or more sub-bands are to be extracted, the baseband is extracted from the frequency mixer in proportion to the number of the sub-bands to be extracted. A receiving system having the same configuration as the above up to the signal processing unit is required.
Japanese Patent No. 3161146 Japanese Patent Application Laid-Open No. 9-200565 Yoshio Urabe and two others, "SR-Chirp System Spread Spectrum Wireless Modem", IEICE Technical Report RCS95-102, The Institute of Electronics, Information and Communication Engineers, November 1995, p. 27-32 Hirohito Yamano, et al., “Batch demodulation method using band-divided filter bank in multi-channel TDMA system”, IEICE General Conference, 1998, B-5-62, p. 426

However, in the data transmitting and receiving apparatus described in Patent Document 1, when extracting different partial band signals, the frequency of the local oscillator must be changed. However, there is a problem that this switching takes time.

On the other hand, in the receiver described in Non-Patent Document 1, since a plurality of local oscillators are prepared in advance, switching of the partial band signal to be extracted does not require time, but baseband signal processing is performed by the frequency mixer. It is necessary to prepare a plurality of analog reception systems having the same configuration up to the section, and there is a problem that the characteristics of each analog circuit must be substantially the same in order to make the characteristics of the plurality of reception systems uniform. . Further, since a plurality of receiving systems need to be prepared, there is a problem that the hardware configuration becomes large.

Focusing on the hardware configuration of the differential detection calculation unit 1103 in the baseband signal processing unit 1512 (see FIG. 29), the complex baseband signal that is the input signal contains a signal unnecessary for demodulation in advance. There is a problem that it needs to be removed using an analog circuit.

Further, the differential detection operation unit 1103 requires one sign inverter, two selectors, one delay unit, and two multipliers. A post-filter is required. Therefore, for example, there is a problem that the gate scale becomes large when implementing the LSI, which is not suitable for miniaturization and weight reduction.

Therefore, an object of the present invention is to extract a partial band signal from a received phase-modulated signal and, for a data receiving apparatus that obtains a detection signal by delay detection, reduce the time required to extract a plurality of partial band signals. An object of the present invention is to provide a data receiving apparatus which can be easily integrated into an LSI and has a simple configuration without reducing the number of analog circuits having the same characteristics.

The present invention is a data receiving apparatus that outputs a detection signal using, as input signals, an in-phase signal and a quadrature signal obtained by performing quadrature detection after frequency-modulating a phase-modulated modulated signal. The data receiving device includes a first sampler, a second sampler, a partial band extractor, and a differential detection calculator. The first sampler samples the in-phase signal every fixed sampling period and outputs the same as a sampled in-phase signal. The second sampler samples the orthogonal signal at a fixed sampling period and outputs the sampled orthogonal signal. The partial band extraction unit is configured by a complex filter, and includes at least a frequency component included in a sampled in-phase signal output by the first sampler and a sampled quadrature signal output by the second sampler. One partial band is extracted and output as a partial band signal. The delay detection calculation unit performs delay detection based on the partial band signal output from the partial band extraction unit, and outputs a detection signal.

Preferably, the partial band extracting section may extract at least one signal whose center frequency is not 0 as a partial band signal to be extracted, and output the signal divided into an in-phase component and a quadrature component.

The partial band extracting unit may extract the partial band signal such that the center frequency of the partial band signal is an integral multiple of the symbol frequency of the transmitted data.

Further, the partial band extracting section may extract the partial band signal such that the number of samples in one symbol period is a multiple of 8 obtained by dividing the center frequency of the partial band signal to be extracted by the symbol frequency. .

(4) The partial band extracting unit may extract an even number of partial band signals. These partial band signals are paired with positive and negative frequencies equidistant from frequency 0 as center frequencies.

Specifically, the differential detection operation unit includes a delay unit, a first multiplier, a second multiplier, a first low-pass filter, and a second low-pass filter. The delay unit delays the in-phase component of the partial band signal output by the partial band extracting unit by one symbol time and outputs the delayed signal. The first multiplier multiplies the in-phase component of the partial band signal output from the partial band extraction unit by the output of the delay unit, and outputs the result as an in-phase component data sequence. The second multiplier multiplies the orthogonal component of the partial band signal output by the partial band extracting unit with the output of the delay unit, and outputs the result as an orthogonal component data sequence. The first low-pass filter removes and outputs high-frequency components of the in-phase component data string output from the first multiplier. The second low-pass filter removes and outputs high-frequency components of the orthogonal component data string output from the second multiplier.

In addition, the partial band extraction unit includes a first filtering device, a second filtering device, a third filtering device, a fourth filtering device, a first subtractor, a first adder, It includes a second subtractor and a second adder. The first filtering device is a complex filter, and calculates and outputs a convolution integral of a sampled in-phase signal and an in-phase component of a transfer function of the complex filter. The second filtering device is a complex filter, and calculates a convolution integral of the sampled orthogonal signal and an orthogonal component of a transfer function of the complex filter. The third filtering device is a complex filter, and calculates a convolution integral of the sampled quadrature signal and an in-phase component of a transfer function of the complex filter. The fourth filtering device is a complex filter, and calculates a convolution integral of the sampled in-phase signal and a quadrature component of a transfer function of the complex filter. The first subtractor subtracts a signal output by the second filtering device from a signal output by the first filtering device. The first adder adds a signal output from the first filtering device and a signal output from the second filtering device. The second subtractor subtracts a signal output from the fourth filtering device from a signal output from the third filtering device. The second adder adds the signal output from the third filtering device and the signal output from the fourth filtering device.

Further, the partial band extraction unit includes a first input selector, a second input selector, a first filtering device, a second filtering device, a first output selector, and a second output selector. It includes a selector, a first delay unit, a second delay unit, a first subtractor, a first adder, a second subtractor, and a second adder. The first input selector uses the sampled in-phase signal and the sampled quadrature signal as input signals, and alternately selects and outputs a sampled in-phase signal and a sampled quadrature signal every half a sample period. The second input selector uses the sampled in-phase signal and the sampled quadrature signal as input signals and alternately selects and outputs a sampled in-phase signal and a sampled quadrature signal every half of the sample period. The first filtering device is a complex filter, and performs convolution integration of a signal output from the first input selector and an in-phase component of the complex filter. The second filtering device is a complex filter, and performs convolution integration of a signal output from the second input selector and an orthogonal component of the complex filter. The first output selector alternately outputs an output signal from the first filtering device that changes in a half cycle of the sampling cycle to the first output terminal and the second output terminal in a half cycle of the sampling cycle. I do. The second output selector alternately outputs an output signal from the second filtering device that changes in a half cycle of the sampling cycle to a third output terminal and a fourth output terminal in a half cycle of the sampling cycle. I do. The first delay unit delays the signal output from the first output terminal of the first output selector by a half of a sample period. The second delay unit delays the signal output from the third output terminal of the second output selector by half the sample period. The first subtractor subtracts a signal output from the second delay unit from a signal output from the first delay unit. The first adder adds a signal output from the first delay unit and a signal output from the second delay unit. The second subtractor subtracts a signal output from a fourth output terminal of the second output selector from a signal output from a second output terminal of the first output selector. The second adder adds the signal output from the second output terminal of the first output selector and the signal output from the fourth output terminal of the second output selector.

{Preferably, the partial band extracting section may extract the partial band signal such that the center frequency of the partial band signal is an integral multiple of the symbol frequency of the transmitted data.

(4) The partial band extracting section may extract the partial band signal such that the number of samples in one symbol period is a multiple of 8 obtained by dividing the center frequency of the partial band signal to be extracted by the symbol frequency.

Preferably, the delay detection calculation unit performs delay detection using the partial band signal output from the partial band extraction unit as an intermediate frequency signal.

Preferably, the modulated signal is a signal from which a demodulated partial band signal can be obtained by extracting at least one partial band from a frequency band of the modulated signal.

Preferably, the modulated signal is a signal subjected to spread spectrum.

Preferably, the modulated signal is a spread spectrum signal using a chirp signal obtained by repeatedly sweeping the frequency of a sine wave at regular intervals as a spread signal.

In a preferred embodiment, the data receiving device is used for a wireless communication device. The wireless communication device may perform a reception process by selecting one of a plurality of pieces of reception data obtained based on a plurality of partial bands, or obtain one piece of reception data by integrating a plurality of pieces of reception data. Alternatively, a plurality of received data may be processed in parallel at the same time.

The data receiving apparatus according to the present invention extracts a partial band signal in a partial band extracting unit formed of a digital circuit, performs delay detection based on the partial band signal, and outputs a signal for obtaining a demodulated signal. I do. That is, a partial band signal is extracted by digital processing. Therefore, it is possible to provide a data receiving apparatus which does not require an analog circuit corresponding to the number of partial band signals to be extracted unlike the related art and does not require time for switching the partial band signals. Therefore, an increase in the hardware configuration can be suppressed. In addition, since signals other than the required partial band are removed in the partial band extracting unit, it is not necessary to remove unnecessary signals such as interference waves (interference waves due to interference) using an analog circuit.

(4) Since the partial band signal is an intermediate frequency signal whose center frequency is not 0, it is not necessary to perform a vector operation, and it is possible to simplify the differential detection operation unit.

Delay detection for making the center frequency of the partial band signal an integral multiple of the symbol frequency of the transmitted data without generating unnecessary phase rotation components and for making it equivalent to delay detection calculation using a complex baseband signal The operation unit can be simplified.

By extracting the partial band signal such that the number of samples in one symbol period is a multiple of 8 obtained by dividing the center frequency of the partial band signal to be extracted by the symbol frequency, the partial band extracting unit sets the tap coefficient to 0. Can be omitted, and the in-phase component and the quadrature component of some tap coefficients can be shared, so that the tap coefficient multiplier of the complex filter constituting the partial band extraction unit can be used. Can be further reduced.

The partial band extraction unit extracts an even number of partial band signals, and these partial band signals are paired with the positive and negative frequencies that are equidistant from the frequency 0 as the center frequency. Since the convolution integral operation can be shared in the configuration of the complex filter for extraction, the partial band extraction section can be realized with a simple configuration.

Since the differential detection operation unit is realized by one delay unit, two multipliers, and two low-pass filters, it is possible to realize a delay detection operation unit with a smaller hardware configuration than in the related art. .

こ と Further, by making the partial band extracting unit as in the present invention, the partial band extracting unit is simplified, and unnecessary phase rotation components are not generated, and the differential detection calculating unit can be simplified.

The delay detection calculation unit can use the phase rotation component of the intermediate frequency signal by performing the delay detection using the partial band signal detected by the partial band extraction unit as the intermediate frequency signal. It is possible to configure easily.

The modulated signal is a signal obtained from a demodulated partial band signal by extracting at least one partial band from a frequency band of the modulated signal, thereby obtaining a demodulated partial band signal from the modulated signal. It will be easier.

(4) It is more effective in practical use than using a generally used spread spectrum signal.

(4) By using a chirp signal obtained by repeatedly sweeping (sweeping) the frequency of a sine wave at regular intervals as a spread signal, it is effective in practical use.

(1st Embodiment)
FIG. 1 is a diagram showing a configuration of a data receiving device 1 according to the first embodiment of the present invention. The data receiving device 1 is a device for extracting at least one partial band signal from a frequency component of a received phase modulation signal and obtaining a detection signal by delay detection. FIG. 1 shows a data receiving apparatus that extracts two partial bands. In FIG. 1, a data receiving apparatus 1 includes a first sampler 100, a second sampler 101, a partial band extraction unit 102, a first delay detection operation unit 103, and a second delay detection And an operation unit 104. A frequency conversion circuit 105 is connected before the first sampler 100 and the second sampler 101.

FIG. 2 is a signal spectrum diagram for schematically explaining how to obtain in-phase component I (t) and quadrature component Q (t) of a complex baseband signal from a high-frequency signal input to frequency conversion circuit 105. Hereinafter, the operations of the frequency conversion circuit 105 and the data receiving device 1 will be described with reference to FIGS.

In FIG. 2, a high-frequency modulated signal r (t) is a high-frequency signal based on a spread spectrum method or the like, and is a signal input to the frequency conversion circuit 105. The center frequency of the high frequency modulated signal r (t), and f _i. It is assumed that the high-frequency modulated signal r (t) includes a first partial band high-frequency modulated signal 202 and a second partial band high-frequency modulated signal 203. Each partial band high frequency modulated signal is a signal that can be demodulated by itself. Here, for the sake of simplicity, high frequency modulated signal r (t) includes two partial band high frequency modulated signals 202 and 203, but three or more partial band high frequency modulated signals A signal may be included.

The frequency conversion circuit 105 is an analog circuit, and is, for example, a known circuit including one frequency converter, a local oscillator, a band-pass filter, a gain controller, and a quadrature detector as shown in FIG. The frequency conversion circuit 105 frequency-converts the input high-frequency modulated signal r (t) into a signal having a center frequency of 0, and performs low-pass filtering. Thereby, the high frequency modulated signal r (t) is converted into a complex baseband signal 205 having a center frequency of 0, the first partial band high frequency modulated signal 202 is converted into a first partial band complex signal 206, The second partial band high frequency modulated signal 203 will be converted into a second partial band complex signal 207.

The frequency conversion circuit 105 outputs the in-phase component I (t) and the quadrature component Q (t) of the complex baseband signal 205 and inputs them to the first sampler 100 and the second sampler 101, respectively. The in-phase component I (t) and the quadrature component Q (t) include signals having the same spectrum as the first partial band complex signal 206 and the second partial band complex signal 207.

The first sampler 100 samples the in-phase component I (t) of the complex baseband signal input from the frequency conversion circuit 105 and outputs a complex baseband signal in-phase component data sequence I (nT). It is input to the band extraction unit 102. Here, n is an integer (n =... -1, 0, 1,...), And T is a sampling period. The second sampler 101 samples the orthogonal component Q (t) of the input complex baseband signal and outputs a complex baseband signal orthogonal component data sequence Q (nT). input. Note that the complex baseband signal in-phase component data sequence may be referred to as a sampling in-phase component. Also, the complex baseband signal orthogonal component data sequence may be referred to as a sampled orthogonal component.

The complex baseband signal in-phase component data sequence I (nT) and the complex baseband signal quadrature component data sequence Q (nT) are signals obtained by sampling I (t) and Q (t) at the timing of the sampling period T, respectively. It is. Therefore, the orthogonal relationship established between I (t) and Q (t) also holds between I (nT) and Q (nT).

The partial band extraction unit 102 is formed of a complex filter, and has an in-phase component of a partial band signal of the input complex baseband signal in-phase component data sequence I (nT) (hereinafter, referred to as a partial band signal in-phase component data sequence) IB. _r (nT) and the orthogonal component QB _r (nT) of the partial band signal of the complex baseband signal orthogonal component data sequence Q (nT) (hereinafter referred to as the partial band signal orthogonal component data sequence) do not have a center frequency of 0. In this way, m identical bands are extracted and output. Here, r = 1, 2, 3,..., M and m are positive integers (m = 1, 2, 3,...). FIG. 1 shows a case where m = 2 as an example. I (nT) and Q (nT) have the partial band signal in-phase component data sequence IB _r (nT) and the partial band signal quadrature component data sequence QB _r (nT) output from the partial band extraction unit 102. It maintains orthogonality.

The first partial band complex signal 206 has a partial band signal in-phase component data sequence IB ₁ (nT) as an in-phase component and a partial band signal quadrature component data sequence QB ₁ (nT) as a quadrature component. Similarly, the second partial band complex signal 207 has a partial band signal in-phase component data sequence IB ₂ (nT) as an in-phase component and a partial band signal quadrature component data sequence QB ₂ (nT) as a quadrature component. .

As shown in FIG. 2, the partial band signal in-phase component data sequence IB ₁ (nT), the partial band signal quadrature component data sequence QB ₁ (nT), the partial band signal in-phase component data sequence IB ₂ (nT), and the partial band signal quadrature The component data string QB ₂ (nT) does not include a DC component. Therefore, these signals can be said to be intermediate frequency signals that have their own phase rotation.

Since the partial band extraction unit 102 extracts a partial band signal required to obtain a demodulated signal from the complex baseband signal, the unnecessary signal included in the input signals I (t) and Q (t) is extracted. Will be removed. For example, when extracting the first partial band complex signal 206, the partial band extracting unit 102 removes all signals having frequency components other than the first partial band complex signal 206.

The partial band extraction unit 102 inputs the partial band signal in-phase component data sequence IB ₁ (nT) and the partial band signal quadrature component data sequence QB ₁ (nT) to the first differential detection calculation unit 103, and outputs the partial band signal in-phase component Data sequence IB ₂ (nT) and partial band signal quadrature component data sequence QB ₂ (nT) are input to second differential detection operation section 104.

The first differential detection operation section 103 generates a partial band detection signal in-phase component data sequence based on the input partial band signal in-phase component data sequence IB ₁ (nT) and partial band signal quadrature component data sequence QB ₁ (nT). BI ₁ (nT) and a partial band detection signal orthogonal component data sequence BQ ₁ (nT) are output. The second differential detection operation section 104 generates a partial band detection signal in-phase component data sequence based on the input partial band signal in-phase component data sequence IB ₂ (nT) and partial band signal quadrature component data sequence QB ₂ (nT). BI ₂ (nT) and a partial band detection signal orthogonal component data sequence BQ ₂ (nT) are output.

A determination circuit (not shown) is connected to the output side of the first delay detection calculation section 103 and the second delay detection calculation section 104. The determination circuit (not shown) includes a partial band detection signal in-phase component data sequence BI ₁ (nT) and a partial band detection signal quadrature component data sequence BQ ₁ (nT) output from the first differential detection calculation unit 103, and 2 based on the partial-band detection signal in-phase component data sequence BI ₂ (nT) and the partial-band detection signal quadrature component data sequence BQ ₂ (nT) output by the differential detection operation unit 104 of FIG. Then, for example, more appropriate received data is output according to the reception status such as the number of errors or CRC errors.

FIG. 3 is a diagram showing a configuration of the first delay detection calculation unit 103 or the second delay detection calculation unit 104 in FIG. Since the configuration of the first delay detection calculation unit 103 and the configuration of the second delay detection calculation unit 104 are the same, the first delay detection calculation unit 103 will be described below as a representative. In FIG. 3, the first differential detection calculation unit 103 includes a delay unit 302, a first multiplier 304, a second multiplier 305, a first low-pass filter 308, and a second low-pass filter 308. And a pass filter 309.

　ここで、ａ（ｎＴ）は部分帯域信号をベースバンド帯域で表示した場合の複素ベースバンド信号を、ωは部分帯域信号の中心周波数の角周波数を表している。 Next, the operation of the first differential detection calculation section 103 will be described.
When a partial band signal that is an input signal to the first differential detection calculation unit 103 is represented as S (nT), S (nT) is represented as (Expression 1) using complex notation.

Here, a (nT) represents the complex baseband signal when the partial band signal is displayed in the baseband band, and ω represents the angular frequency of the center frequency of the partial band signal.

The partial band signal in-phase component data sequence IB _r (nT) and the partial band signal quadrature component data sequence QB _r (nT) are the in-phase component and the quadrature component of S (nT), respectively. Is done. Note that in the case of the first differential detection calculation unit 103, r = 1.

The partial band signal in-phase component data sequence IB _r (nT) is input to first multiplier 304 and delay device 302. The delay unit 302 delays IB _r (nT) by one symbol time length kT, outputs it as a partial band signal in-phase component delay data sequence IB _r (nT-kT), and outputs a first multiplier 304 and a second multiplier Input to the container 305. Here, k is the number of samples per symbol.

The first multiplier 304 multiplies IB _r (nT) and IB _r (nT−kT) to generate a differential detector in-phase component data sequence DETI _r (nT), and supplies the delayed low-pass filter 308 to the first low-pass filter 308. input. The second multiplier 305 multiplies QB _r (nT) by IB _r (nT−kT) and generates a differential detector quadrature component data sequence DETQ _r (nT) for the second low-pass filter 309. input. DETI _r (nT) is expressed as (Equation 3). DETQ _r (nT) is expressed as (Equation 4).

The first low-pass filter 308 removes high-frequency components from DETI _r (nT) and inputs the result to a determination circuit (not shown) as BI _r (nT). The second low-pass filter 309 removes high-frequency components from DETQ _r (nT) and inputs the result to a determination circuit (not shown) as BQ _r (nT). BI _r (nT) is represented as (Equation 5). BQ _r (nT) is represented as (Equation 6).

ここで、ωｋＴ＝２πｚ（ただしｚは整数；ｚ＝・・・、−１、０、１、・・・）となるように部分帯域信号の中心周波数の角周波数ωを選ぶと、すなわち、部分帯域信号の中心周波数をＦｂ、シンボル周波数をＦｓとした場合、ω＝２πＦｂ、ｋＦｓ＝１／Ｔより、部分帯域信号の中心周波数が受信すべきデータのシンボル周波数の整数倍となるようにωを選ぶと、ｅｘｐで表される項は常に１となるので、（式７）は（式８）のように表される。

The complex conjugate multiplication of S (nT) and S (nT-kT), which is a signal obtained by delaying S (nT) by one symbol time length, is represented by using a (nT) as shown in (Equation 7). Is done.

Here, when the angular frequency ω of the center frequency of the partial band signal is selected so that ωkT = 2πz (where z is an integer; z =... -1, 0, 1,...) When the center frequency of the band signal is Fb and the symbol frequency is Fs, ω is set so that the center frequency of the partial band signal becomes an integral multiple of the symbol frequency of the data to be received from ω = 2πFb and kFs = 1 / T. When selected, the term represented by exp is always 1, so (Expression 7) is expressed as (Expression 8).

(Equation 8) is clearly equivalent to a differential detection operation using a complex baseband signal. Therefore, the first differential detection operation unit 103 does not require one sign inverter and two selectors, which were conventionally required (see FIG. 29), and as shown in FIG. Delay detection can be realized by a simple configuration using only a multiplier, two multipliers, and two low-pass filters. The same applies to the second delay detection calculation section 104.

As described above, the data receiving device 1 according to the first embodiment of the present invention uses the partial band extracting unit 102 to convert a partial band signal whose center frequency is not 0 from the complex baseband signal of the received modulated signal. At least one is extracted, and differential detection is performed using the extracted signal that is an intermediate frequency signal. When extracting a plurality of partial bands, the data receiving apparatus 1 simultaneously extracts a plurality of partial band signals from one complex baseband signal by using a partial band extracting unit 102 realized by a complex filter. That is, a partial band signal is extracted by digital processing. Therefore, it is possible to provide a data receiving device that does not require time for switching the local oscillation signal and does not require a plurality of analog circuits for extracting a plurality of partial band signals.

In addition, since signals other than the necessary partial band are removed by the partial band extracting unit 102, the data receiving apparatus 1 does not remove unnecessary signals such as interference waves using an analog circuit as in the related art. It is possible to use a complex baseband signal.

{Circle around (2)} Since the partial band signal extracted by the partial band extracting unit 102 is an intermediate frequency signal with a phase rotation, the data receiving apparatus can perform the differential detection operation using the intermediate frequency signal.

Also, by selecting ω so that the center frequency of the partial band signal is an integer multiple of the symbol frequency of the data to be received, two selectors and one sign inverter are not required as in the related art, and one It can be realized with a delay unit, two multipliers, and two low-pass filters. Therefore, it is possible to provide a data receiving apparatus that solves the problem related to the reduction of the hardware scale when implementing the LSI, which is one of the conventional problems.

Further, the data receiving apparatus 1 according to the first embodiment of the present invention converts the high-frequency modulated signal into an intermediate-frequency signal and then samples the intermediate-frequency signal directly with a sampler. After orthogonally transforming the modulated signal, a partial band signal obtained by removing unnecessary signals from a complex baseband signal obtained as a result of the orthogonal transform is extracted and used as an intermediate frequency signal. Therefore, in the data receiving apparatus 1 according to the first embodiment of the present invention, it is sufficient that the signal processing bandwidth required for the sampler is at least half the bandwidth of the high-frequency modulated signal. There is also an advantage that the data receiving apparatus of the present invention can be realized using a cheaper sampler.

Note that, as the high-frequency modulated signal used in the above embodiment, a spread spectrum signal is obtained by using a chirp signal obtained by repeatedly sweeping (sweeping) the frequency of a sine wave at regular intervals on a phase-modulated signal. The performed signal is used as an example. FIG. 4 is a diagram illustrating an example of a signal obtained by performing spectrum spreading using a chirp signal as a spread modulation signal.

In the above embodiment, the frequency conversion circuit 105 converts the frequency of the high-frequency modulated signal r (t) so that the center frequency becomes 0. However, the partial band extraction unit 102 determines that the center frequency is 0. If a partial band signal that does not need to be extracted is extracted, the frequency conversion circuit 105 may perform frequency conversion so that the center frequency does not become zero.

In the above embodiment, the angular frequency ω of the center frequency of the partial band signal is selected so that ωkT = 2πz. Alternatively, ω may be selected so that ωkT = (2z + 1) π. In this case, the signal output from the first differential detection operation unit 103 is a signal obtained by inverting the sign of (Equation 8), and thus the signal is output after the first low-pass filter 308 and the second low-pass filter 309. By providing a sign inverter, the same result as that of the circuit shown in FIG. 3 can be obtained.

Note that the same effect can be obtained even when ωkT is not equal to 2πz or (2z + 1) π. FIG. 5 is a diagram illustrating a configuration of the first or second differential detection calculation units 103 and 104 when a phase rotator is provided. In FIG. 5, the first and second delay detection calculation units 103 and 104 include a delay unit 402, a first multiplier 404, a second multiplier 405, a first low-pass filter 408, A second low-pass filter 409 and a phase rotator 412 are included.

The operation of obtaining the differential detector in-phase component data sequence DETI _r (nT) and the differential detector quadrature component data sequence DETQ _r (nT) in the differential detection operation units 103 and 104 shown in FIG. This is the same as in the case of the detection calculation unit.

However, when ωkT is equal to 2πz, (Expression 7) can be expressed as (Expression 8), and when ωkT is equal to (2z + 1) π, (Expression 7) is multiplied by (Expression 8) by −1. Although the expression can be expressed as the following expression (an expression obtained by inverting the sign of (Expression 8)), in other cases, the above expression cannot be performed. Therefore, the phase rotator 412 multiplies the signal represented by (Expression 7) by exp (-jωkT) so that the signal represented by (Expression 7) can be represented by (Expression 8). By performing this operation, the phase rotator 412 obtains an effect equivalent to a differential detection operation using a complex baseband signal as shown in FIG. 3 even when ωkT is not equal to 2πz or (2z + 1) π. be able to.

In the above embodiment, the partial band extraction unit 102 outputs both the in-phase component data sequence and the quadrature component data sequence, but may output either one. However, in this case, it is necessary to provide an orthogonal transformer on the output side of the partial band extraction unit 102. FIG. 6 is a diagram illustrating a configuration of the data receiving device 1 when an orthogonal transformer is provided. As shown in FIG. 6, orthogonal transformers 106 and 107 are provided on the output side of partial band extraction section 102, and convert in-phase component data strings (or quadrature component data strings) output from partial band extraction section 102. The orthogonal transform is performed, and the in-phase component data sequence and the quadrature component data sequence are input to the first and second differential detection operation units 103 and 104.

(Second embodiment)
In the first embodiment, a high-frequency modulated signal including a plurality of partial band signals is input to the data receiving device. However, in the second embodiment, a case where a single modulated signal is input is described. The data receiving device will be described.

FIG. 7 is a diagram showing the configuration of the data receiving device 2 according to the second embodiment of the present invention. 7, the data receiving device 2 includes a first sampler 500, a second sampler 501, a partial band extractor 502, and a differential detection calculator 503. A frequency conversion circuit 505 is connected to a stage preceding the first sampler 500 and the second sampler 501. A determination circuit (not shown) is connected to a stage subsequent to the differential detection calculation unit 503.

Hereinafter, operations of the frequency conversion circuit 505 and the data receiving device 2 will be described. First sampler 500 samples in-phase component I (t) of the complex baseband signal output from frequency conversion circuit 505, and outputs a complex baseband signal in-phase component data sequence I (nT). The second sampler 501 samples the orthogonal component Q (t) of the complex baseband signal and outputs a complex baseband signal orthogonal component data sequence Q (nT).

FIG. 8 is a signal spectrum diagram for schematically explaining how to obtain in-phase component I (t) and quadrature component Q (t) of a complex baseband signal from a high-frequency signal input to frequency conversion circuit 505. In FIG. 8, the received modulated signal r (t) is a high-frequency signal input to the frequency conversion circuit 505. The center frequency of the received modulated signal r (t) is f _i. Frequency conversion circuit 505 regards a band including received modulated signal r (t) and unnecessary signal 603 as virtual modulated signal 607. Frequency converting circuit 505, as the frequency conversion reference frequency f _a of the virtual modulated signal 607 is converted into a complex baseband signal center frequency f _c = 0, the virtual modulated signal 607 to frequency conversion and quadrature detection Output a complex baseband signal.

By this frequency conversion, the received modulated signal r (t) is frequency-converted into a complex signal 605, and the unnecessary signal 603 is frequency-converted into an unnecessary complex signal 606. Therefore, a complex baseband signal which is an input signal of the first sampler 500 and the second sampler 501 is an analog signal in which the spectrum of the complex signal 605 and the spectrum of the unnecessary complex signal 606 are mixed. Therefore, even if the complex baseband signal is low-pass filtered using a low-pass filter, the complex signal 605 and the unnecessary complex signal 606 cannot be separated.

In the data receiving apparatus 2, the complex baseband signal including the complex signal 605 and the unnecessary complex signal 606 becomes an input signal to the first sampler 500 and the second sampler 501. Since the partial band extracting section 502 extracts the partial band from the complex baseband signal using the complex filter, the partial band extracting section 502 can separate and extract the complex signal 605 and the unnecessary complex signal 606. The partial band extracting section 502 extracts only the complex signal 605 having a band substantially equal to the band of the modulated signal to be received, and outputs a partial band signal in-phase component data sequence IB (nT), which is an in-phase component of the complex signal 605. And a quadrature component data sequence QB (nT), which is a partial band signal that is an orthogonal component.

こ の As shown in FIG. 8, this partial band signal is an intermediate frequency signal whose center frequency is not 0. Therefore, by using the same configuration (see FIG. 3) as the delay detection calculation unit shown in the first embodiment, the delay detection calculation unit 503 can detect the detection signal in-phase component data in the same manner as in the first embodiment. A column BI (nT) and a detection signal quadrature component data column BQ (nT) are output.

As described above, the data receiving apparatus 2 according to the second embodiment of the present invention uses the complex baseband signal including the modulated signal as a partial band from the virtual modulated signal frequency-converted so that the center frequency does not become 0. Is extracted using a partial band extraction unit 502 composed of a complex filter, excluding unnecessary signal components. That is, the data receiving apparatus 2 extracts an intermediate frequency signal including almost all frequency components of the modulated signal that has been frequency-converted into a low frequency band, performs delay detection using the extracted intermediate frequency signal, and performs detection. Get the signal. Therefore, the data receiving apparatus 2 according to the second embodiment is different from the first embodiment in that at least one partial band component is extracted from the frequency components of the received modulated signal to obtain a demodulated signal. Can also be used for demodulation of the phase modulation method.

Further, the data receiving apparatus 2 according to the second embodiment uses a complex filter as an input signal to receive a plurality of modulated wave signals using a complex baseband signal including a plurality of modulated wave signals having mutually different band characteristics. Can be applied at the same time to obtain a detection signal. However, in this case, an individual determination circuit is required for each modulated wave signal.

In the above embodiment, a signal whose spectrum is shown in FIG. 8 is used as the received modulated signal r (t) to be received, and the unnecessary signal 603 to be removed is used. Can be obtained.

(4) If the number of partial band signals to be extracted is increased, modulated signals corresponding to the number of extracted partial bands can be simultaneously detected.

(Third embodiment)
Next, a detailed configuration of the partial band extraction unit 102 in the data receiving device 1 according to the first embodiment will be described. First, the theory that is the basis of the configuration of the sub-band extraction unit 102 will be described using mathematical expressions.

　（式９）および（式１０）において、＊は畳み込み積分演算を、ｊは虚数単位を表している。 Now, it is assumed that the center frequencies of the two partial band signals to be extracted are equidistant from each other by 0 to 1 MHz. Further, it is assumed that a transfer function of a complex filter included in the sub-band extraction unit 102 for extracting the sub-band complex signal 207 shown in FIG. 2 is represented by Hb (nT). In this case, the transfer function of the complex filter for extracting the partial band complex signal 206 shown in FIG. 2 is a complex conjugate of Hb (nT). As a result, assuming that the partial band complex signal 207 is represented by S2 (nT) and the partial band complex signal 206 is represented by S1 (nT), S2 (nT) and S1 (nT) are represented by (Equation 9) and (Equation 10). Is represented as

In (Equation 9) and (Equation 10), * represents a convolution integral operation, and j represents an imaginary unit.

Comparing the in-phase component and the quadrature component of S2 (nT) and S1 (nT) in (Equation 9) and (Equation 10), the in-phase component is Re (S (nT)) * Re (Hb (nT) ) And Im (S (nT)) * Im (Hb (nT)), where the orthogonal components are Im (S (nT)) * Re (Hb (nT)) and Re (S (nT)) * Im (Hb ( nT)). By using this mathematical theory, the partial band extraction unit 102 in the first embodiment can be easily realized. Hereinafter, the configuration of the partial band extraction unit 102 will be specifically described.

FIG. 9 is a diagram illustrating a configuration of a sub-band extraction unit according to the third embodiment. The partial band extraction unit 102 shown in FIG. 9 utilizes the mathematical theoretical results shown in (Equation 9) and (Equation 10). In FIG. 9, the partial band extraction unit 102 includes a first filtering device 1701, a second filtering device 1702, a third filtering device 1703, a fourth filtering device 1704, a first subtractor 1705, , A second subtractor 1707, a first adder 1706, and a second adder 1708.

In FIG. 9, if the input signal Re {S (nT)} is associated with I (nT) and the input signal Im {S (nT)} is associated with Q (nT), the data receiving apparatus according to the first embodiment will be described. One partial band extraction unit 102 is realized.

The first filtering device 1701 performs a convolution integral operation of Re (S (nT)) * Re (Hb (nT)). Similarly, the second filtering device 1702 calculates Im (S (nT)) * Im (Hb (nT)). The third filtering device 1703 calculates Im (S (nT)) * Re (Hb (nT)). The filtering device 1704 calculates Re (S (nT)) * Im (Hb (nT)).

The first subtractor 1705 performs an operation of Re (S (nT)) * Re (Hb (nT))-Im (S (nT)) * Im (Hb (nT)) to obtain a partial band complex signal. The in-phase component of S2 (nT) is output. The second adder 1708 performs an operation of Im (S (nT)) * Re (Hb (nT)) + Re (S (nT)) * Im (Hb (nT)) to obtain the partial band complex signal S2. Output the (nT) orthogonal component.

The first adder 1706 performs an operation of Re (S (nT)) * Re (Hb (nT)) + Im (S (nT)) * Im (Hb (nT)) to obtain a partial band complex. An in-phase component of the signal S1 (nT) is output. The second subtractor 1707 performs the operation of Im (S (nT)) * Re (Hb (nT))-Re (S (nT)) * Im (Hb (nT)) to obtain the complex signal S1 ( nT).

Thus, partial band extracting section 102, the IB ₁ (nT) as an output signal _{Im {S 1 (nT)}} , QB 1 as Re {S ₁ (nT)} a _{(nT), Im {S 2} (nT ) IB ₂ a (nT) as}, and output the QB ₂ (nT) as _{Re {S 2 (nT)}} ( refer to FIG. 1).

As described above, in the third embodiment, as represented by (Equation 9) and (Equation 10), since the filtering devices having the common tap coefficients are shared, the partial band extraction unit is used. It is possible to simplify the configuration of 102.

In the above embodiment, two partial band signals are extracted. However, the present invention can be applied to a case where a plurality of partial bands are extracted. Specifically, filtering devices having a common tap coefficient may be shared so as to constitute a partial band extracting unit.

(Fourth embodiment)
In the partial band extraction unit 102 shown in FIG. 9, it is necessary to prepare two filtering devices 1701 and 1703 and two filtering devices 1702 and 1704 having the same configuration. In the fourth embodiment, a description will be given of a partial band extracting unit that combines overlapping filtering devices into one.

FIG. 10 is a diagram illustrating a configuration of a partial band extraction unit according to the fourth embodiment. In FIG. 10, the partial band extraction unit 102 includes a first input selector 2101, a second input selector 2102, a first filtering device 2103, a second filtering device 2104, and a first output selection device. , A second output selector 2106, a first subtractor 2107, a second subtractor 2109, a first adder 2108, a second adder 2110, a first delayer 2 and a second delay unit 2112.

Hereinafter, the operation of the partial band extraction unit 102 shown in FIG. 10 will be described.
The first input selector 2101 and the second input selector 2102 alternately select two input signals whose values change in the period τ every period τ / 2, and output the selected signals. FIG. 11 is a timing chart showing the operation of the first input selector 2101 or the second input selector 2102.

第 The first filtering device 2103 connected to the subsequent stage of the first input selector 2101 performs convolution integration on a signal input every period τ / 2. The second filtering device 2104 performs convolution integration on a signal input every period τ / 2.

The first output selector 2105 and the second output selector 2106 output a signal whose value changes at a period of τ / 2 to two different output terminals every period τ / 2 in synchronization with a data change timing. Output. FIG. 12 is a timing chart showing the operation of the first output selector 2105 or the second output selector 2106.

FIG. 13 is a timing chart of signals output from the first input selector 2101 or the second input selector 2102. As can be seen from FIGS. 11 and 12, the first input selector 2101 and the second input selector 2102 receive the signal Re {S (nT)} and the signal Im {S (nT)} that change in the cycle T. In this case, assuming that τ is equal to T, the signals Bil and Bi2 output from the first input selector 2101 and the second input selector 2102 change at the timing shown in FIG. Go.

FIG. 14 is a timing chart of signals output from the first output selector 2105 or the second output selector 2106. Since the first filtering device 2103 and the second filtering device 2104 perform convolution integration every period T / 2, the signals C1 and C2 output from the first output selector 2105 and the second output selector 2106 The signals C3 and C4 output from the CPU change at timings as shown in FIG.

The above-mentioned outputs C1 to C4 will be specifically described on the assumption that there is no signal processing delay. For example, when Bi1 is Re {S (nT)}, Bi2 is Im {S (nT)}. At this time, C1 (nT) becomes Re {S (nT)} * Re {Hb} for one cycle. C2 (nT) becomes Im {S ((n-1) T)} * Re {Hb} in the first half of this cycle, and Im {S (nT)} * Re {Hb} in the second half of this cycle. Become. C3 (nT) becomes Im {S (nT)} * Im {Hb} during this one cycle. C4 (nT) becomes Re {S ((n-1) T} * Im {Hb} in the first half of this cycle, and becomes Re {S (nT)} * Im {Hb} in the second half of this cycle. .

The first delay unit 2 delays the signal C1 by the time U = T / 2, and the second delay unit 2112 delays the signal C3 by the time U = T / 2, so that the first subtractor 2107 and the first The timing of the signal input to the adder 2108 is substantially the same. The timings of the signals input to the second subtractor 2109 and the second adder 2110 are substantially the same.

Therefore, as can be seen from the specific examples, (Equation 9) and (Equation 10), the first adder 2108 outputs the in-phase component of the partial band complex signal S1 (nT). The second subtractor 2109 outputs the quadrature component of the complex signal S1 (nT). The first subtractor 2107 outputs an in-phase component of the partial band complex signal S2 (nT). Second adder 2110 outputs the quadrature component of complex signal S2 (nT).

As shown in (Equation 9) and (Equation 10), if a pair of partial band complex signals located at the same distance from frequency 0 is paired, taps of a complex filter for extracting the pair of partial band complex signals are provided. The coefficients can be in a complex conjugate relationship with each other. Therefore, it is possible to share a filtering device for extracting each partial band as in the partial band extracting unit in the fourth embodiment.

In the above specific example, the number of partial bands to be extracted is two. However, when there are four or more even number of partial bands, a pair of partial bands whose center frequency is equidistant from the frequency 0 is set as a pair. Tap coefficients can be shared for pairs.

In the above embodiment, the input selection devices 2101 and 2102 select input signals in the order of the in-phase component and the quadrature component of S (nT) for each T / 2. However, this order is reversed. Is also good. That is, the quadrature component and the in-phase component may be selected in this order. In this case, the first delay unit 2 is connected to the output terminal on the C2 side of the first output selector 2105, and the second delay unit 2112 is connected to the output terminal on the C4 side of the second output selector 2106. What should I do?

(Fifth embodiment)
FIG. 15 is a diagram illustrating a general configuration of a complex filter used in a filtering device in the partial band extraction units according to the third and fourth embodiments. FIG. 15 shows a configuration in which an FIR (Finite Impulse Response) filter is used as a complex filter. In the fifth embodiment, a method for making the FIR filter simpler will be described.

FIG. 16 is a complex plan view for explaining tap coefficients of a complex filter. FIG. 17 is a schematic diagram illustrating a passband characteristic of a complex filter used in a partial band extraction unit in a baseband band.

In FIG. 15, the FIR filter includes u−1 delay units 900, u tap coefficient multipliers 903, and one adder 906. Here, u is an integer of 2 or more. In the drawing, h1, h2,..., Hu indicate the complex tap coefficient values of each tap coefficient multiplier 903. X (nT) is a complex signal data sequence. Y (nT) is a complex signal data sequence after waveform shaping.

In order to extract a sub-band signal whose center frequency is Fb using a low-pass filter having a pass band characteristic shown in FIG. 17, a phase rotation component is previously added to each tap coefficient of the filter showing the pass band characteristic. It must be multiplied. Now, assuming that the symbol frequency of the data to be transmitted is Fs, the phase rotation component θ to be multiplied by the tap coefficient hd (where d = 1, 2, 3,..., U) is given by (Equation 11) ).

The relationship between the angular frequency ω of the center frequency of the partial band signal to be extracted and the sample period T is ωkT = 2πz (where z is an integer; z =... -1, 0, 1,...). That is, if the angular frequency ω of the center frequency in the extracted sub-band signal is selected so that the center frequency of the sub-band signal is an integral multiple of the symbol frequency of the data to be transmitted, the differential detection calculation units 103 and 104 The simple implementation has been described in the first embodiment.

　なぜなら、ｋとｚとの関係が（式１２）のように表される場合、タップ係数ｈｄに乗算すべき位相回転成分θの集合には、（式１１）より、同相成分あるいは直交成分のいずれか一方を０にする０ｒａｄ，π／２ｒａｄ，πｒａｄ，３π／２ｒａｄが含まれ、かつ、同相成分および直交成分の絶対値が同じ値となるπ／４ｒａｄ，３π／４ｒａｄ，５π／４ｒａｄ，７π／４ｒａｄが含まれるためである。 In addition, if ω is selected so as to satisfy the relationship shown in (Equation 12), not only the differential detection calculation units 103 and 104 but also a filtering device (complex filter) used for the partial band extraction unit 102 can be easily realized. can do.

Because, when the relationship between k and z is expressed as (Equation 12), the set of phase rotation components θ to be multiplied by the tap coefficient hd is expressed by (Equation 11) as either the in-phase component or the quadrature component. Π / 4 rad, 3π / 4 rad, 5π / 4 rad, 7π /, which include 0 rad, π / 2 rad, π rad, and 3π / 2 rad for setting either one to 0, and in which the absolute values of the in-phase component and the quadrature component have the same value. This is because 4 rad is included.

First, note that 0 rad, π / 2 rad, π rad, and 3π / 2 rad are included in the phase rotation component θ. When the phase rotation component θ to be multiplied with the tap coefficient hd is equal to 0 rad, π / 2 rad, π rad, 3π / 2 rad, the in-phase component or quadrature component of the tap coefficient obtained as a result of the multiplication becomes 0, and the tap coefficient multiplier 903 Can be reduced.

Next, note that the phase rotation component θ includes π / 4 rad, 3π / 4 rad, 5π / 4 rad, and 7π / 4 rad. When the phase rotation component θ to be multiplied by the tap coefficient hd is equal to π / 4 rad, 3π / 4 rad, 5π / 4 rad, 7π / 4 rad, the absolute values of the in-phase component and the quadrature component of the tap coefficients obtained as a result of the multiplication are equal. , Can be used in common, and the tap coefficient multiplier 903 can be reduced.

The above description will be described using mathematical expressions. FIG. 18 is a diagram illustrating an impulse response waveform of the complex filter. For example, a low-pass filter in which a complex filter is expressed in a baseband band is an FIR filter having 20 taps (u = 20), and its impulse response waveform is a symmetric waveform as shown in FIG. Then, the transfer function HL (nT) of the complex filter is generally represented by (Expression 13) using the Z-transform.

ここで、Ｈｂ（ｎＴ）は、（式９）および（式１０）に示された複素フィルタの伝達関数Ｈｂ（ｎＴ）の一つの例である。また、（式１４）中のＲｅ｛Ｈｂ（ｎＴ）｝は、伝達関数の同相成分を表す。また、（式１５）中のＩｍ｛Ｈｂ（ｎＴ）｝は、伝達関数の直交成分を表す。 FIG. 19 is a diagram illustrating, on a complex plane, a set of phase rotation components θ to be multiplied by each tap coefficient satisfying the relationship of (Equation 12). In (Equation 13), the phase rotation component θ is multiplied by the phase rotation component θ = 1 + j0 and the phase rotation component θ is converted to each tap coefficient hd so that the subband complex signal S2 (nT) is extracted. Is multiplied by (Expression 13), the expression is expressed as (Expression 14) and (Expression 15) when divided into an in-phase component and a quadrature component.

Here, Hb (nT) is one example of the transfer function Hb (nT) of the complex filter shown in (Equation 9) and (Equation 10). Re {Hb (nT)} in (Equation 14) represents an in-phase component of the transfer function. Im {Hb (nT)} in (Equation 15) represents an orthogonal component of the transfer function.

Focusing on (Equation 14), it can be seen that there are no terms of h4 and h8. This is because the coefficient becomes 0 as a result of multiplying π / 2 rad and 3π / 2 rad as the phase rotation component θ. Focusing on (Equation 15), it can be seen that there are no terms of h2, h6, and h10. This is because the coefficient becomes 0 as a result of multiplying 0 rad and π rad as the phase rotation component θ. Further, in (Equation 14) and (Equation 15), focusing on the values of the tap coefficients excluding the sign, h1, h3, h5, h7, and h9 are calculated for the in-phase component and the quadrature component of the transfer function Hb (nT). It can be seen that the included five coefficients are common. This is due to the fact that the phase rotation component θ is arranged so as to include a value that is an integral multiple of π / 4 when the relationship shown in (Equation 12) is satisfied.

As described above, ωkT = 2πz (where z is an integer; z = ..., -1, 0, 1, ...), that is, the center frequency of the partial band to be extracted is an integer multiple of the symbol frequency, Further, by setting the number of samples within one symbol period to be a multiple of 8 obtained by dividing the center frequency of the sub-band to be extracted by the symbol frequency, the tap of the complex filter constituting the sub-band extraction unit can be reduced. The number can be small. Therefore, it is possible to realize the partial band extracting units shown in the fourth and fifth embodiments with a simpler configuration.

In addition, since the tap coefficients of the complex filter for extracting a pair of partial bands have a complex conjugate relationship with each other, when extracting a plurality of partial bands, a pair of partial bands that are equidistant from the frequency 0 are regarded as a pair. By extracting an even number of partial bands, in addition to the above two effects, there is an effect that tap coefficients can be shared between filters for extracting the respective partial bands.

(Specific explanation of effects)
Hereinafter, the above-described effect will be specifically described by taking, as an example, a case where the partial band extracting unit 102 shown in the first or second embodiment extracts two partial bands.

Now, the number of samples per symbol k = 16, the symbol frequency Fs of the signal to be transmitted is set to 0.5 MHz, and the center frequencies of the two sub-bands to be extracted are set at positions separated by 1 MHz from the frequency 0. And That is, kT = 1 / Fs = 2 MHz and Fb = 1 MHz or -1 MHz. From (Equation 11), the phase rotation component θ to be multiplied by the tap coefficient hd (where d = 0, 1, 2,..., U) is π / 4 rad. Further, from Fb / Fs = z, α in (Equation 12) is 1. From the above, it can be seen that the above setting satisfies the two conditions of ωkT = 2πz (z is an integer) and (Equation 12).

The value of π / 4 rad obtained by (Equation 11) is obtained by dividing the eight values shown on the complex plane in FIG. 19 counterclockwise or clockwise by the phase rotation component θ every sample period T. It means to go forward one by one. As can be seen from FIG. 19, since the phase rotation component θ takes values of 0 rad, π / 2 rad, π rad, and 3π / 2 rad, the in-phase component or quadrature component of the tap coefficient becomes 0 in the phase rotation component, and The number of multipliers can be reduced. Further, since the phase rotation component θ takes values of π / 4 rad, 3π / 4 rad, 5π / 4 rad, and 7π / 4 rad, the in-phase component and the quadrature component of the tap coefficient have the same absolute value in the phase rotation component. Since the tap coefficient multiplier can be shared, the number of tap coefficient multipliers can be reduced.

From the above, when ωkT = 2πz (where z is an integer; z =... -1, 0, 1,...) And ω satisfying the relationship shown in (Equation 12) are selected, the tap coefficient It can be seen that the number of multipliers can be reduced, and not only the realization of the differential detection operation unit but also the partial band extraction unit can be easily realized.

(Sixth embodiment)
FIG. 20 is a schematic diagram of a wireless communication system using the data receiving device according to the one embodiment of the present invention. 20, the wireless communication system includes i (where i is a positive integer) base stations (first base station 2500, second base station 2501,..., I−1 base station 2502, i th base station). Base station 2503) and a mobile station 2504. The mobile station 2504 is a wireless communication device using the data receiving device according to the one embodiment of the present invention. Hereinafter, the mobile station 2504 will be described as using the data receiving device 1 according to the first embodiment as a data receiving device. Good. Note that there may be a plurality of mobile stations. Hereinafter, the operation of the wireless communication system shown in FIG. 20 will be described with reference to FIG. 1 and FIG.

FIG. 21 is a diagram schematically showing a spectrum of a high-frequency modulated signal used in the wireless communication system shown in FIG. In FIG. 21, spectrum r ₁ (t) indicates the spectrum of the phase-modulated high-frequency modulated signal output from first base station 2500. The spectrum r ₂ (t) indicates the spectrum of the phase-modulated high-frequency modulated signal output from the second base station 2501. The spectrum ri _-1 (t) indicates the spectrum of the phase-modulated high-frequency modulated signal output from the ( _i-1 ) th base station 2502. The spectrum r _i (t) indicates the spectrum of the phase-modulated high-frequency modulated signal output from the i-th base station 2503.

As described in the first embodiment, the high-frequency modulated signal may include two or more partial band high-frequency modulated signals. Therefore, the data receiving apparatus of the present invention can extract at least one partial band, that is, m (where m is a positive integer of 1 or more and i or less) i. In the following, for simplicity, it is assumed that m = 2, that is, a data receiving apparatus incorporating a partial band extracting unit for extracting two partial bands is used in the mobile station 2504.

Here, the mobile station 2504 selects the high-frequency modulated signal output from the first base station 2500 and the high-frequency modulated signal output from the second base station 2501 out of the i spectra shown in FIG. Assume that one wants to receive a modulated signal. A high-frequency modulated signal having, as a frequency component, a virtual spectrum R (t) including all bands from the spectrums r ₁ (t) to r _i (t) is input to the frequency conversion circuit 105 shown in FIG. Is done. In such a situation, the frequency conversion circuit 105 generates a high-frequency modulated signal having a frequency component of a virtual spectrum r (t) having a center frequency f _i including the spectrum r ₁ (t) and the spectrum r ₂ (t). Is regarded as a high-frequency modulated signal to be received. Then, the frequency conversion circuit 105, the center frequency f _i is such that the frequency 0, frequency conversion of the virtual spectrum r (t). That is, the frequency conversion circuit 105 determines that the spectrum r ₁ (t) becomes the spectrum 2601, the spectrum r ₂ (t) becomes the spectrum 2602, the spectrum r _i-1 (t) becomes the spectrum 2603, and the spectrum r _i (t) becomes Frequency conversion is performed so that the spectrum becomes a spectrum 2604 and the virtual spectrum r (t) becomes the virtual spectrum 2600. As a result, as in the first embodiment, the data receiving apparatus 1 in the mobile station 2504 outputs the in-phase component data of the in-phase component and the quadrature component of the complex baseband signal having only the spectrum 2601 as the frequency component. Sequence BI ₁ (nT) and partial band detection signal quadrature component data sequence BQ ₁ (nT), and partial band detection signal in-phase component data sequence which is an in-phase component and a quadrature component of a complex baseband signal having only spectrum 2602 as a frequency component BI ₂ (nT) and a partial band detection signal orthogonal component data sequence BQ ₂ (nT) are output.

A determination circuit (not shown) is independently connected to the output side of each of the first delay detection calculation section 103 and the second delay detection calculation section 104. A determination circuit (not shown) provided on the output side of the first differential detection operation unit 103 includes a partial band detection signal in-phase component data sequence BI ₁ (nT) output from the first differential detection operation unit 103 and a partial Phase determination is performed based on the band detection signal orthogonal component data sequence BI ₂ (nT), and a received data sequence is output. The determination circuit (not shown) provided on the output side of the second differential detection operation unit 104 includes a partial band detection signal in-phase component data sequence BI ₂ (nT) output from the second differential detection operation unit 104 and a partial Phase determination is performed based on the band detection signal orthogonal component data sequence BQ ₂ (nT), and a received data sequence is output. In other words, the mobile station 2504 can simultaneously receive data from the first and second base stations 2500 and 2501 by using the data receiving device 1 without preparing a plurality of receiving systems as in the related art. Can be.

{Conventional receivers require i reception systems to receive i independent high-frequency modulated signals and obtain respective reception data. However, as described above, the mobile station, which is the wireless communication apparatus of the present invention, can simultaneously obtain received data from i independent high-frequency modulated signals using only one receiving system.

Note that in order for the mobile station to extract m partial bands, the mobile station uses a data receiving device in which a partial band extraction unit that extracts m partial bands is incorporated.

Note that the first to i-th base stations 2500 to 2503 may have a function as a mobile station, and the mobile station 2504 may have a function as a base station. In this case, mobile station 2504 as a base station can simultaneously receive data from base stations 2500 and 2501 as mobile stations.

When a mobile station using the data receiving apparatus of the present invention receives m high-frequency modulated signals at the same time as described above, the speed is m times faster than when communication is performed using only one band. Can be performed.

As described in the first embodiment, it is preferable that the data receiving device of the mobile station selects one appropriate data from the m pieces of received data according to the reception level and outputs the selected data. Thus, in the case where one high-frequency modulated signal is output from one base station, when the mobile station moves between the areas of m base stations, the mobile station selects one appropriate base station. You can communicate while selecting.

(Seventh embodiment)
FIGS. 22 and 23 are block diagrams showing configuration examples of the wireless communication devices 10 and 20 according to the seventh embodiment of the present invention using the data receiving device according to the embodiment of the present invention.
First, the operation of the wireless communication device 10 will be described with reference to FIGS. 22, the wireless communication device 10 includes a frequency conversion circuit 2700, a data reception device 2701 according to the embodiment of the present invention, first to i-th determination circuits 2703, a reception data integration circuit 2704, an antenna 2705, a transmission circuit 2706, and a transmission / reception switch 2707. The wireless communication device 10 is a virtual high-frequency modulated signal including the spectrums r ₁ (t), r ₂ (t),..., R _i (t) (where i is a positive integer) shown in FIG. Receive R (t).

The frequency conversion circuit 2700 performs frequency conversion so that the center frequency f _i of the virtual high-frequency modulated signal R (t) becomes zero. Partial band extracting section of the data receiving apparatus 2701, the spectrum r ₁ included in the virtual high-frequency modulated signal R (t) (t), r 2 (t), ..., to extract each band of r _i (t) . Each differential detection operation unit of data receiving apparatus 2701 outputs a partial band detection signal quadrature component data sequence and an in-phase component data sequence corresponding to each band extracted by the partial band extraction unit. The first to i-th determination circuits 2703 output data D1 to Di based on the input partial-band detection signal quadrature component data sequence and in-phase component data sequence, respectively.

Now, it is assumed that the transmission / reception switch 2707 is set so that the antenna 2705 and the reception circuit are connected. In this case, the first to i-th determination circuits 2703 of the reception circuit respectively output reception data Dk corresponding to a high-frequency modulated signal having a spectrum r _k (t) as a frequency component (k = 1,..., i).

Here, a transmitter (not shown) for transmitting a signal to the wireless communication apparatus 10 divides the transmission data TXD into i pieces of transmission data TXD ₁ to TXD _i in advance, and transmits each divided transmission data TXD the _k, assume each transmit a spectrum r _k (t) as a high frequency modulated signal to frequency components. That is, the received data Dk is the one whose divided transmitted data TXD _k on the transmitting side.

The received data integration circuit 2704 combines the received data D1 to Di into one, generates the transmission data TXD before being divided, and outputs it as the received data.

As described above, when the data receiving apparatus of the present invention is incorporated in a wireless communication apparatus, data reception processing can be performed at a speed i times faster than in the case where communication is performed using only the band represented by spectrum r _i (t). Can be.

Next, the operation of the wireless communication device 20 will be described with reference to FIGS. In FIG. 23, parts having the same functions as those of the wireless communication apparatus shown in FIG. 22 are denoted by the same reference numerals. The wireless communication device 20 includes a frequency conversion circuit 2700, a data reception device 2701 according to the embodiment of the present invention, first to i-th determination circuits 2703, a display 2804, an antenna 2705, and a transmission circuit 2706. And a transmission / reception switch 2707. The wireless communication device 20 receives the virtual high-frequency modulated signal R (t) including the spectrums r ₁ (t), r ₂ (t),..., R _i (t) (where i is a positive integer) as frequency components. I do. The wireless communication device 20 obtains the reception data Dk corresponding to the high-frequency modulated signal having the spectrum r _k (t) as a frequency component, similarly to the wireless communication device 10. The display 2804 in the wireless communication device 20 displays the content of the received data independently according to the obtained i received data Dk (k = 1,..., I).

As described above, if the data receiving apparatus of the present invention is incorporated in a wireless communication apparatus, a plurality of signal processings are performed simultaneously by simply preparing one receiving system, and the obtained received data is independently processed in parallel. , Can be displayed.

From the above, if the data receiving apparatus of the present invention is used for a wireless communication apparatus, it is possible to increase the data transmission speed and to perform parallel processing of received data simply by preparing one receiving system.

The data receiving apparatus according to the present invention reduces the time required to extract a plurality of partial band signals, and does not require a plurality of analog circuits having the same characteristics. It is useful as a device used for a wireless communication device or the like.

FIG. 1 is a diagram showing a configuration of a data receiving device 1 according to a first embodiment of the present invention. FIG. 4 is a signal spectrum diagram schematically illustrating how to obtain in-phase component I (t) and quadrature component Q (t) of a complex baseband signal from a high-frequency signal input to frequency conversion circuit 105. FIG. 2 is a diagram showing a configuration of the first delay detection calculation unit 103 or the second delay detection calculation unit 104 in FIG. Diagram showing an example of a signal obtained by performing spectrum spreading using a chirp signal as a spread modulation signal The figure which shows the structure of the 1st or 2nd differential detection calculation parts 103 and 104 in case a phase rotator is provided. The figure which shows the structure of the data receiving apparatus 1 in case the orthogonal transformer is provided. FIG. 2 is a diagram illustrating a configuration of a data receiving device 2 according to a second embodiment of the present invention. FIG. 4 is a signal spectrum diagram schematically illustrating how to obtain in-phase component I (t) and quadrature component Q (t) of a complex baseband signal from a high-frequency signal input to frequency conversion circuit 505. FIG. 14 is a diagram illustrating a configuration of a partial band extraction unit according to the third embodiment. The figure which shows the structure of the partial band extraction part which concerns on 4th Embodiment. Timing chart showing the operation of the first input selector 2101 or the second input selector 2102 A timing chart showing the operation of the first output selector 2105 or the second output selector 2106 Timing chart of signals output from first input selector 2101 or second input selector 2102 Timing chart of signals output from first output selector 2105 or second output selector 2106 The figure which shows the general structure of the complex filter used for the filtering device in the partial band extraction part which concerns on 3rd and 4th embodiment. Complex plan view for explaining tap coefficients of complex filter Schematic diagram showing the passband characteristics of the complex filter used in the subband extraction unit in the baseband band Diagram showing impulse response waveform of complex filter Diagram showing a set of phase rotation components θ to be multiplied by each tap coefficient satisfying the relationship of (Equation 12) on a complex plane. Schematic diagram of a wireless communication system using a data receiving device FIG. 20 is a diagram schematically illustrating a state of a spectrum of a high-frequency modulated signal used in the wireless communication system illustrated in FIG. 20. FIG. 14 is a block diagram illustrating a configuration example of wireless communication devices 10 and 20 according to a seventh embodiment of the present invention using a data receiving device according to an embodiment of the present invention. FIG. 14 is a block diagram illustrating a configuration example of wireless communication devices 10 and 20 according to a seventh embodiment of the present invention using a data receiving device according to an embodiment of the present invention. FIG. 9 is a diagram schematically showing a spectrum of a received signal for explaining operations of the wireless communication devices 10 and 20 according to the seventh embodiment. FIG. 1 shows a configuration of a data receiving apparatus described in Japanese Patent No. 3161146. FIG. 25 is a view showing a spectrum of a signal in a main part of the data receiving apparatus shown in FIG. "SR-chirp scheme spread spectrum wireless modem" is a block diagram schematically showing a configuration of a receiver in a wireless modem described in IEICE Technical Report RCS95-102. The figure which shows an example of a structure of the delay detection apparatus provided inside the baseband signal processing part 1512. The figure which shows the structure of the differential detection calculation part 1103

Explanation of reference numerals

1, 2, 2701 Data receiving device 10, 20 Wireless communication device 100, 500 First sampler 101, 501 Second sampler 102, 502 Partial band extraction unit 103 First delay detection operation unit 503 Delay detection Operation unit 104 Second delay detection operation units 105, 505, 2700 Frequency conversion circuits 106, 107 Quadrature converters 302, 402, 900 Delay units 304, 404 First multipliers 305, 405 Second multipliers 308, 408 First low-pass filter 309, 409 Second low-pass filter 412 Phase rotator 1701, 103 First filtering device 1702, 2104 Second filtering device 1703 Third filtering device 1704 Fourth filtering device 1705 , 2107 First subtractor 1706, 2108 First adder 170 7, 2109 Second subtractor 1708, 2110 Second adder 2101 First input selector 2102 Second input selector 2105 First output selector 2106 Second output selector 2 First delay 2112 second delay unit 903 tap coefficient multiplier 906 adder 2500 to 2503 base station 2504 mobile station 2703 decision circuit 2704 data integration circuit 2705 antenna 2706 transmission circuit 2707 transmission / reception switch 2804 display

Claims (20)

A data receiving apparatus (1) for outputting a detection signal using an in-phase signal and a quadrature signal obtained by performing quadrature detection after frequency-converting a modulated wave signal subjected to phase modulation as an input signal,
A first sampler (100) that samples the in-phase signal at a fixed sampling period and outputs the sampled in-phase signal;
A second sampler (101) that samples the quadrature signal at the fixed sample period and outputs the quadrature signal as a sampled quadrature signal;
At least one of frequency components included in the sampled in-phase signal output from the first sampler and the sampled quadrature signal output from the second sampler, which is configured by a complex filter, A sub-band extracting unit (102) for extracting a sub-band and outputting it as a sub-band signal;
A data receiving apparatus comprising: a delay detection operation unit (103, 104) that performs delay detection based on a partial band signal output by the partial band extraction unit and outputs a detection signal. The said partial band extraction part extracts at least 1 signal whose center frequency is not 0 as the said partial band signal to extract, It divides into an in-phase component and a quadrature component, and outputs it, The Claim 1 characterized by the above-mentioned. The data receiving device as described in the above. The method according to claim 2, wherein the partial band extracting unit extracts the partial band signal such that a center frequency of the partial band signal is an integral multiple of a symbol frequency of data being transmitted. Data receiver. The differential detection calculation unit,
A delay unit (302) for delaying the in-phase component of the partial band signal output from the partial band extraction unit by one symbol time and outputting the delayed signal;
A first multiplier (304) that multiplies the in-phase component of the partial band signal output by the partial band extraction unit and the output of the delay unit and outputs the result as an in-phase component data sequence;
A second multiplier (305) that multiplies the orthogonal component of the partial band signal output by the partial band extracting unit with the output of the delay unit and outputs the result as an orthogonal component data sequence;
A first low-pass filter (308) that removes and outputs high-frequency components of the in-phase component data string output from the first multiplier;
The data receiving apparatus according to claim 3, further comprising a second low-pass filter (309) that removes a high-frequency component of the orthogonal component data string output from the second multiplier and outputs the result. The partial band extracting unit extracts the partial band signal such that the number of samples in one symbol period is a multiple of 8 obtained by dividing the center frequency of the partial band signal to be extracted by the symbol frequency. The data receiving apparatus according to claim 3, wherein The partial band extracting unit extracts an even number of partial band signals,
3. The data receiving device according to claim 2, wherein the partial band signals are paired with positive and negative frequencies at the same distance from the frequency 0 as center frequencies. The partial band extraction unit,
A first filtering device (1701), which is a complex filter and calculates and outputs a convolution integral of the sampled in-phase signal and an in-phase component of a transfer function of the complex filter;
A second filtering device (1702) for calculating a convolution integral of the sampled orthogonal signal and an orthogonal component of a transfer function of the complex filter;
A third filtering device (1703) for obtaining a convolution integral of the sampled quadrature signal and an in-phase component of a transfer function of the complex filter;
A fourth filtering device (1704) for calculating a convolution integral of the sampled in-phase signal and a quadrature component of a transfer function of the complex filter;
A first subtractor (1705) for subtracting a signal output by the second filtering device from a signal output by the first filtering device;
A first adder (1706) for adding a signal output from the first filtering device and a signal output from the second filtering device;
A second subtractor (1707) for subtracting a signal output by the fourth filtering device from a signal output by the third filtering device;
The data receiving device according to claim 6, further comprising a second adder (1708) for adding a signal output from the third filtering device and a signal output from the fourth filtering device. 9. The partial band signal according to claim 7, wherein the partial band extracting unit extracts the partial band signal such that a center frequency of the partial band signal is an integral multiple of a symbol frequency of transmitted data. Data receiver. The partial band extracting unit extracts the partial band signal such that the number of samples in one symbol period is a multiple of 8 obtained by dividing the center frequency of the partial band signal to be extracted by the symbol frequency. The data receiving apparatus according to claim 7, wherein The partial band extraction unit,
A first input selection for alternately selecting and outputting the sampled in-phase signal and the sampled quadrature signal every half a sample period using the sampled in-phase signal and the sampled quadrature signal as input signals; Vessel (2101),
A second input selection for alternately selecting and outputting the sampled in-phase signal and the sampled quadrature signal every half a sample period using the sampled in-phase signal and the sampled quadrature signal as input signals; Vessel (2102);
A first filtering device (2103) for performing convolution integration of a signal output from the first input selector and an in-phase component of a transfer function of the complex filter;
A second filtering device (2104) for performing convolution integration of a signal output from the second input selector and an orthogonal component of a transfer function of the complex filter;
A first output selector that alternately outputs an output signal from the first filtering device that changes in a half cycle of a sampling cycle to a first output terminal and a second output terminal in a half cycle of a sampling cycle (2105),
A second output selector that alternately outputs an output signal from the second filtering device that changes in a half cycle of the sampling cycle to a third output terminal and a fourth output terminal in a half cycle of the sampling cycle (2106),
A first delay unit (2) for delaying a signal output from a first output terminal of the first output selector by half a sample period;
A second delay unit (2112) for delaying a signal output from a third output terminal of the second output selector by half a sample period;
A first subtractor (2107) for subtracting a signal output from the second delay device from a signal output from the first delay device;
A first adder (2108) for adding a signal output from the first delay unit and a signal output from the second delay unit;
A second subtractor (2109) for subtracting a signal output from a fourth output terminal of the second output selector from a signal output from a second output terminal of the first output selector;
A second adder (2110) for adding a signal output from a second output terminal of the first output selector and a signal output from a fourth output terminal of the second output selector; The data receiving device according to claim 6, comprising: The partial band extractor according to claim 10, wherein the partial band extractor extracts the partial band signal such that a center frequency of the partial band signal is an integral multiple of a symbol frequency of transmitted data. Data receiver. The partial band extracting unit extracts the partial band signal such that the number of samples in one symbol period is a multiple of 8 obtained by dividing the center frequency of the partial band signal to be extracted by the symbol frequency. The data receiving apparatus according to claim 10, wherein 3. The data receiving apparatus according to claim 2, wherein the delay detection operation unit performs delay detection using a partial band signal output from the partial band extraction unit as an intermediate frequency signal. The data receiving apparatus according to claim 1, wherein the modulated signal is a signal from which a demodulated partial band signal is obtained by extracting at least one partial band from a frequency band of the modulated signal. 2. The data receiving apparatus according to claim 1, wherein the modulated signal is a signal subjected to spread spectrum. 14. The data receiving apparatus according to claim 13, wherein the modulated signal is a spread spectrum signal using, as a spread signal, a chirp signal obtained by repeatedly sweeping the frequency of a sine wave at regular intervals. . A wireless communication device (10, 20) for receiving and processing a modulated wave signal subjected to phase modulation,
A frequency conversion circuit (2700) for performing quadrature detection after frequency conversion of the received modulated wave signal and outputting an in-phase signal and a quadrature signal;
A data receiving device (2701) that outputs a detection signal using the in-phase signal and the quadrature signal output from the frequency conversion circuit as input signals;
A phase determination processing device (2703, 2704, 2804) for determining and processing the phase of the detection signal output by the data receiving device;
The data receiving device,
A first sampler (100) that samples the in-phase signal at a fixed sampling period and outputs the sampled in-phase signal;
A second sampler (101) that samples the quadrature signal at the fixed sample period and outputs the quadrature signal as a sampled quadrature signal;
At least one of frequency components included in the sampled in-phase signal output from the first sampler and the sampled quadrature signal output from the second sampler, which is configured by a complex filter, A sub-band extracting unit (102) for extracting a sub-band and outputting it as a sub-band signal;
A wireless communication apparatus comprising: a delay detection operation unit (103, 104) that performs delay detection based on a partial band signal output by the partial band extraction unit and outputs a detection signal. The partial band extracting unit extracts a plurality of partial bands and outputs the extracted partial bands as a partial band signal,
18. The phase determination processing device according to claim 17, wherein the phase determination processing device selects and processes one of a plurality of data obtained by performing phase determination on the plurality of detection signals from the delay detection calculation unit. Wireless communication device. The partial band extracting unit extracts a plurality of partial bands and outputs the extracted partial bands as a partial band signal,
The phase determination processing device (2704) generates reception data based on a plurality of data obtained by performing a phase determination on a plurality of detection signals from the differential detection calculation unit. Wireless communication device. The partial band extracting unit extracts a plurality of partial bands and outputs the extracted partial bands as a partial band signal,
The wireless communication apparatus according to claim 17, wherein the phase determination processing device (2804) performs parallel processing on data obtained by determining the phases of the plurality of detection signals from the differential detection calculation unit.

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