JP3643109B2 - Data receiving device - Google Patents

Description

  The present invention relates to a data receiving apparatus for demodulating a modulated signal, and more particularly to a data receiving apparatus for obtaining a detection signal from a phase-modulated modulated signal by digital signal processing.

  Conventionally, as a device for extracting and demodulating at least one partial band signal from a received modulated signal, a data transmitting / receiving device described in Patent Document 1 and a device described in Non-Patent Document 1 have been known. .

  FIG. 25 is a diagram illustrating a configuration of a data receiving device described in Patent Document 1. In FIG. 25, the data receiving apparatus includes a frequency mixer 1301, a band pass filter (referred to as BPF in the drawing) 1302, a local oscillator 1303, a reception state determination unit 1304, a delay unit 1305, and a multiplier 1306. , A low-pass filter (denoted as LPF in the drawing) 1307 and a decoder 1308.

  The local oscillator 1303 outputs a local oscillation signal whose frequency can be changed at intervals of an integer multiple of the symbol frequency of the data to be received. The frequency mixer 1301 converts the input spread spectrum signal r (t) into a frequency band that is a difference from the local oscillation signal from the local oscillator 1303 and outputs it. Here, it is assumed that the spread spectrum signal r (t) is a phase-modulated signal that can be demodulated by extracting at least one partial band from the frequency band that it has.

  The band pass filter 1302 extracts and outputs an intermediate signal b (t) that is a part of the frequency component of the spread spectrum signal r (t) frequency-converted by the frequency mixer 1301.

  FIG. 26 is a diagram showing a spectrum of a signal in the main part of the data receiving apparatus shown in FIG. FIG. 26 (a) is a schematic diagram of the spectrum of the received spread spectrum signal r (t). There are three frequencies of the local oscillation signal output from the local oscillator 1303. The frequency of each local oscillation signal is an integral multiple of the symbol frequency of the data to be received. The center frequency of each local oscillation signal is the center frequency of one of the partial bands indicated by B1, B2, and B3.

  FIG. 26B is a schematic diagram of the spectrum of the intermediate signal b (t). The intermediate signal b (t) is a signal of any one of the partial bands B1, B2, and B3 obtained as a result of frequency conversion of r (t) and band limitation.

  The reception state determination unit 1304 outputs a band switching signal according to the data reception state, and switches the frequency of the local oscillation signal output from the local oscillator 1303. The local oscillator 1303 switches the frequency of the local oscillation signal to be output based on the band switching signal output from the reception state determination unit 1304. As a result, any one of the partial bands B1, B2, and B3 is selected, and the band pass filter 1302 outputs an intermediate signal b (t) corresponding to the partial band.

  The multiplier 1306 multiplies the intermediate signal b (t) by the intermediate signal b (t−Ts) obtained by delaying the intermediate signal b (t) by the delay unit 1305 by the symbol period Ts, and outputs the output signal to the low frequency band. Input to the pass filter 1307. The low-pass filter 1307 performs low-pass filtering of the input signal and outputs a detection signal c (t). The decoder 1308 determines the polarity of the detection signal c (t) and outputs data dat (t).

  FIG. 27 is a block diagram showing an outline of the configuration of the receiver in the wireless modem described in Non-Patent Document 1. In FIG. 27, the receiver includes a duplexer 1501, a first frequency mixer 1502, a second frequency mixer 1503, a first local oscillator 1504, a second local oscillator 1505, A band-pass filter 1506, a second band-pass filter 1507, a first gain controller (denoted as AGC1 in the figure) 1508, a second gain controller (denoted as AGC2 in the figure) 1509, A first quadrature detector 1510, a second quadrature detector 1511, and a baseband signal processing unit 1512 are provided.

  This receiver uses a spread spectrum signal as an input signal, extracts two partial bands at the same time, and outputs received data according to the reception situation. This receiver has two reception systems having the same configuration from the first frequency mixer 1502 to the baseband signal processing unit 1512 and from the second frequency mixer 1503 to the baseband signal processing unit 1512. The operation of the receiver shown in FIG. 27 will be described below.

  The demultiplexer 1501 demultiplexes the received spread spectrum signal r (t) into two signals, and inputs them to the first frequency mixer 1502 and the second frequency mixer 1503, respectively. The first local oscillator 1504 and the second local oscillator 1505 each output a local oscillation signal having a center frequency in a band having different band characteristics. A local oscillation signal output from the local oscillator 1504 is input to the frequency mixer 1502. A local oscillation signal output from the local oscillator 1505 is input to the frequency mixer 1503.

  The frequency mixer 1502 converts the demultiplexed spread spectrum signal r (t) into a signal in a frequency band that is the difference from the local oscillation signal output from the local oscillator 1504 and inputs the signal to the first band pass filter 1506. To do. The first band pass filter 1506 extracts a part of the partial band signal from the input signal and inputs the partial band signal to the first gain controller 1508 as the partial band signal b1 (t). The first gain controller 1508 controls the amplitude of the partial band signal b 1 (t) and inputs the signal to the first quadrature detector 1510. The first quadrature detector 1510 outputs I1 (t), which is the in-phase component of the complex baseband signal from the first gain controller 1508, and Q1 (t), which is the quadrature component.

  The other receiving system below the second frequency mixer 1503 also operates in the same manner, and the second quadrature detector 1511 is I2 (I2 (the in-phase component of the complex baseband signal from the second gain controller 1509). t) and quadrature component Q2 (t) are output. The baseband signal processing unit 1512 performs delay detection processing with the complex baseband signals I1 (t) and Q1 (t), and I2 (t) and Q2 (t) as a set, for example, each system. The reception data of the receiving system that has been determined to have fewer errors is output according to the reception status of. In addition to the above method, a method of selecting a system using the reception level and obtaining received data may be used.

  FIG. 28 is a diagram illustrating an example of a configuration of a delay detection apparatus provided in the baseband signal processing unit 1512. In the baseband signal processing unit 1512, one delay detector is provided for each quadrature detector. In FIG. 28, only one delay detection device is shown as a representative. In FIG. 28, the delay detection apparatus includes a first sampler 1101, a second sampler 1102, a delay detection calculation unit 1103, a first post-detection filter 1104, and a second post-detection filter 1105. Including.

  The first sampler 1101 samples (samples) the in-phase component i (t) (I1 (t) or I2 (t) in FIG. 27) of the complex baseband signal to obtain the sampled baseband signal in-phase component. The data string I (nT) is output and input to the delay detection calculation unit 1103. Here, n is an integer (n =... -1, 0, 1,...), And T is a sampling period. Similarly, the second sampler 1102 samples the quadrature component q (t) (Q1 (t) or Q2 (t) in FIG. 27) of the complex baseband signal, and samples the baseband signal quadrature component data. The column Q (nT) is output and input to the delay detection calculation unit 1103.

  FIG. 29 is a diagram illustrating a configuration of the delay detection calculation unit 1103. In FIG. 29, the delay detection calculation unit 1103 includes a first selector 1201, a second selector 1202, a delay device 1203, a sign inverter 1204, a first multiplier 1205, and a second multiplier 1206. And have. The first selector 1201 alternately selects the data bases I (nT) and Q (nT) of the sampled baseband signal every sample period T and outputs it as S1 (nT). The second selector 1202 alternates the signals -I (nT) and Q (nT) obtained by inverting the sign of the sampled baseband signal in-phase component data sequence I (nT) output from the sign inverter 1204 every sample period T. And output as S2 (nT).

  While the first selector 1201 selects I (nT), the second selector 1202 is set to select Q (nT). Further, while the first selector 1201 selects Q (nT), the second selector 1202 is set to select -I (nT).

  Delay device 1203 uses S1 (nT) as an input signal and outputs a signal obtained by delaying S1 (nT) by one symbol time length kT. Here, k is the number of samples per symbol. Thus, the first multiplier 1205 uses, as F1 (nT), I (nT) I {(n−k) T}, which is the product of the sampled baseband signal in-phase component data sequence, for each sample period T. Q (nT) Q {(n−k) T}, which is the product of the sampled baseband signal orthogonal component data strings, is alternately output. The second multiplier 1206 uses, as F2 (nT), the product of the sampled baseband signal in-phase component and the sampled baseband signal quadrature component I {(n−k) T} Q ( nT) and -I (nT) Q {(n-k) T} are output alternately.

  The first post-detection filter 1104 low-pass filters the input signal F1 (nT), and I (nT) I {(nk) T} and Q (nT) Q {(nk) T. } Is output as a signal D1 (nT) equivalent to the signal obtained by adding. Similarly, the second post-detection filter 1105 performs low-pass filtering on the input signal F2 (nT), and I {(n−k) T} Q (nT) and −I (nT) Q {(n -K) A signal D2 (nT) equivalent to the signal obtained by adding T} is output.

  D1 (nT) and D2 (nT) are complex numbers of A (nT) = I (nT) + jQ (nT), where I (nT) and Q (nT) are in-phase and quadrature components, respectively, where j is (Representing an imaginary unit) and a complex result of A {(n−k) T} delayed by one symbol time length kT from A (nT), corresponding to the in-phase component and the quadrature component of the multiplication result, respectively. ing. Accordingly, the phase represented by D1 (nT) and D2 (nT) represents the difference between the phase of A (nT) and the phase of A {(n−k) T}, and therefore a determination circuit (not shown). ) And the like can be demodulated using D1 (nT) and D2 (nT).

  In this way, in order to obtain a demodulated signal for a plurality of partial band signals, the receiver shown in FIG. 27 obtains a plurality of complex baseband signals different from each other from partial band signals having different frequency band characteristics. Each of the complex baseband signals is subjected to delay detection calculation to obtain a plurality of demodulated signals, and the received data is output according to the reception status.

In FIG. 27, two cases are shown as the partial bands to be extracted. However, when two or more partial bands are extracted, the baseband from the frequency mixer is proportional to the number of partial bands to be extracted. A reception system having the same configuration as described above is required up to the signal processing unit.
Japanese Patent No. 3161146 Japanese Patent Laid-Open No. 9-200165 Yoshio Urabe and two others, “SR-chirp spread spectrum wireless modem”, IEICE Technical Report RCS95-102, The Institute of Electronics, Information and Communication Engineers, November 1995, p. 27-32 Hirohito Yamano and two others, “Batch Demodulation Method Using Band Division Filter Bank in Multi-Channel TDMA System”, IEICE General Conference, 1998, B-5-62, p. 426

  However, in the data transmission / reception apparatus described in Patent Document 1, when different partial band signals are extracted, the frequency of the local oscillator must be changed. However, there is a problem that this switching takes time.

  On the other hand, in the receiver described in Non-Patent Document 1, since a plurality of local oscillators are prepared in advance, it does not take time to switch the partial band signal to be extracted. It is necessary to prepare a plurality of analog reception systems having the same configuration, and in order to align the characteristics of the plurality of reception systems, there is a problem that the characteristics of each analog circuit must be substantially the same. . Further, since it is necessary to prepare a plurality of receiving systems, there is a problem that the hardware configuration becomes large.

  When attention is paid to the hardware configuration of the delay detection calculation unit 1103 in the baseband signal processing unit 1512 (see FIG. 29), a signal unnecessary for demodulation is previously included in the complex baseband signal that is the input signal. There is a problem that it must be removed using an analog circuit.

  Further, the delay detection calculation unit 1103 requires one sign inverter, two selectors, one delay device, and two multipliers. Furthermore, in the delay detection device, two detection signals are used. A post filter is required. Therefore, for example, there is a problem that the scale of the gate becomes large when the LSI is implemented, and it is not suitable for miniaturization and weight reduction.

  Therefore, an object of the present invention is to reduce the time required to extract a plurality of partial band signals for a data receiving apparatus that extracts a partial band signal from a received phase modulation signal and obtains a detection signal by delay detection. It is an object of the present invention to provide a data receiving apparatus that is easy to implement as an LSI and has a simple configuration without requiring a plurality of analog circuits with reduced characteristics.

  The present invention is a data receiving apparatus that outputs a detection signal using an in-phase signal and a quadrature signal obtained by performing quadrature detection after frequency-converting a phase-modulated modulated wave signal as input signals. The data receiving apparatus includes a first sampler, a second sampler, a partial band extraction unit, and a delay detection calculation unit. The first sampler samples the in-phase signal at fixed sample periods and outputs the sampled in-phase signal. The second sampler samples the quadrature signal at regular sample periods and outputs the sampled quadrature signal. The partial band extraction unit includes a complex filter, and includes at least one of frequency components included in the sampled in-phase signal output from the first sampler and the sampled quadrature signal output from the second sampler. One partial band is extracted and output as a partial band signal. The delay detection calculation unit performs delay detection based on the partial band signal output from the partial band extraction unit, and outputs a detection signal.

  Preferably, the partial band extraction unit extracts at least one signal whose center frequency is not 0 as a partial band signal to be extracted, and outputs the signal divided into an in-phase component and a quadrature component.

  The partial band extraction unit may extract the partial band signal so that the center frequency of the partial band signal is an integral multiple of the symbol frequency of the data being transmitted.

  Further, the partial band extraction unit may extract the partial band signal so that the number of samples in one symbol period is a multiple of 8 obtained by dividing the center frequency of the partial band signal to be extracted by the symbol frequency. .

  Further, the partial band extraction unit may extract an even number of partial band signals. These partial band signals are paired with a positive and negative frequency equidistant from the frequency 0 as a center frequency.

  Specifically, the delay detection calculation unit includes a delay unit, a first multiplier, a second multiplier, a first low-pass filter, and a second low-pass filter. The delay device delays the in-phase component of the partial band signal output from the partial band extraction unit by one symbol time and outputs the delayed signal. The first multiplier multiplies the in-phase component of the partial band signal output from the partial band extraction unit by the output of the delay unit, and outputs the result as an in-phase component data string. The second multiplier multiplies the orthogonal component of the partial band signal output from the partial band extraction unit by the output of the delay device, and outputs the result as an orthogonal component data string. The first low-pass filter removes a high-frequency component from the in-phase component data string output from the first multiplier and outputs the result. The second low-pass filter removes the high-frequency component of the orthogonal component data string output from the second multiplier and outputs the result.

  The partial band extraction unit includes a first filtering device, a second filtering device, a third filtering device, a fourth filtering device, a first subtractor, a first adder, A second subtracter and a second adder are included. The first filtering device is a complex filter, and obtains and outputs a convolution integral of the sampled in-phase signal and the in-phase component of the transfer function of the complex filter. The second filtering device is a complex filter, and obtains a convolution integral between the sampled orthogonal signal and the orthogonal component of the transfer function of the complex filter. The third filtering device is a complex filter, and obtains a convolution integral between the sampled quadrature signal and the in-phase component of the transfer function of the complex filter. The fourth filtering device is a complex filter, and obtains a convolution integral between the sampled in-phase signal and the orthogonal component of the transfer function of the complex filter. The first subtracter subtracts the signal output from the second filtering device from the signal output from the first filtering device. The first adder adds the signal output from the first filtering device and the signal output from the second filtering device. The second subtracter subtracts the signal output from the fourth filtering device from the signal output from the third filtering device. The second adder adds the signal output from the third filtering device and the signal output from the fourth filtering device.

  The partial band extraction unit includes a first input selector, a second input selector, a first filtering device, a second filtering device, a first output selector, and a second output. A selector, a first delayer, a second delayer, a first subtracter, a first adder, a second subtractor, and a second adder are included. The first input selector uses the sampled in-phase signal and the sampled quadrature signal as input signals, and alternately selects and outputs the sampled in-phase signal and the sampled quadrature signal every half the sample period. The second input selector uses the sampled in-phase signal and the sampled quadrature signal as input signals, and alternately selects and outputs the sampled in-phase signal and the sampled quadrature signal every half of the sample period. The first filtering device is a complex filter, and performs convolution integration between the signal output from the first input selector and the in-phase component of the complex filter. The second filtering device is a complex filter, and performs convolution integration of the signal output from the second input selector and the orthogonal component of the complex filter. The first output selector alternately outputs an output signal from the first filtering device that changes at a half period of the sampling period to the first output terminal and the second output terminal at a half period of the sampling period. To do. The second output selector alternately outputs an output signal from the second filtering device that changes at a half period of the sampling period to the third output terminal and the fourth output terminal at a half period of the sampling period. To do. The first delay device delays the signal output from the first output terminal of the first output selector by a half of the sample period. The second delay device delays the signal output from the third output terminal of the second output selector by a half time of the sample period. The first subtracter subtracts the signal output from the second delay unit from the signal output from the first delay unit. The first adder adds the signal output from the first delay device and the signal output from the second delay device. The second subtracter subtracts the signal output from the fourth output terminal of the second output selector from the signal output from the second output terminal of the first output selector. The second adder adds the signal output from the second output terminal of the first output selector and the signal output from the fourth output terminal of the second output selector.

  Preferably, the partial band extraction unit may extract the partial band signal so that the center frequency of the partial band signal is an integral multiple of the symbol frequency of the data being transmitted.

  Further, the partial band extraction unit may extract the partial band signal so that the number of samples in one symbol period is a multiple of 8 that is obtained by dividing the center frequency of the partial band signal to be extracted by the symbol frequency.

  Preferably, the delay detection calculation unit may perform delay detection using the partial band signal output from the partial band extraction unit as an intermediate frequency signal.

  Preferably, the modulated signal is a signal from which a subband signal that can be demodulated is obtained by extracting at least one subband from the frequency band of the modulated signal.

  Preferably, the modulated signal is a spectrum spread signal.

  Preferably, the modulated signal is a spread spectrum signal using a chirp signal obtained by repeatedly sweeping the frequency of a sine wave at regular intervals as a spread signal.

  In a preferred embodiment, the data receiving device is used for a wireless communication device. The wireless communication device may perform reception processing by selecting one of a plurality of received data obtained based on a plurality of partial bands, or obtain a single received data by integrating a plurality of received data Alternatively, a plurality of received data may be simultaneously processed in parallel.

  The data receiving apparatus of the present invention extracts a partial band signal in a partial band extraction unit constituted by a digital circuit, performs delay detection based on the partial band signal, and outputs a signal for obtaining a demodulated signal To do. That is, a partial band signal is extracted by digital processing. Therefore, it is possible to provide a data receiving apparatus that does not require an analog circuit corresponding to the number of partial band signals to be extracted as in the prior art and does not require time for switching of the partial band signals. Therefore, an increase in the hardware configuration can be suppressed. Further, since the signal other than the required partial band is removed in the partial band extraction unit, it is not necessary to remove unnecessary signals such as a jamming wave (a jamming wave due to interference) using an analog circuit.

  Since the partial band signal is an intermediate frequency signal whose center frequency is not 0, it is not necessary to perform vector calculation, and the delay detection calculation unit can be simplified.

  Delay detection to equalize the delay detection operation using complex baseband signals without generating unnecessary phase rotation components because the center frequency of the subband signal is an integral multiple of the symbol frequency of the data being transmitted. It is possible to simplify the calculation unit.

  The partial band extraction unit extracts the partial band signal so that the number of samples in one symbol period is a multiple of 8 that is obtained by dividing the center frequency of the partial band signal to be extracted by the symbol frequency, so that the tap coefficient is 0. Can be omitted, and in-phase and quadrature components of some tap coefficients can be shared, so that the tap coefficient multiplier of the complex filter constituting the partial band extraction unit Can be further reduced.

  The partial band extraction unit extracts an even number of partial band signals, and these partial band signals are paired with the positive and negative frequencies that are equidistant from frequency 0 as the center frequency. Since the convolution integral calculation can be shared in the configuration of the complex filter for extraction, the partial band extraction unit can be realized with a simple configuration.

  Since the delay detection calculation unit is realized by one delay unit, two multipliers, and two low-pass filters, it becomes possible to realize a delay detection calculation unit having a smaller hardware configuration compared to the conventional one. .

  Further, by making the partial band extraction unit as in the present invention, it becomes simple and unnecessary phase rotation components do not occur, and the delay detection calculation unit can be simplified.

  The delay detection calculation unit can use the phase rotation component of the intermediate frequency signal by performing delay detection using the partial band signal detected by the partial band extraction unit as an intermediate frequency signal. It can be configured easily.

  The modulated signal is a signal obtained from a subband signal that can be demodulated by extracting at least one partial band from the frequency band that it has, so that a subband signal that can be demodulated can be obtained from the modulated signal. It becomes easy.

  The use of a spread spectrum signal that is generally used is more effective in practical use.

  Use of a chirp signal obtained by repeatedly sweeping (sweeping) the frequency of a sine wave at regular intervals is effective in practical use.

(First embodiment)
FIG. 1 is a diagram showing a configuration of a data receiving apparatus 1 according to the first embodiment of the present invention. The data receiving apparatus 1 is an apparatus for extracting at least one partial band signal from a frequency component of a received phase modulation signal and obtaining a detection signal by delay detection. FIG. 1 shows a data receiving apparatus that extracts two partial bands. In FIG. 1, a data receiving apparatus 1 includes a first sampler 100, a second sampler 101, a partial band extraction unit 102, a first delay detection calculation unit 103, and a second delay detection. And an arithmetic unit 104. A frequency conversion circuit 105 is connected to the preceding stage of the first sampler 100 and the second sampler 101.

  FIG. 2 is a signal spectrum diagram schematically illustrating how the in-phase component I (t) and the quadrature component Q (t) of the complex baseband signal are obtained from the high-frequency signal input to the frequency conversion circuit 105. Hereinafter, the operations of the frequency conversion circuit 105 and the data receiving apparatus 1 will be described with reference to FIGS. 1 and 2.

In FIG. 2, a high frequency modulated signal r (t) is a high frequency signal by a spread spectrum method or the like, and is a signal input to the frequency conversion circuit 105. Let f _i be the center frequency of the high-frequency modulated signal r (t). It is assumed that the high frequency modulated signal r (t) includes the first partial band high frequency modulated signal 202 and the second partial band high frequency modulated signal 203. Each partial band high frequency modulated signal is a signal that can be demodulated by itself. Here, for the sake of simplicity, it is assumed that the high-frequency modulated signal r (t) includes two partial-band high-frequency modulated signals 202 and 203, but three or more partial-band high-frequency modulated signals are included. A signal may be included.

  The frequency conversion circuit 105 is an analog circuit, for example, as shown in FIG. 27, and is a known circuit including one frequency converter, a local oscillator, a bandpass filter, a gain controller, and a quadrature detector. The frequency conversion circuit 105 converts the input high-frequency modulated signal r (t) to a signal having a center frequency of 0 and performs low-pass filtering. As a result, the high frequency modulated signal r (t) is converted into a complex baseband signal 205 with a center frequency of 0, the first partial band high frequency modulated signal 202 is converted into a first partial band complex signal 206, The second partial band high frequency modulated signal 203 is converted into the second partial band complex signal 207.

  The frequency conversion circuit 105 outputs the in-phase component I (t) and the quadrature component Q (t) of the complex baseband signal 205 and inputs them to the first sampler 100 and the second sampler 101, respectively. The in-phase component I (t) and the quadrature component Q (t) are mixed with signals having the same spectrum as the first partial band complex signal 206 and the second partial band complex signal 207.

  The first sampler 100 samples the in-phase component I (t) of the complex baseband signal input from the frequency conversion circuit 105, and outputs a complex baseband signal in-phase component data sequence I (nT). Input to the band extraction unit 102. Here, n is an integer (n =..., -1, 0, 1,...), And T is a sample period. The second sampler 101 samples the quadrature component Q (t) of the input complex baseband signal, outputs a complex baseband signal quadrature component data sequence Q (nT), and outputs it to the partial band extraction unit 102. input. The complex baseband signal in-phase component data string may be referred to as a sampled in-phase component. Further, the complex baseband signal orthogonal component data string may be referred to as a sampled orthogonal component.

  The complex baseband signal in-phase component data sequence I (nT) and the complex baseband signal quadrature component data sequence Q (nT) are signals obtained by sampling I (t) and Q (t) at the timing of the sample period T, respectively. It is. Therefore, the orthogonal relationship established between I (t) and Q (t) is also established between I (nT) and Q (nT).

The partial band extraction unit 102 includes a complex filter, and an in-phase component (hereinafter referred to as a partial band signal in-phase component data sequence) IB of a partial band signal of the input complex baseband signal in-phase component data sequence I (nT). _The center frequency of _r (nT) and the quadrature component (hereinafter referred to as the partial band signal orthogonal component data sequence) QB _r (nT) of the partial band signal of the complex baseband signal orthogonal component data sequence Q (nT) is not zero. In this way, m identical bands are extracted and output. Here, r = 1, 2, 3,..., M, m are positive integers (m = 1, 2, 3,...). FIG. 1 shows a case where m = 2 as an example. The partial band signal in-phase component data sequence IB _r (nT) and the partial band signal quadrature component data sequence QB _r (nT) output from the partial band extraction unit 102 are held by I (nT) and Q (nT). Maintains orthogonality.

The first partial band complex signal 206 has a partial band signal in-phase component data sequence IB ₁ (nT) as an in-phase component and a partial band signal quadrature component data sequence QB ₁ (nT) as a quadrature component. Similarly, the second partial band complex signal 207 has a partial band signal in-phase component data sequence IB ₂ (nT) as an in-phase component and a partial band signal quadrature component data sequence QB ₂ (nT) as a quadrature component. .

As shown in FIG. 2, the partial band signal in-phase component data sequence IB ₁ (nT), the partial band signal quadrature component data sequence QB ₁ (nT), the partial band signal in-phase component data sequence IB ₂ (nT) and the partial band signal quadrature. The component data string QB ₂ (nT) does not include a DC component. Therefore, it can be said that these signals are intermediate frequency signals having phase rotation by themselves.

  Since the partial band extraction unit 102 extracts a partial band signal necessary for obtaining a demodulated signal from the complex baseband signal, an unnecessary signal included in the input signals I (t) and Q (t) Will be removed. For example, when extracting the first partial band complex signal 206, the partial band extraction unit 102 removes all signals having frequency components other than the first partial band complex signal 206.

The partial band extraction unit 102 inputs the partial band signal in-phase component data sequence IB ₁ (nT) and the partial band signal quadrature component data sequence QB ₁ (nT) to the first delay detection calculation unit 103, and the partial band signal in-phase component Data sequence IB ₂ (nT) and partial band signal orthogonal component data sequence QB ₂ (nT) are input to second delay detection calculation section 104.

The first delay detection calculation unit 103 generates a partial band detection signal in-phase component data sequence based on the input partial band signal in-phase component data sequence IB ₁ (nT) and the partial band signal quadrature component data sequence QB ₁ (nT). BI ₁ (nT) and the partial band detection signal orthogonal component data sequence BQ ₁ (nT) are output. The second delay detection calculation unit 104 generates a partial band detection signal in-phase component data sequence based on the input partial band signal in-phase component data sequence IB ₂ (nT) and the partial band signal quadrature component data sequence QB ₂ (nT). BI ₂ (nT) and the partial band detection signal orthogonal component data sequence BQ ₂ (nT) are output.

A determination circuit (not shown) is connected to the output side of the first delay detection calculation unit 103 and the second delay detection calculation unit 104. The determination circuit (not shown) includes the partial band detection signal in-phase component data sequence BI ₁ (nT) and the partial band detection signal quadrature component data sequence BQ ₁ (nT) output from the first delay detection calculation unit 103, and the first The phase polarity is determined based on the partial band detection signal in-phase component data sequence BI ₂ (nT) and the partial band detection signal quadrature component data sequence BQ ₂ (nT) output by the second delay detection calculation unit 104, and the received data is determined. For example, more appropriate reception data is output according to the reception status such as the number of errors and CRC error.

  FIG. 3 is a diagram illustrating a configuration of the first delay detection calculation unit 103 or the second delay detection calculation unit 104 in FIG. Since the configuration of the first delay detection calculation unit 103 and the configuration of the second delay detection calculation unit 104 are the same, the first delay detection calculation unit 103 will be described below as a representative. In FIG. 3, the first delay detection calculation unit 103 includes a delay unit 302, a first multiplier 304, a second multiplier 305, a first low-pass filter 308, and a second low-pass filter. And a pass filter 309.

ここで、ａ（ｎＴ）は部分帯域信号をベースバンド帯域で表示した場合の複素ベースバンド信号を、ωは部分帯域信号の中心周波数の角周波数を表している。 Next, the operation of the first delay detection calculation unit 103 will be described.
When a partial band signal that is an input signal to the first delay detection calculation unit 103 is expressed as S (nT), S (nT) is expressed as (Equation 1) using a complex display.

Here, a (nT) represents the complex baseband signal when the partial band signal is displayed in the baseband band, and ω represents the angular frequency of the center frequency of the partial band signal.

Since the partial band signal in-phase component data sequence IB _r (nT) and the partial band signal quadrature component data sequence QB _r (nT) are the in-phase component and quadrature component of S (nT), respectively, Is done. In the case of the first delay detection calculation unit 103, r = 1.

The partial band signal in-phase component data sequence IB _r (nT) is input to the first multiplier 304 and the delay unit 302. The delay unit 302 delays IB _r (nT) by one symbol time length kT and outputs it as a partial band signal in-phase component delayed data sequence IB _r (nT−kT). The first multiplier 304 and the second multiplier Input to the device 305. Here, k is the number of samples per symbol.

The first multiplier 304 multiplies IB _r (nT) and IB _r (nT−kT) to the first low-pass filter 308 as a delay detector in-phase component data string DETI _r (nT). input. The second multiplier 305 multiplies QB _r (nT) and IB _r (nT−kT) to obtain a delayed detector quadrature component data sequence DETQ _r (nT) for the second low-pass filter 309. input. DETI _r (nT) is expressed as (Equation 3). DETQ _r (nT) is expressed as (Equation 4).

The first low-pass filter 308 removes a high-frequency component from DETI _r (nT) and inputs it as BI _r (nT) to a determination circuit (not shown). The second low-pass filter 309 removes a high-frequency component from DETQ _r (nT) and inputs it to a determination circuit (not shown) as BQ _r (nT). BI _r (nT) is expressed as (Equation 5). BQ _r (nT) is expressed as (Equation 6).

ここで、ωｋＴ＝２πｚ（ただしｚは整数；ｚ＝・・・、−１、０、１、・・・）となるように部分帯域信号の中心周波数の角周波数ωを選ぶと、すなわち、部分帯域信号の中心周波数をＦｂ、シンボル周波数をＦｓとした場合、ω＝２πＦｂ、ｋＦｓ＝１／Ｔより、部分帯域信号の中心周波数が受信すべきデータのシンボル周波数の整数倍となるようにωを選ぶと、ｅｘｐで表される項は常に１となるので、（式７）は（式８）のように表される。

The complex conjugate multiplication of S (nT-kT), which is a signal obtained by delaying S (nT) and S (nT) by one symbol time length, is expressed as shown in (Expression 7) using a (nT). Is done.

Here, when the angular frequency ω of the center frequency of the partial band signal is selected so that ωkT = 2πz (where z is an integer; z =..., -1, 0, 1,...), When the center frequency of the band signal is Fb and the symbol frequency is Fs, ω = 2πFb, kFs = 1 / T, so that ω is an integer multiple of the symbol frequency of the data to be received. When selected, the term represented by exp is always 1, so (Expression 7) is expressed as (Expression 8).

  (Equation 8) is clearly equivalent to a delay detection operation using a complex baseband signal. Therefore, the first delay detection calculation unit 103 does not require one sign inverter and two selectors, which have been conventionally required (see FIG. 29), and one delay as shown in FIG. Delay detection can be realized with a simple configuration using only a multiplier, two multipliers, and two low-pass filters. The same applies to the second delay detection calculation unit 104.

  As described above, the data receiving apparatus 1 according to the first embodiment of the present invention uses the partial band extraction unit 102 to extract a partial band signal whose center frequency is not 0 from the complex baseband signal of the received modulated signal. At least one is extracted, and delay detection is performed using the extracted signal which is an intermediate frequency signal. When extracting a plurality of partial bands, the data receiving apparatus 1 simultaneously extracts a plurality of partial band signals from one complex baseband signal using the partial band extraction unit 102 realized by a complex filter. That is, a partial band signal is extracted by digital processing. Therefore, it is possible to provide a data receiving apparatus that does not require time for switching the local oscillation signal and does not require a plurality of analog circuits for extracting a plurality of partial band signals.

  Further, since signals other than the partial band required by the partial band extraction unit 102 are removed, the data receiving apparatus 1 can remove an unnecessary signal such as an interference wave using an analog circuit as in the prior art. A complex baseband signal can be used.

  In addition, since the partial band signal extracted by the partial band extraction unit 102 is an intermediate frequency signal with phase rotation, the data receiving apparatus can perform a delay detection calculation using the intermediate frequency signal.

  Further, by selecting ω so that the center frequency of the partial band signal is an integral multiple of the symbol frequency of the data to be received, two selectors and one sign inverter are not required as in the prior art, and one This can be realized with a delay unit, two multipliers, and two low-pass filters. Therefore, it is possible to provide a data receiving apparatus that solves the problem related to the reduction of the hardware scale when the LSI is implemented, which is one of the conventional problems.

  Furthermore, the data receiving apparatus 1 according to the first embodiment of the present invention does not directly sample the intermediate frequency signal with the sampler after frequency-converting the high frequency modulated signal into the intermediate frequency signal, After orthogonally transforming the modulation signal, a partial band signal obtained by removing unnecessary signals from the complex baseband signal obtained as a result of the orthogonal transformation is extracted and used as an intermediate frequency signal. Therefore, in the data receiving device 1 according to the first embodiment of the present invention, it is sufficient that the signal processing bandwidth required for the sampler is at least half the bandwidth of the high-frequency modulated signal. There is also an advantage that the data receiving apparatus of the present invention can be realized by using a cheaper sampler.

  Note that the high-frequency modulated signal used in the above embodiment is a spectrum modulated signal using a chirp signal obtained by repeatedly sweeping (sweeping) the frequency of a sine wave at a certain period in a phase-modulated signal. The performed signal is used as an example. FIG. 4 is a diagram illustrating an example of a signal obtained by performing spectrum spreading using a chirp signal as a spread modulation signal.

  In the above embodiment, the frequency conversion circuit 105 converts the frequency of the high frequency modulated signal r (t) so that the center frequency becomes 0. However, the partial band extraction unit 102 determines that the center frequency is 0. If a partial band signal that is not to be extracted is extracted, the frequency conversion circuit 105 may perform frequency conversion so that the center frequency does not become zero.

  In the above embodiment, the angular frequency ω of the center frequency of the partial band signal is selected so that ωkT = 2πz. However, ω may be selected so that ωkT = (2z + 1) π. In this case, since the signal output from the first delay detection calculation unit 103 is a signal obtained by inverting the sign of (Equation 8), the subsequent stage of the first low-pass filter 308 and the second low-pass filter 309. By providing a sign inverter, the same result as that of the circuit shown in FIG. 3 can be obtained.

  The same effect can be obtained even when ωkT is not equal to 2πz or (2z + 1) π. FIG. 5 is a diagram illustrating a configuration of the first or second delay detection calculation units 103 and 104 when a phase rotator is provided. In FIG. 5, the first and second delay detection calculation units 103 and 104 include a delay unit 402, a first multiplier 404, a second multiplier 405, a first low-pass filter 408, A second low-pass filter 409 and a phase rotator 412 are included.

The operations until the delay detector in-phase component data sequence DETI _r (nT) and the delay detector quadrature component data sequence DETQ _r (nT) are obtained in the delay detection arithmetic units 103 and 104 shown in FIG. 5 are the delays shown in FIG. This is the same as in the case of the detection calculation unit.

  However, when ωkT is equal to 2πz, (Expression 7) can be expressed as (Expression 8), and when ωkT is equal to (2z + 1) π, (Expression 7) is multiplied by (Expression 8) by -1. Although it can be expressed as an expression (an expression obtained by inverting the sign of (Expression 8)), the above expression cannot be performed in other cases. Therefore, the phase rotator 412 multiplies the signal expressed by (Expression 7) by exp (−jωkT) so that the signal expressed by (Expression 7) can be expressed by (Expression 8). By performing this calculation, the phase rotator 412 obtains an effect equivalent to the delay detection calculation using the complex baseband signal as shown in FIG. 3 even when ωkT is not equal to 2πz or (2z + 1) π. be able to.

  In the above embodiment, the partial band extraction unit 102 outputs both the in-phase component data sequence and the quadrature component data sequence. However, either one may be output. However, in that case, it is necessary to provide an orthogonal transformer on the output side of the partial band extraction unit 102. FIG. 6 is a diagram illustrating a configuration of the data receiving device 1 when an orthogonal transformer is provided. As shown in FIG. 6, the orthogonal transformers 106 and 107 are provided on the output side of the partial band extraction unit 102, and the in-phase component data sequence (or quadrature component data sequence) output from the partial band extraction unit 102 is used. After performing orthogonal transform, the in-phase component data sequence and the quadrature component data sequence are input to the first and second delay detection calculation units 103 and 104.

(Second Embodiment)
In the first embodiment, a high-frequency modulated signal including a plurality of partial band signals is input to the data receiving device. However, in the second embodiment, a case where a single modulated signal is input. A data receiving apparatus will be described.

  FIG. 7 is a diagram showing the configuration of the data receiving apparatus 2 according to the second embodiment of the present invention. In FIG. 7, the data receiving apparatus 2 includes a first sampler 500, a second sampler 501, a partial band extraction unit 502, and a delay detection calculation unit 503. A frequency conversion circuit 505 is connected to the preceding stage of the first sampler 500 and the second sampler 501. A determination circuit (not shown) is connected to the subsequent stage of the delay detection calculation unit 503.

  Hereinafter, operations of the frequency conversion circuit 505 and the data reception device 2 will be described. The first sampler 500 samples the in-phase component I (t) of the complex baseband signal output from the frequency conversion circuit 505, and outputs a complex baseband signal in-phase component data sequence I (nT). The second sampler 501 samples the quadrature component Q (t) of the complex baseband signal and outputs a complex baseband signal quadrature component data sequence Q (nT).

FIG. 8 is a signal spectrum diagram for schematically explaining how the in-phase component I (t) and the quadrature component Q (t) of the complex baseband signal are obtained from the high-frequency signal input to the frequency conversion circuit 505. In FIG. 8, the reception modulated signal r (t) is a high frequency signal input to the frequency conversion circuit 505. The center frequency of the received modulated signal r (t) is f _i. The frequency conversion circuit 505 regards a band including the received modulated signal r (t) and the unnecessary signal 603 as the virtual modulated signal 607. The frequency conversion circuit 505 frequency-converts the virtual modulated signal 607 so as to convert the reference frequency f _a for frequency conversion of the virtual modulated signal 607 into the complex baseband signal center frequency f _c = 0, and performs quadrature detection. Output complex baseband signal.

  By this frequency conversion, the received modulated signal r (t) is frequency-converted to the complex signal 605 and the unnecessary signal 603 is converted to the unnecessary complex signal 606. Therefore, the complex baseband signal that is an input signal of the first sampler 500 and the second sampler 501 is an analog signal in which the spectrum of the complex signal 605 and the spectrum of the unnecessary complex signal 606 are mixed. Therefore, even if the complex baseband signal is low-pass filtered using a low-pass filter, the complex signal 605 and the unnecessary complex signal 606 cannot be separated.

  In the data receiving apparatus 2, the complex baseband signal including the complex signal 605 and the unnecessary complex signal 606 becomes an input signal to the first sampler 500 and the second sampler 501. Since the partial band extraction unit 502 extracts a partial band from the complex baseband signal using a complex filter, the partial band extraction unit 502 can separate and extract the complex signal 605 and the unnecessary complex signal 606. The partial band extraction unit 502 extracts only the complex signal 605 having a band substantially equal to the band of the modulated signal to be originally received, and the partial band signal in-phase component data string IB (nT), which is the in-phase component of the complex signal 605, And a partial band signal quadrature component data string QB (nT), which is a quadrature component, is output.

  As shown in FIG. 8, this partial band signal is an intermediate frequency signal whose center frequency is not zero. Therefore, by using the same configuration (see FIG. 3) as the delay detection calculation unit shown in the first embodiment, the delay detection calculation unit 503 detects the detection signal in-phase component data as in the case of the first embodiment. A sequence BI (nT) and a detection signal orthogonal component data sequence BQ (nT) are output.

  As described above, the data receiving apparatus 2 according to the second embodiment of the present invention uses a complex baseband signal that includes a modulated signal as a partial band from a virtual modulated signal that is frequency-converted so that the center frequency does not become zero. Are extracted by removing unnecessary signal components using a partial band extraction unit 502 formed of a complex filter. That is, the data receiving apparatus 2 extracts an intermediate frequency signal including almost all frequency components of the modulated signal that has been frequency-converted to the low frequency band, performs delay detection using the extracted intermediate frequency signal, and performs detection. Get a signal. Therefore, as shown in the first embodiment, the data receiving apparatus 2 according to the second embodiment is a method other than a method of extracting at least one partial band component from the frequency components of the received modulated signal and obtaining a demodulated signal. It can also be used for demodulation of the phase modulation method.

  Further, the data receiving apparatus 2 according to the second embodiment uses a complex filter as a complex baseband signal including a plurality of modulated wave signals having mutually different band characteristics, and uses a complex filter to generate a plurality of modulated wave signals. This can also be applied to the case where a detection signal is obtained by simultaneously extracting. However, in this case, a separate determination circuit is required for each modulated wave signal.

  In the above embodiment, the received modulated signal r (t) to be received is a signal whose spectrum is represented in FIG. 8, and the unnecessary signal 603 to be removed is used. Can be obtained.

  Further, if the number of partial band signals to be extracted is increased, modulated signals corresponding to the number of extracted partial bands can be detected simultaneously.

(Third embodiment)
Next, a detailed configuration of the partial band extracting unit 102 in the data receiving device 1 according to the first embodiment will be described. First, the theory that is the basis for the configuration of the partial band extraction unit 102 will be described using mathematical expressions.

（式９）および（式１０）において、＊は畳み込み積分演算を、ｊは虚数単位を表している。 Now, it is assumed that the center frequencies of the two partial band signals to be extracted are at equidistant positions that are separated from each other by 0 to 1 MHz. Further, it is assumed that the transfer function of the complex filter constituting the partial band extraction unit 102 for extracting the partial band complex signal 207 shown in FIG. 2 is represented by Hb (nT). In this case, the transfer function of the complex filter for extracting the partial band complex signal 206 shown in FIG. 2 is a complex conjugate of Hb (nT). As a result, if the partial band complex signal 207 is represented by S2 (nT) and the partial band complex signal 206 is represented by S1 (nT), S2 (nT) and S1 (nT) are expressed by (Equation 9) and (Equation 10). It is expressed as follows.

In (Equation 9) and (Equation 10), * represents a convolution integral operation, and j represents an imaginary unit.

  In (Equation 9) and (Equation 10), comparing the in-phase component and the quadrature component of S2 (nT) and S1 (nT), the in-phase component is Re (S (nT)) * Re (Hb (nT) ) And Im (S (nT)) * Im (Hb (nT)), and the orthogonal components are Im (S (nT)) * Re (Hb (nT)) and Re (S (nT)) * Im (Hb ( nT)). If this mathematical theory is used, the partial band extraction unit 102 in the first embodiment can be easily realized. Hereinafter, the configuration of the partial band extraction unit 102 will be specifically described.

  FIG. 9 is a diagram illustrating a configuration of a bandwidth extraction unit according to the third embodiment. The partial band extraction unit 102 illustrated in FIG. 9 uses mathematical theoretical results represented by (Expression 9) and (Expression 10). In FIG. 9, the partial band extraction unit 102 includes a first filtering device 1701, a second filtering device 1702, a third filtering device 1703, a fourth filtering device 1704, and a first subtractor 1705. , A second subtracter 1707, a first adder 1706, and a second adder 1708.

  In FIG. 9, if I (nT) corresponds to the input signal Re {S (nT)} and Q (nT) corresponds to the input signal Im {S (nT)}, the data receiving apparatus according to the first embodiment. One partial band extraction unit 102 is realized.

  The first filtering device 1701 performs a convolution integral operation of Re (S (nT)) * Re (Hb (nT)). Similarly, the second filtering device 1702 calculates Im (S (nT)) * Im (Hb (nT)). The third filtering device 1703 calculates Im (S (nT)) * Re (Hb (nT)). The filtering device 1704 calculates Re (S (nT)) * Im (Hb (nT)).

  The first subtractor 1705 calculates Re (S (nT)) * Re (Hb (nT))-Im (S (nT)) * Im (Hb (nT)) to obtain a partial band complex signal. The in-phase component of S2 (nT) is output. The second adder 1708 performs an operation of Im (S (nT)) * Re (Hb (nT)) + Re (S (nT)) * Im (Hb (nT)), thereby obtaining the partial band complex signal S2. The orthogonal component of (nT) is output.

  In addition, the first adder 1706 performs a calculation of Re (S (nT)) * Re (Hb (nT)) + Im (S (nT)) * Im (Hb (nT)), thereby obtaining a partial band complex. The in-phase component of the signal S1 (nT) is output. The second subtractor 1707 calculates Im (S (nT)) * Re (Hb (nT)) − Re (S (nT)) * Im (Hb (nT)), thereby calculating the complex signal S1 ( nT) orthogonal components are output.

Thus, partial band extracting section 102, the IB ₁ (nT) as an output signal _{Im {S 1 (nT)}} , QB 1 as Re {S ₁ (nT)} a _{(nT), Im {S 2} (nT ) IB ₂ a (nT) as}, and output the QB ₂ (nT) as _{Re {S 2 (nT)}} ( refer to FIG. 1).

  Thus, in the third embodiment, as represented by (Equation 9) and (Equation 10), since the filtering devices having a common tap coefficient are shared, the partial band extraction unit The configuration of 102 can be simplified.

  In the above embodiment, two partial band signals are extracted. However, the present invention can be applied to the case of extracting a plurality of partial bands. Specifically, the filtering devices having the same tap coefficient may be shared to configure the partial band extraction unit.

(Fourth embodiment)
In the partial band extraction unit 102 shown in FIG. 9, it is necessary to prepare two filtering devices 1701 and 1703 and two filtering devices 1702 and 1704 having the same configuration. In the fourth embodiment, a partial band extraction unit that combines overlapping filtering devices into one will be described.

  FIG. 10 is a diagram illustrating the configuration of the partial band extraction unit according to the fourth embodiment. In FIG. 10, the partial band extraction unit 102 includes a first input selector 2101, a second input selector 2102, a first filtering device 2103, a second filtering device 2104, and a first output selection. 2105, second output selector 2106, first subtractor 2107, second subtractor 2109, first adder 2108, second adder 2110, and first delay device 2 and a second delay device 2112.

Hereinafter, the operation of the partial band extraction unit 102 shown in FIG. 10 will be described.
The first input selector 2101 and the second input selector 2102 alternately select two input signals whose values change with the period τ every period τ / 2, and output the selected signals. FIG. 11 is a timing chart showing the operation of the first input selector 2101 or the second input selector 2102.

  The first filtering device 2103 connected to the subsequent stage of the first input selector 2101 performs convolution integration on the signal input every period τ / 2. The second filtering device 2104 performs convolution integration on the signal input every period τ / 2.

  The first output selector 2105 and the second output selector 2106 send a signal whose value changes in a cycle of τ / 2 to two different output terminals every cycle τ / 2 in synchronization with the data change timing. Output. FIG. 12 is a timing chart showing the operation of the first output selector 2105 or the second output selector 2106.

  FIG. 13 is a timing chart of signals output from the first input selector 2101 or the second input selector 2102. As can be seen from FIGS. 11 and 12, the signal Re {S (nT)} and the signal Im {S (nT)} that change in the period T are input to the first input selector 2101 and the second input selector 2102. Assuming that τ is equal to T, the signals Bi1 and Bi2 output from the first input selector 2101 and the second input selector 2102 change at the timing as shown in FIG. Go.

  FIG. 14 is a timing chart of signals output from the first output selector 2105 or the second output selector 2106. Since the first filtering device 2103 and the second filtering device 2104 perform convolution integration every period T / 2, the signals C1 and C2 output from the first output selector 2105, the second output selector 2106 The signals C3 and C4 output from are respectively changed at the timing as shown in FIG.

  The outputs C1 to C4 will be specifically described on the assumption that there is no signal processing delay. For example, when Bi1 is Re {S (nT)}, Bi2 is Im {S (nT)}. At this time, C1 (nT) becomes Re {S (nT)} * Re {Hb} for one period. C2 (nT) becomes Im {S ((n-1) T)} * Re {Hb} in the first half of this period, and Im {S (nT)} * Re {Hb} in the latter half of this period. Become. C3 (nT) becomes Im {S (nT)} * Im {Hb} during this period. C4 (nT) becomes Re {S ((n-1) T} * Im {Hb} in the first half of this period, and Re {S (nT)} * Im {Hb} in the latter half of this period. .

  The first delayer 2 delays the signal C1 by a time U = T / 2, and the second delayer 2112 delays the signal C3 by a time U = T / 2, so that the first subtractor 2107 and the first subtractor 2107 The timing of the signal input to the adder 2108 is almost the same. In addition, the timings of signals input to the second subtractor 2109 and the second adder 2110 are substantially the same.

  Therefore, as can be seen from the specific examples (Equation 9) and (Equation 10), the first adder 2108 outputs the in-phase component of the partial band complex signal S1 (nT). The second subtracter 2109 outputs an orthogonal component of the complex signal S1 (nT). The first subtractor 2107 outputs the in-phase component of the partial band complex signal S2 (nT). The second adder 2110 outputs the quadrature component of the complex signal S2 (nT).

  As shown in (Equation 9) and (Equation 10), if a pair of partial band complex signals located equidistant from the frequency 0 is taken as a pair, a complex filter tap for extracting the pair of partial band complex signals. The coefficients can be in a complex conjugate relationship with each other. Therefore, it is possible to share the filtering device that extracts each partial band, like the partial band extracting unit in the fourth embodiment.

  In the above specific example, there are two partial bands to be extracted. However, when there are an even number of partial bands of four or more, a pair of partial bands whose center frequencies are equidistant from frequency 0 are used as a pair. Tap coefficients can be shared for pairs.

  In the above embodiment, the input selection devices 2101 and 2102 select the input signal in the order of the in-phase component and quadrature component of S (nT) every T / 2, but this order is reversed. Also good. That is, you may make it select in order of a quadrature component and an in-phase component. In this case, the first delay device 2 is connected to the output end on the C2 side of the first output selector 2105, and the second delay device 2112 is connected to the output end on the C4 side of the second output selector 2106. What should I do?

(Fifth embodiment)
FIG. 15 is a diagram illustrating a general configuration of a complex filter used in the filtering device in the partial band extraction unit according to the third and fourth embodiments. FIG. 15 shows a configuration in the case where an FIR (Finite Impulse Response) filter is used as the complex filter. In the fifth embodiment, a method for making the FIR filter simpler will be described.

  FIG. 16 is a complex plan view for explaining tap coefficients of the complex filter. FIG. 17 is a schematic diagram expressing the passband characteristics of the complex filter used in the partial band extraction unit in the baseband band.

  In FIG. 15, the FIR filter includes u−1 delay units 900, u tap coefficient multipliers 903, and one adder 906. Here, u is an integer of 2 or more. In the drawing, h1, h2,..., Hu indicate complex tap coefficient values of the respective tap coefficient multipliers 903. X (nT) is a complex signal data sequence. Y (nT) is a complex signal data string after waveform shaping.

In order to extract a partial band signal whose center frequency is Fb using the low pass filter having the pass band characteristic shown in FIG. 17, a phase rotation component is previously added to each tap coefficient of the filter showing the pass band characteristic. It is necessary to multiply. Assuming that the symbol frequency of the transmitted data is Fs, the phase rotation component θ to be multiplied by the tap coefficient hd (d = 1, 2, 3,..., U) is expressed by (Equation 11 ).

  The relationship between the angular frequency ω of the center frequency of the subband signal to be extracted and the sample period T is ωkT = 2πz (where z is an integer; z =..., -1, 0, 1,...). That is, if the angular frequency ω of the center frequency in the partial band signal to be extracted is selected so that the center frequency of the partial band signal is an integral multiple of the symbol frequency of the data to be transmitted, the delay detection calculation units 103 and 104 are It has been described in the first embodiment that it can be easily realized.

なぜなら、ｋとｚとの関係が（式１２）のように表される場合、タップ係数ｈｄに乗算すべき位相回転成分θの集合には、（式１１）より、同相成分あるいは直交成分のいずれか一方を０にする０ｒａｄ，π／２ｒａｄ，πｒａｄ，３π／２ｒａｄが含まれ、かつ、同相成分および直交成分の絶対値が同じ値となるπ／４ｒａｄ，３π／４ｒａｄ，５π／４ｒａｄ，７π／４ｒａｄが含まれるためである。 In addition, when ω is selected so as to satisfy the relationship shown in (Equation 12), not only the delay detection calculation units 103 and 104 but also a filtering device (complex filter) used for the partial band extraction unit 102 can be easily realized. can do.

This is because when the relationship between k and z is expressed as in (Expression 12), the set of phase rotation components θ to be multiplied by the tap coefficient hd is either in-phase component or quadrature component from (Expression 11). Π / 4 rad, 3π / 4 rad, 5π / 4 rad, 7π /, which include 0 rad, π / 2 rad, π rad, 3π / 2 rad, in which one of them is 0, and the in-phase component and the quadrature component have the same absolute value. This is because 4 rads are included.

  First, note that the phase rotation component θ includes 0 rad, π / 2 rad, π rad, 3π / 2 rad. When the phase rotation component θ to be multiplied by the tap coefficient hd is equal to 0 rad, π / 2 rad, π rad, 3π / 2 rad, the in-phase component or quadrature component of the tap coefficient obtained as a result of multiplication becomes 0, and the tap coefficient multiplier 903 is Can be reduced.

  Next, attention is paid to the fact that the phase rotation component θ includes π / 4 rad, 3π / 4 rad, 5π / 4 rad, and 7π / 4 rad. When the phase rotation component θ to be multiplied by the tap coefficient hd is equal to π / 4 rad, 3π / 4 rad, 5π / 4 rad, 7π / 4 rad, the absolute values of the in-phase component and quadrature component of the tap coefficient obtained as a result of multiplication are equal. Both tap coefficients can be shared, and the tap coefficient multiplier 903 can be reduced.

The above description will be described using mathematical expressions. FIG. 18 is a diagram illustrating an impulse response waveform of the complex filter. For example, a low-pass filter expressing a complex filter in the baseband band is an FIR filter with 20 taps (u = 20), and its impulse response waveform is a symmetric waveform as shown in FIG. Then, the transfer function HL (nT) of the complex filter is generally expressed as (Equation 13) using Z transformation.

ここで、Ｈｂ（ｎＴ）は、（式９）および（式１０）に示された複素フィルタの伝達関数Ｈｂ（ｎＴ）の一つの例である。また、（式１４）中のＲｅ｛Ｈｂ（ｎＴ）｝は、伝達関数の同相成分を表す。また、（式１５）中のＩｍ｛Ｈｂ（ｎＴ）｝は、伝達関数の直交成分を表す。 FIG. 19 is a diagram showing a set of phase rotation components θ to be multiplied by the tap coefficients satisfying the relationship of (Equation 12) on a complex plane. In (Equation 13), the tap coefficient h10 located just in the center is multiplied by the phase rotation component θ = 1 + j0, and the phase rotation component θ is extracted to each tap coefficient hd so that the partial band complex signal S2 (nT) is extracted. (Equation 13) is expressed as (Equation 14) and (Equation 15) in the case where the in-phase component and the quadrature component are expressed separately.

Here, Hb (nT) is an example of the transfer function Hb (nT) of the complex filter shown in (Equation 9) and (Equation 10). In addition, Re {Hb (nT)} in (Expression 14) represents the in-phase component of the transfer function. Also, Im {Hb (nT)} in (Expression 15) represents an orthogonal component of the transfer function.

  Focusing on (Equation 14), it can be seen that there are no terms of h4 and h8. This is because the coefficient becomes 0 as a result of multiplication by π / 2 rad and 3π / 2 rad as the phase rotation component θ. Further, focusing on (Equation 15), it can be seen that there are no terms of h2, h6, and h10. This is because the coefficient becomes 0 as a result of multiplying 0 rad and π rad as the phase rotation component θ. Further, in (Equation 14) and (Equation 15), when attention is paid to the value of each tap coefficient excluding the sign, h1, h3, h5, h7, and h9 are expressed in the in-phase component and the quadrature component of the transfer function Hb (nT). It can be seen that the five coefficients included are common. This is because the phase rotation component θ is arranged so as to include a value that is an integral multiple of π / 4 when the relationship shown in (Equation 12) is satisfied.

  Thus, ωkT = 2πz (where z is an integer; z =... -1, 0, 1,...), That is, the center frequency of the partial band to be extracted is an integer multiple of the symbol frequency. In addition, by setting the number of samples in one symbol period to be a multiple of eight times the value obtained by dividing the center frequency of the partial band to be extracted by the symbol frequency, the taps of the complex filters constituting the partial band extraction unit The number can be made small. Therefore, the partial band extraction unit shown in the fourth embodiment and the fifth embodiment can be realized with a simpler configuration.

  Since the tap coefficients of the complex filter for extracting a pair of partial bands are in a complex conjugate relationship with each other, when extracting a plurality of partial bands, a pair of partial bands located at equidistant positions from frequency 0 is used. By extracting an even number of partial bands, in addition to the above two effects, there is an effect that tap coefficients can be shared between filters that extract each partial band.

(Specific explanation of effect)
Hereinafter, the above effect will be described in detail by taking as an example a case where the partial band extraction unit 102 shown in the first or second embodiment extracts two partial bands.

  Now, the number of samples per symbol k = 16, the symbol frequency Fs of the signal to be transmitted Fs = 0.5 MHz, and the center frequencies of the two partial bands to be extracted are set at a frequency 1 MHz apart from the frequency 0 And That is, it is assumed that kT = 1 / Fs = 2 MHz, Fb = 1 MHz or −1 MHz. From (Equation 11), the phase rotation component θ to be multiplied by the tap coefficient hd (where d = 0, 1, 2,..., U) is π / 4 rad. Further, from Fb / Fs = z, α in (Expression 12) is 1. From the above, it can be seen that the above setting satisfies two conditions of ωkT = 2πz (z is an integer) and (Equation 12).

  Π / 4 rad, which is the value obtained by (Equation 11), is equal to eight values shown on the complex plane of FIG. 19 counterclockwise or clockwise when the phase rotation component θ is every sample period T. It means to go one by one. As can be seen from FIG. 19, since the phase rotation component θ takes values of 0 rad, π / 2 rad, π rad, 3π / 2 rad, in the phase rotation component, the in-phase component or quadrature component of the tap coefficient is 0, and the tap coefficient The number of multipliers can be reduced. Further, since the phase rotation component θ takes values of π / 4 rad, 3π / 4 rad, 5π / 4 rad, and 7π / 4 rad, the absolute values of the in-phase component and the quadrature component of the tap coefficients are the same in the phase rotation component. Since the tap coefficient multipliers can be shared, the number of tap coefficient multipliers can be reduced.

  From the above, if ωkT = 2πz (where z is an integer; z =..., -1, 0, 1,...) And ω satisfying the relationship shown in (Equation 12) are selected, the tap coefficient It can be seen that the number of multipliers can be reduced, and not only the delay detection operation unit can be easily realized but also the partial band extraction unit can be easily realized.

(Sixth embodiment)
FIG. 20 is a schematic diagram of a wireless communication system using the data receiving apparatus according to the embodiment of the present invention. 20, the wireless communication system includes i (where i is a positive integer) number of base stations (first base station 2500, second base station 2501,..., I−1th base station 2502, i th. Base station 2503) and a mobile station 2504. The mobile station 2504 is a wireless communication device that uses the data receiving device according to the embodiment of the present invention. Hereinafter, the mobile station 2504 will be described as using the data receiving apparatus 1 according to the first embodiment as a data receiving apparatus. However, any data receiving apparatus may be used as long as it is the above embodiment. Good. Note that there may be a plurality of mobile stations. Hereinafter, the operation of the wireless communication system shown in FIG. 20 will be described with reference to FIG. 1 and FIG.

FIG. 21 is a diagram schematically showing the state of the spectrum of the high-frequency modulated signal used in the wireless communication system shown in FIG. In FIG. 21, a spectrum r ₁ (t) indicates a spectrum of a phase-modulated high frequency modulated signal output from the first base station 2500. A spectrum r ₂ (t) represents a spectrum of the phase-modulated high-frequency modulated signal output from the second base station 2501. A spectrum r _i-1 (t) represents a spectrum of the phase-modulated high-frequency modulated signal output from the ( _i−1 ) -th base station 2502. A spectrum r _i (t) represents a spectrum of the phase-modulated high-frequency modulated signal output from the i-th base station 2503.

  As described in the first embodiment, the high frequency modulated signal may include two or more partial band high frequency modulated signals. Therefore, the data receiving apparatus of the present invention can extract at least one partial band, that is, m (where m is a positive integer not less than 1 and not more than i) partial bands. In the following description, for simplicity, it is assumed that m = 2, that is, a data reception apparatus incorporating a partial band extraction unit that extracts two partial bands is used in the mobile station 2504.

Here, the mobile station 2504 uses the high frequency modulated signal output from the first base station 2500 and the high frequency output from the second base station 2501 out of the i spectra shown in FIG. Assume that you are trying to receive a modulated signal. The frequency conversion circuit 105 shown in FIG. 1 receives a high frequency modulated signal having a virtual spectrum R (t) including all bands from the spectrum r ₁ (t) to r _i (t) as frequency components. Is done. In such a situation, the frequency conversion circuit 105 uses the virtual spectrum r (t) having a center frequency f _i including the spectrum r ₁ (t) and the spectrum r ₂ (t) as a frequency component. Is regarded as a high frequency modulated signal to be received. Then, the frequency conversion circuit 105 performs frequency conversion on the virtual spectrum r (t) so that the center frequency f _i becomes the frequency 0. That is, in the frequency conversion circuit 105, the spectrum r ₁ (t) becomes the spectrum 2601, the spectrum r ₂ (t) becomes the spectrum 2602, the spectrum r _i-1 (t) becomes the spectrum 2603, and the spectrum r _i (t) becomes the spectrum 2601. Frequency conversion is performed so that the spectrum 2604 becomes the virtual spectrum r (t) and the virtual spectrum 2600. As a result, the data reception device 1 in the mobile station 2504 is similar to the first embodiment, and the in-phase component data of the complex baseband signal having only the spectrum 2601 as the frequency component and the sub-band detection signal in-phase component data which is the quadrature component. The sequence BI ₁ (nT) and the partial band detection signal quadrature component data sequence BQ ₁ (nT), and the in-phase component and quadrature component in-phase component data sequence of the complex baseband signal having only the spectrum 2602 as the frequency component BI ₂ (nT) and the partial band detection signal orthogonal component data sequence BQ ₂ (nT) are output.

A determination circuit (not shown) is independently connected to the output side of the first delay detection calculation unit 103 and the second delay detection calculation unit 104. A determination circuit (not shown) provided on the output side of the first delay detection calculation unit 103 includes a partial band detection signal in-phase component data string BI ₁ (nT) and a partial output from the first delay detection calculation unit 103. Based on the band detection signal orthogonal component data string BI ₂ (nT), the phase is determined, and the received data string is output. A determination circuit (not shown) provided on the output side of the second delay detection calculation unit 104 includes a partial band detection signal in-phase component data sequence BI ₂ (nT) and a partial output from the second delay detection calculation unit 104. Based on the band detection signal orthogonal component data string BQ ₂ (nT), the phase is determined, and the received data string is output. That is, the mobile station 2504 can simultaneously obtain the received data from the first and second base stations 2500 and 2501 by using the data receiving apparatus 1 without preparing a plurality of receiving systems as in the prior art. Can do.

  Conventional receivers require i reception systems in order to receive i independent high-frequency modulated signals and obtain respective received data. However, as described above, the mobile station that is the wireless communication apparatus of the present invention can simultaneously obtain received data from i independent high-frequency modulated signals using only one receiving system.

  In order for the mobile station to extract m partial bands, the mobile station uses a data receiving apparatus in which a partial band extraction unit for extracting m partial bands is incorporated.

  Note that the first to i-th base stations 2500 to 2503 may have a function as a mobile station, and the mobile station 2504 may have a function as a base station. In this case, the mobile station 2504 as a base station can simultaneously receive data received from the base stations 2500 and 2501 as mobile stations.

  If a mobile station using the data receiving apparatus of the present invention receives m high frequency modulated signals simultaneously as described above, it is m times faster than the case where communication is performed using only one band. The data reception process can be performed.

  As described in the first embodiment, the data reception device of the mobile station may select and output one piece of appropriate data from the m pieces of reception data according to the reception level. As a result, when one high frequency modulated signal is output from one base station, the mobile station selects one appropriate base station when moving between areas of m base stations. You can communicate while selecting.

(Seventh embodiment)
22 and 23 are block diagrams illustrating configuration examples of the wireless communication devices 10 and 20 according to the seventh embodiment of the present invention using the data receiving device according to the embodiment of the present invention.
First, the operation of the wireless communication device 10 will be described with reference to FIGS. In FIG. 22, the radio communication device 10 includes a frequency conversion circuit 2700, a data reception device 2701 according to the embodiment of the present invention, first to i-th determination circuits 2703, a reception data integration circuit 2704, an antenna, 2705, a transmission circuit 2706, and a transmission / reception changeover switch 2707. The radio communication apparatus 10 includes a virtual high frequency modulated signal including the spectrum r ₁ (t), r ₂ (t),..., R _i (t) (where i is a positive integer) shown in FIG. R (t) is received.

The frequency conversion circuit 2700 performs frequency conversion so that f _i that is the center frequency of the virtual high frequency modulated signal R (t) becomes zero. The partial band extraction unit of the data receiving device 2701 extracts each band of the spectra r ₁ (t), r ₂ (t),..., R _i (t) included in the virtual high frequency modulated signal R (t). . Each delay detection calculation unit of the data reception device 2701 outputs a partial band detection signal orthogonal component data sequence and an in-phase component data sequence corresponding to each band extracted by the partial band extraction unit. First to i-th determination circuits 2703 output data D1 to Di based on the input partial band detection signal quadrature component data sequence and in-phase component data sequence, respectively.

Now, it is assumed that the transmission / reception changeover switch 2707 is set so that the antenna 2705 and the reception circuit are connected. In this case, each of the first to i-th determination circuits 2703 of the reception circuit outputs reception data Dk corresponding to the high-frequency modulated signal having the spectrum r _k (t) as a frequency component (k = 1,..., i).

Here, a transmitter (not shown) for transmitting a signal to the wireless communication apparatus 10 divides the transmission data TXD into i pieces of transmission data TXD ₁ to TXD _i in advance, and the divided transmission data TXD. Assume that _k is transmitted as a high-frequency modulated signal having a spectrum r _k (t) as a frequency component. That is, the received data Dk is the one whose divided transmitted data TXD _k on the transmitting side.

  The reception data integration circuit 2704 combines the reception data D1 to Di, generates transmission data TXD before being divided, and outputs it as reception data.

As described above, when the data receiving device of the present invention is incorporated in a wireless communication device, the data receiving process can be performed at a speed i times faster than the case where communication is performed using only the band represented by the spectrum r _i (t). Can do.

Next, the operation of the wireless communication device 20 will be described with reference to FIGS. In FIG. 23, parts having the same functions as those of the wireless communication apparatus shown in FIG. The wireless communication device 20 includes a frequency conversion circuit 2700, a data reception device 2701 according to the embodiment of the present invention, first to i-th determination circuits 2703, a display 2804, an antenna 2705, and a transmission circuit 2706. And a transmission / reception changeover switch 2707. The wireless communication device 20 receives a virtual high frequency modulated signal R (t) including the spectrum r ₁ (t), r ₂ (t),..., R _i (t) (where i is a positive integer) as a frequency component. To do. Similarly to the wireless communication device 10, the wireless communication device 20 obtains reception data Dk corresponding to a high-frequency modulated signal having the spectrum r _k (t) as a frequency component. The display 2804 in the wireless communication device 20 displays the contents of the received data independently of each of the i received data Dk (k = 1,..., I) obtained.

  In this way, if the data receiving device of the present invention is incorporated into a wireless communication device, a single receiving system is prepared, and a plurality of signal processing is performed simultaneously, and the obtained received data is independently processed in parallel. Can be displayed.

  As described above, if the data receiving apparatus of the present invention is used for a wireless communication apparatus, it is possible to increase the data transmission speed and to process received data in parallel only by preparing one receiving system.

  The data receiving apparatus according to the present invention reduces the time required to extract a plurality of partial band signals, does not require a plurality of analog circuits with uniform characteristics, is ready for LSI, has a simple configuration, It is useful as a device used for a wireless communication device or the like.

The figure which shows the structure of the data receiver 1 which concerns on the 1st Embodiment of this invention. Signal spectrum diagram for schematically explaining how in-phase component I (t) and quadrature component Q (t) of a complex baseband signal are obtained from a high-frequency signal input to frequency conversion circuit 105 The figure which shows the structure of the 1st delay detection calculating part 103 or the 2nd delay detection calculating part 104 in FIG. The figure which shows an example of the signal which spectrum-spreaded the chirp signal as a spread modulation signal The figure which shows the structure of the 1st or 2nd delay detection calculating part 103,104 in the case of providing a phase rotator. The figure which shows the structure of the data receiver 1 at the time of providing an orthogonal transformer. The figure which shows the structure of the data receiver 2 which concerns on the 2nd Embodiment of this invention. Signal spectrum diagram for schematically explaining how in-phase component I (t) and quadrature component Q (t) of a complex baseband signal are obtained from a high-frequency signal input to frequency conversion circuit 505 The figure which shows the structure of the partial band extraction part which concerns on 3rd Embodiment. The figure which shows the structure of the partial band extraction part which concerns on 4th Embodiment. Timing chart showing the operation of the first input selector 2101 or the second input selector 2102 Timing chart showing the operation of the first output selector 2105 or the second output selector 2106 Timing chart of signals output from the first input selector 2101 or the second input selector 2102 Timing chart of signals output from the first output selector 2105 or the second output selector 2106 The figure which shows the general structure of the complex filter used for the filtering apparatus in the partial band extraction part which concerns on 3rd and 4th embodiment. Complex plan view for explaining tap coefficients of complex filter Schematic representation of the passband characteristics of the complex filter used in the subband extractor in the baseband Diagram showing impulse response waveform of complex filter A diagram in which a set of phase rotation components θ to be multiplied with each tap coefficient satisfying the relationship of (Expression 12) is represented on a complex plane. Schematic diagram of wireless communication system using data receiver The figure which showed roughly the mode of the spectrum of the high frequency modulated signal used in the radio | wireless communications system shown in FIG. The block diagram which shows the structural example of the radio | wireless communication apparatuses 10 and 20 which concern on the 7th Embodiment of this invention using the data receiver which concerns on one Embodiment of this invention. The block diagram which shows the structural example of the radio | wireless communication apparatuses 10 and 20 which concern on the 7th Embodiment of this invention using the data receiver which concerns on one Embodiment of this invention. The figure which showed typically the spectrum of the received signal in order to demonstrate operation | movement of the radio | wireless communication apparatuses 10 and 20 which concern on 7th Embodiment. The figure which shows the structure of the data receiver described in the patent 3161146 gazette The figure which shows the spectrum of the signal in the principal part of the data receiver shown in FIG. Block diagram showing an outline of a configuration of a receiver in a wireless modem described in "SR-chirp spread spectrum wireless modem" IEICE Technical Report RCS95-102 The figure which shows an example of a structure of the delay detection apparatus provided in the inside of the baseband signal processing part 1512. The figure which shows the structure of the delay detection calculating part 1103.

Explanation of symbols

1, 2, 2701 Data receiving device 10, 20 Wireless communication device 100, 500 First sampler 101, 501 Second sampler 102, 502 Partial band extraction unit 103 First delay detection calculation unit 503 Delay detection Calculation unit 104 Second delay detection calculation unit 105, 505, 2700 Frequency conversion circuit 106, 107 Orthogonal transformer 302, 402, 900 Delay unit 304, 404 First multiplier 305, 405 Second multiplier 308, 408 First low-pass filter 309, 409 Second low-pass filter 412 Phase rotators 1701, 2103 First filtering device 1702, 2104 Second filtering device 1703 Third filtering device 1704 Fourth filtering device 1705 , 2107 First subtractor 1706, 2108 First adder 170 7, 2109 Second subtractor 1708, 2110 Second adder 2101 First input selector 2102 Second input selector 2105 First output selector 2106 Second output selector 2 First delay device 2112 2nd delay device 903 Tap coefficient multiplier 906 Adder 2500 to 2503 Base station 2504 Mobile station 2703 Determination circuit 2704 Data integration circuit 2705 Antenna 2706 Transmission circuit 2707 Transmission / reception changeover switch 2804 Display

Claims (21)

The in-phase and quadrature signals obtained by quadrature detection modulated wave signal phase-modulated after frequency conversion as an input signal, a data receiving equipment which outputs a detection signal,
And sampling said in-phase signal at every predetermined sampling period, a first sampler for outputting the sampled in-phase signal,
And sampling said quadrature signal at every said predetermined sampling period, a second sampler for outputting a sampled quadrature signal,
A center frequency is selected from frequency components included in the sampled in-phase signal output from the first sampler and the sampled quadrature signal output from the second sampler. extracting at least one partial band non-zero, the signal of the extracted sub-band is divided into in-phase and quadrature components, a partial band extracting section for outputting as a partial band signal,
Based on the partial band signal the partial band extracting section outputs, and outputs a detection wave signal, the data receiving apparatus. The data reception device according to claim 1, further comprising a delay detection calculation unit that performs delay detection based on the partial band signal output from the partial band extraction unit and outputs a detection signal .   The said partial band extraction part extracts the said partial band signal so that the center frequency of the said partial band signal may become an integral multiple of the symbol frequency of the data currently transmitted. Data receiving device. The delay detection calculation unit includes:
A delay unit for outputting delayed by one symbol time in-phase component of the partial band signal the partial band extracting section outputs,
By multiplying the output of the delay unit in-phase component of the partial band signal the partial band extracting section outputs, a first multiplier for outputting the in-phase component data string,
By multiplying the output of the orthogonal component and the delay unit of the partial band signal the partial band extracting section outputs, a second multiplier for outputting a quadrature component data string,
The first low pass filter for outputting to remove high frequency components of the in-phase component data string output from the first multiplier,
And a second low-pass filter for outputting to remove high-frequency component of the quadrature component data string output from the second multiplier, the data receiving apparatus according to claim 3.   The partial band extraction unit extracts the partial band signal so that the number of samples in one symbol period is a multiple of 8 obtained by dividing the center frequency of the partial band signal to be extracted by the symbol frequency. The data receiving device according to claim 3. The partial band extraction unit extracts an even number of partial band signals,
The data receiving apparatus according to claim 2, wherein the partial band signals are paired with a positive and negative frequency equidistant from frequency 0 as a center frequency. The partial band extraction unit includes:
A complex filter, a first filtering equipment which obtains and outputs the convolution integral of the phase component of the transfer function of the sampling phase signal and the complex filter,
A complex filter, a second filtering equipment for obtaining the convolution integral of the quadrature component of the transfer function of the sampled quadrature signal and the complex filter,
A complex filter, the third filtering equipment for obtaining the convolution integral of the phase component of the transfer function of the sampled quadrature signal and the complex filter,
A complex filter, the fourth filtering equipment for obtaining the convolution integral of the quadrature component of the transfer function of the sampling phase signal and the complex filter,
A first subtractor for subtracting the signal output by the second filtering device from the signal the first filtering device outputs,
A first adder for adding the signal said signal to the first filtering device outputs the second filtering device outputs,
A second subtractor for subtracting the signal output from the fourth filtering unit from the signal the third filtering device outputs,
And a second adder the third said filtering device is a signal output from the fourth filtering device adds the signal output, the data receiving apparatus according to claim 6.   8. The partial band extraction unit according to claim 7, wherein the partial band extraction unit extracts the partial band signal so that a center frequency of the partial band signal is an integral multiple of a symbol frequency of data being transmitted. Data receiving device.   The partial band extraction unit extracts the partial band signal so that the number of samples in one symbol period is a multiple of 8 obtained by dividing the center frequency of the partial band signal to be extracted by the symbol frequency. The data receiving device according to claim 7. The partial band extraction unit includes:
First input selection for alternately selecting and outputting the sampled in-phase signal and the sampled quadrature signal every half of the sample period using the sampled in-phase signal and the sampled quadrature signal as input signals And
Second input selection for alternately selecting and outputting the sampled in-phase signal and the sampled quadrature signal every half of the sample period using the sampled in-phase signal and the sampled quadrature signal as input signals And
A complex filter, a first filtering equipment that performs convolution integration between the in-phase component of the transfer function of the signal and the complex filter to the first input selector and outputs,
A complex filter, a second filtering equipment that performs convolution integration between the orthogonal component of the signal and the transfer function of the complex filter to the second input selector outputs,
A first output selector that alternately outputs an output signal from the first filtering device that changes at a half period of the sampling period to the first output terminal and the second output terminal at a half period of the sampling period . And
A second output selector that alternately outputs an output signal from the second filtering device that changes at half the sampling period to the third output terminal and the fourth output terminal at half the sampling period . And
A first delay device for delaying a signal output from the first output terminal of the first output selector by a half of a sample period;
A second delayer which only delayed half the time of the third signal sample period is output from the output terminal of the second output selector,
A first subtractor for subtracting the signal output by the second delay unit from the signal of the first delay unit outputs,
A first adder for adding the signal signal and the second delay unit the first delay unit outputs are outputted,
A second subtractor for subtracting the signal output from the fourth output terminal of the second output selector from the signal output from the second output of the first output selector,
And a second adder for adding the signal output from the fourth output signal and the second output selector that is output from the second output terminal of the first output selector, The data receiving device according to claim 6.   11. The partial band extraction unit according to claim 10, wherein the partial band extraction unit extracts the partial band signal so that a center frequency of the partial band signal is an integral multiple of a symbol frequency of data being transmitted. Data receiving device.   The partial band extraction unit extracts the partial band signal so that the number of samples in one symbol period is a multiple of 8 obtained by dividing the center frequency of the partial band signal to be extracted by the symbol frequency. The data receiving device according to claim 10.   The data reception apparatus according to claim 2, wherein the delay detection calculation unit performs delay detection using the partial band signal output from the partial band extraction unit as an intermediate frequency signal.   2. The data receiving apparatus according to claim 1, wherein the modulated signal is a signal that can be demodulated by extracting at least one partial band from a frequency band of the modulated signal.   The data receiving apparatus according to claim 1, wherein the modulated signal is a spectrum-spread signal.   14. The data receiving apparatus according to claim 13, wherein the modulated signal is a spread spectrum signal using a chirp signal obtained by repeatedly sweeping the frequency of a sine wave at regular intervals as a spread signal. . A wireless communication equipment for receiving and processing a modulated wave signal that is phase-modulated,
Quadrature detection to the received modulated wave signal after frequency conversion, a frequency conversion circuits for outputting the in-phase and quadrature signals,
The in-phase and quadrature signals output from the frequency converting circuit as an input signal, and a data receiving equipment which outputs a detection signal,
And a phase decision processing equipment for processing by the phase determining detection signal the data receiving device outputs,
The data receiving device is:
And sampling said in-phase signal at every predetermined sampling period, a first sampler for outputting the sampled in-phase signal,
And sampling said quadrature signal at every said predetermined sampling period, a second sampler for outputting a sampled quadrature signal,
A center frequency is selected from frequency components included in the sampled in-phase signal output from the first sampler and the sampled quadrature signal output from the second sampler. extracting at least one partial band non-zero, the extracted sub-band signal is divided into in-phase and quadrature components, and a partial band extracting section for outputting as a partial band signal,
The data receiving apparatus based on the partial band signal the partial band extracting section outputs, you output a detection wave signal, a radio communication device. The radio communication apparatus according to claim 17, wherein the data receiving apparatus further includes a delay detection calculation unit that performs delay detection based on the partial band signal output from the partial band extraction unit and outputs a detection signal. The partial band extraction unit extracts a plurality of partial bands and outputs them as partial band signals,
The phase determination processing device selects and processes one of a plurality of data obtained by phase determination of a plurality of detection signals from the delay detection calculation unit, according to claim 18 . The wireless communication device described. The partial band extraction unit extracts a plurality of partial bands and outputs them as partial band signals,
It said phase determining processing equipment is characterized by generating the reception data based on a plurality of data obtained by a plurality of detection signals with a phase determined from the differential detection calculating unit, according to claim 1 8 Wireless communication device. The partial band extraction unit extracts a plurality of partial bands and outputs them as partial band signals,
It said phase determining processing equipment is characterized by parallel processing of the data obtained by the phase determining a plurality of detection signals from the differential detection calculating unit, the radio communication apparatus according to claim 1 8.

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