JP2003312516A5 - - Google Patents
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- JP2003312516A5 JP2003312516A5 JP2002122874A JP2002122874A JP2003312516A5 JP 2003312516 A5 JP2003312516 A5 JP 2003312516A5 JP 2002122874 A JP2002122874 A JP 2002122874A JP 2002122874 A JP2002122874 A JP 2002122874A JP 2003312516 A5 JP2003312516 A5 JP 2003312516A5
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【００２０】
請求項２の発明は、電動機制御値に基づいて電動機を駆動する電動機駆動手段と、直流電源と前記電動機駆動手段間に設けられ、電源電圧を昇圧する昇圧手段と、ＰＷＭ駆動信号を生成出力する昇圧制御手段とを備え、前記昇圧手段は、直流電源の出力端子に接続された昇圧用コイルと、同昇圧用コイルの出力端子に対して共に接続された第１スイッチング素子と第２スイッチング素子と、前記第２スイッチング素子の出力端子に接続された昇圧用コンデンサとを備え、前記両スイッチング素子の内少なくとも前記第１スイッチング素子を前記ＰＷＭ駆動することにより、前記直流電源から昇圧用コイルに供給される電流を制御し、前記昇圧用コンデンサに昇圧電圧を充電する電動パワーステアリング装置において、前記電動機の負荷状態を判定する負荷状態判定手段を設け、前記昇圧制御手段は、前記負荷状態判定手段の判定結果に応じて高負荷のときは、ＰＷＭ駆動信号のキャリア周波数を高周波数にして前記両スイッチング素子をＰＷＭ駆動し、低負荷のときは、ＰＷＭ駆動信号のキャリア周波数を低周波数にして前記両スイッチング素子をＰＷＭ駆動することを特徴とする電動パワーステアリング装置を要旨とするものである。[0020]
The invention according to claim 2 is a motor driving means for driving a motor based on a motor control value, a boosting means provided between a DC power supply and the motor driving means, for boosting a power supply voltage, and generating and outputting a PWM drive signal. And a boosting coil connected to the output terminal of the DC power supply, and a first switching element and a second switching element both connected to the output terminal of the boosting coil. And a boosting capacitor connected to an output terminal of the second switching element, wherein at least the first switching element of the two switching elements is PWM-driven to be supplied from the DC power supply to the boosting coil. Control of the electric current and charging the boosted capacitor with the boosted voltage, the load condition of the motor is Provided a constant loading state determining means, said boost control means, wherein when the determination result high load according to the load state determining means, PWM driving the two switching elements to the carrier frequency of the PWM drive signal to the high frequency and, when the low load, it is an gist an electric power steering apparatus characterized by the carrier frequency of the PWM driving signals in the low frequency PWM driving the two switching elements.
【００２１】
請求項３の発明は、電動機制御値に基づいて電動機を駆動する電動機駆動手段と、直流電源と前記電動機駆動手段間に設けられ、電源電圧を昇圧する昇圧手段と、ＰＷＭ駆動信号を生成出力する昇圧制御手段とを備え、前記昇圧手段は、直流電源の出力端子に接続された昇圧用コイルと、同昇圧用コイルの出力端子に対して共に接続された第１スイッチング素子と第２スイッチング素子と、前記第２スイッチング素子の出力端子に接続された昇圧用コンデンサとを備え、前記両スイッチング素子の内少なくとも前記第１スイッチング素子を前記ＰＷＭ駆動することにより、前記直流電源から昇圧用コイルに供給される電流を制御し、前記昇圧用コンデンサに昇圧電圧を充電する電動パワーステアリング装置において、前記電動機の負荷状態を判定する負荷状態判定手段を設け、前記昇圧制御手段は、前記負荷状態判定手段の判定結果に応じて高負荷のときは、ＰＷＭ駆動信号のキャリア周波数を高周波数にして前記両スイッチング素子を同期整流し、低負荷のときは、前記両スイッチング素子の内、第１スイッチング素子のみを、ＰＷＭ駆動信号のキャリア周波数を低周波数にして非同期整流することを特徴とする電動パワーステアリング装置を要旨とするものである。[0021]
The invention according to claim 3 is a motor driving means for driving a motor based on a motor control value, a boosting means provided between a DC power supply and the motor driving means, for boosting a power supply voltage, and generating and outputting a PWM driving signal. And a boosting coil connected to the output terminal of the DC power supply, and a first switching element and a second switching element both connected to the output terminal of the boosting coil. And a boosting capacitor connected to an output terminal of the second switching element, wherein at least the first switching element of the two switching elements is PWM-driven to be supplied from the DC power supply to the boosting coil. Control of the electric current and charging the boosted capacitor with the boosted voltage, the load condition of the motor is Provided a constant loading state determining means, said boost control means, in response to said load state determining means for determining the result in the high load, synchronous rectification the both switching elements of the carrier frequency in the high frequency of the PWM driving signal When the load is low, only the first switching element of the two switching elements is asynchronously rectified with the carrier frequency of the PWM drive signal as the low frequency. It is.
【０１１１】
Ｓ３０Ａでは、操舵トルクτが閾値τ０よりも大きいと、モータ６が高負荷であると判定されているため、ＰＷＭ駆動信号のキャリア周波数を高周波数にして第１トランジスタＱ１，第２トランジスタＱ２をＰＷＭ駆動する。[0111]
PWM In S30A, the steering torque τ is larger than the threshold .tau.0, since the motor 6 is determined to be a high load, the first transistor Q1 and the carrier frequency of the PWM drive signal to the high frequency, the second transistor Q2 To drive.
【０１１２】
又、Ｓ４０Ａでは、操舵トルクτが閾値τ０以下であると、モータ６が低負荷であると判定されているため、ＰＷＭ駆動信号のキャリア周波数を低周波数にして第１トランジスタＱ１，第２トランジスタＱ２をＰＷＭ駆動する。[0112]
Further, at S40A, it is determined that the motor 6 has a low load if the steering torque τ is equal to or less than the threshold value τ0, so the carrier frequency of the PWM drive signal is set to a low frequency to set the first transistor Q1 and the second transistor Q2. PWM drive.
【０１１３】
このように、モータ６が低負荷の場合、第１トランジスタＱ１，第２トランジスタＱ２を低周波数でＰＷＭ駆動すると、両トランジスタのスイッチングロスが減少する。すなわち、両トランジスタをＰＷＭ駆動でオンオフする場合、両トランジスタが同時にオンしないようにデッドタイムを設けている。低周波数でＰＷＭ駆動すると、一定時間に発現するデッドタイムが少なくなるため、スイッチングロスが少なくなる。このため、スイッチングロスによる両トランジスタの発熱を抑制することができ、この結果、昇圧回路１００の発熱を抑制できる。[0113]
As described above, when the motor 6 has a low load, when the first transistor Q1 and the second transistor Q2 are PWM-driven at a low frequency , the switching loss of both transistors is reduced. That is, when both transistors are turned on and off by PWM driving, a dead time is provided so that both transistors are not simultaneously turned on. When PWM driving is performed at a low frequency , the switching loss is reduced because the dead time developed in a fixed time is reduced. Therefore, the heat generation of both transistors due to the switching loss can be suppressed, and as a result, the heat generation of the booster circuit 100 can be suppressed.
【０１１４】
一方、モータ６が高負荷の場合は、第１トランジスタＱ１，第２トランジスタＱ２を高周波数でＰＷＭ駆動しているため、各トランジスタのオンオフ時のリップル電圧を小さくできる。[0114]
On the other hand, when the motor 6 has a high load, since the first transistor Q1 and the second transistor Q2 are PWM-driven at high frequency , the ripple voltage of each transistor can be reduced.
【０１１５】
なお、リップル電圧の大きさは、ＰＷＭ駆動信号のキャリア周期（すなわちキャリア周波数）に依存しており、すなわち、ＰＷＭ駆動信号のキャリア周波数が高周波数であれば、リップル電圧が小さく、低周波数であれば、リップル電圧が大きくなる。そして、モータ６はリップル電圧があると、電圧が変動しているため、その影響が出る。[0115]
The size of the ripple voltage is dependent on the carrier period of the PWM drive signals (i.e., carrier frequency), i.e., if the carrier frequency is high frequency of the PWM driving signal, the ripple voltage small, at low frequencies there For example, the ripple voltage increases. When the motor 6 has a ripple voltage, the voltage fluctuates, so that the influence is exerted.
【０１１６】
従って、高周波数で両トランジスタをＰＷＭ駆動すると、モータ６は高負荷状態、すなわち、操舵トルクτが出ている状態であるため、リップル電圧が抑制されているほど、操舵フィーリングの悪化を防止できる。[0116]
Therefore, when both transistors are PWM-driven at a high frequency , the motor 6 is in a high load state, that is, a state in which the steering torque τ is being output, so the deterioration of the steering feeling can be prevented as the ripple voltage is suppressed. .
【０１１７】
一方、モータ６が低負荷の場合は、モータ６の電力消費が少なく、特に、無負荷の場合は、モータ６は電力消費がないため、ＰＷＭ駆動信号のキャリア周期を長くし（低周波数）て、両トランジスタをＰＷＭ駆動している。すなわち、この場合、操舵トルクτが出ていない状態（操舵していない状態）であり、このため、操舵フィーリングに影響が出ることはない。[0117]
On the other hand, when the motor 6 has a low load, the power consumption of the motor 6 is small, and in particular, when no load, the motor 6 does not consume any power, so the carrier period of the PWM drive signal is lengthened (low frequency ) , Both transistors are PWM driven. That is, in this case, the steering torque τ is not output (in a non-steering state), and therefore the steering feeling is not affected.
【０１１８】
なお、ＣＰＵ２１は、昇圧制御手段、負荷状態判定手段に相当する。
従って、第４実施形態では、下記の特徴がある。
（１） 第４実施形態では、ＣＰＵ２１（昇圧制御手段）は、モータ６が高負荷のときは、ＰＷＭ駆動信号のキャリア周波数を高周波数にして第１トランジスタＱ１，第２トランジスタＱ２の両トランジスタ（両スイッチング素子）をＰＷＭ駆動するようにした。又、ＣＰＵ２１は、モータ６が低負荷のときは、ＰＷＭ駆動信号のキャリア周波数を低周波数にして第１トランジスタＱ１，第２トランジスタＱ２の両トランジスタをＰＷＭ駆動するようにした。[0118]
The CPU 21 corresponds to boost control means and load state determination means.
Therefore, the fourth embodiment has the following features.
(1) In the fourth embodiment, when the motor 6 has a high load, the CPU 21 (step-up control means) sets the carrier frequency of the PWM drive signal to a high frequency to set both the first transistor Q1 and the second transistor Q2 together. The two switching elements are driven by PWM. Further, when the motor 6 has a low load, the CPU 21 sets the carrier frequency of the PWM drive signal to a low frequency to perform PWM driving of both the first transistor Q1 and the second transistor Q2.
【０１１９】
この結果、低周波数でＰＷＭ駆動すると、一定時間に発現するデッドタイムが少なくなるため、スイッチングロスが少なくなり、スイッチングロスによる両トランジスタの発熱が少なくなり、昇圧回路１００の発熱を抑制できる。[0119]
As a result, when PWM driving is performed at a low frequency , the dead time developed in a fixed time is reduced, the switching loss is reduced, the heat generation of both transistors due to the switching loss is reduced, and the heat generation of the booster circuit 100 can be suppressed.
【０１２０】
又、モータ６は高負荷状態では、ＰＷＭ駆動信号のキャリア周波数を高周波数にして両トランジスタをＰＷＭ駆動しているため、リップル電圧が抑制され、操舵フィーリングの悪化を防止できる。[0120]
Further, the motor 6 is in the high load condition, since the carrier frequency of the PWM drive signals have both transistors in the high-frequency PWM-driven, the ripple voltage can be suppressed, thereby preventing deterioration of the steering feel.
【０１２１】
なお、第４実施形態を、下記のように変更してもよい。
（Ａ） 第４実施形態のフローチャートのうち、Ｓ１０、Ｓ２０を第２実施形態のＳ１０Ａ、Ｓ２０Ａ（図８参照）にそれぞれ変更すること。このようにしても、モータ６の低負荷、高負荷に応じて、ＰＷＭ駆動信号のキャリア周波数をそれぞれ低周波数、高周波数にして両トランジスタをＰＷＭ駆動することができ、その結果、第２実施形態の上記（１）の効果を奏する。[0121]
The fourth embodiment may be modified as follows.
(A) In the flowchart of the fourth embodiment, S10 and S20 should be changed to S10A and S20A (see FIG. 8) of the second embodiment, respectively. Even in this case, both the transistors can be PWM driven with the carrier frequency of the PWM drive signal set to low frequency and high frequency according to the low load and high load of the motor 6, and as a result, the second embodiment The effect of (1) above is exerted.
【０１２２】
（Ｂ） 第４実施形態のフローチャートのうち、Ｓ１０、Ｓ２０を第３実施形態のＳ１０Ｂ、Ｓ２０Ｂ（図９参照）にそれぞれ変更すること。このようにしても、モータ６の低負荷、高負荷に応じて、ＰＷＭ駆動信号のキャリア周波数をそれぞれ低周波数、高周波数にして両トランジスタをＰＷＭ駆動することができ、その結果、第３実施形態の上記（１）の効果を奏する。[0122]
(B) In the flowchart of the fourth embodiment, S10 and S20 should be changed to S10B and S20B (see FIG. 9) of the third embodiment, respectively. Even in this case, both the transistors can be PWM driven with the carrier frequency of the PWM drive signal set to low frequency and high frequency according to the low load and high load of the motor 6, and as a result, the third embodiment The effect of (1) above is exerted.
【０１２４】
Ｓ４０Ｂでは、操舵トルクτが閾値τ０以下であると、モータ６が低負荷であると判定されているため、ＰＷＭ駆動信号のキャリア周波数を低周波数にして第１トランジスタＱ１のみを非同期整流する。[0124]
In S40B, since it is determined that the motor 6 has a low load when the steering torque τ is equal to or less than the threshold value τ0, only the first transistor Q1 is asynchronously rectified with the carrier frequency of the PWM drive signal being a low frequency .
【０１２９】
さらに、第５実施形態では、モータ６が低負荷の場合、ＰＷＭ駆動信号のキャリア周波数を低周波数にしているため、スイッチングロスが少なくなり、スイッチングロスによるトランジスタの発熱が少なくなり、昇圧回路１００の発熱を抑制できる。[0129]
Furthermore, in the fifth embodiment, when the motor 6 has a low load, the carrier frequency of the PWM drive signal is set to a low frequency , so the switching loss is reduced and the heat generation of the transistor due to the switching loss is reduced. Heat generation can be suppressed.
【０１３０】
一方、モータ６が高負荷の場合は、第１トランジスタＱ１，第２トランジスタＱ２を高周波数で同期整流しているため、各トランジスタのオンオフ時のリップル電圧を小さくできる。[0130]
On the other hand, when the motor 6 has a high load, since the first transistor Q1 and the second transistor Q2 are synchronously rectified at a high frequency , the ripple voltage of each transistor can be reduced.
【０１３１】
従って、高周波数で両トランジスタを同期整流すると、モータ６は高負荷状態、すなわち、操舵トルクτが出ている状態であるため、リップル電圧が抑制されているほど、操舵フィーリングの悪化を防止できる。[0131]
Therefore, when both transistors are synchronously rectified at a high frequency , the motor 6 is in a high load state, that is, a state in which the steering torque τ is being outputted, so the deterioration of the steering feeling can be prevented as the ripple voltage is suppressed. .
【０１３２】
一方、モータ６が低負荷の場合は、モータ６の電力消費が少なく、特に、無負荷の場合は、モータ６は電力消費がないため、ＰＷＭ駆動信号のキャリア周期を長くし（低周波数）て、両トランジスタを同期整流している。すなわち、この場合、操舵トルクτが出ていない状態（操舵していない状態）であり、このため、操舵フィーリングに影響が出ることはない。[0132]
On the other hand, when the motor 6 has a low load, the power consumption of the motor 6 is small, and in particular, when no load, the motor 6 does not consume any power, so the carrier period of the PWM drive signal is lengthened (low frequency ) , Both transistors are synchronously rectified. That is, in this case, the steering torque τ is not output (in a non-steering state), and therefore the steering feeling is not affected.
【０１３３】
なお、ＣＰＵ２１は、昇圧制御手段、負荷状態判定手段に相当する。
従って、第５実施形態では、下記の特徴がある。
（１） 第５実施形態では、ＣＰＵ２１（昇圧制御手段）は、モータ６が高負荷のときは、ＰＷＭ駆動信号のキャリア周波数を高周波数にして第１トランジスタＱ１，第２トランジスタＱ２の両トランジスタ（両スイッチング素子）を同期整流するようにした。又、ＣＰＵ２１は、モータ６が低負荷のときは、ＰＷＭ駆動信号のキャリア周波数を低周波数にして第１トランジスタＱ１を非同期整流するようにした。[0133]
The CPU 21 corresponds to boost control means and load state determination means.
Therefore, the fifth embodiment has the following features.
(1) In the fifth embodiment, when the motor 6 has a high load, the CPU 21 (step-up control means) sets the carrier frequency of the PWM drive signal to a high frequency to set both the first transistor Q1 and the second transistor Q2 together. Synchronous switching of both switching elements). Further, when the motor 6 has a low load, the CPU 21 makes the carrier frequency of the PWM drive signal a low frequency to asynchronously rectify the first transistor Q1.
【０１３４】
この結果、低周期で非同期整流すると、スイッチングロスによるトランジスタの発熱が少なくなり、昇圧回路１００の発熱を抑制できる。
又、モータ６は高負荷状態では、ＰＷＭ駆動信号のキャリア周波数を高周波数で両トランジスタを同期整流しているため、リップル電圧が抑制され、操舵フィーリングの悪化を防止できる。[0134]
As a result, when the asynchronous rectification is performed in a low cycle, the heat generation of the transistor due to the switching loss is reduced, and the heat generation of the booster circuit 100 can be suppressed.
Further, in the high load state of the motor 6, the carrier frequency of the PWM drive signal is synchronously rectified at high frequency to both transistors, so that the ripple voltage is suppressed and the deterioration of the steering feeling can be prevented.
【０１３７】
なお、本発明の実施形態は以下のように変更してもよい。
○ 前記第１実施形態〜第３実施形態では、モータ６が低負荷の場合は、Ｓ４０において、第１トランジスタＱ１をオフした。これに代えてＳ４０において、第１トランジスタＱ１のみをＰＷＭ制御し、第２トランジスタＱ２を全オフとする非同期整流で行ってもよい。なお、この場合、第５実施形態と異なり、低負荷時も高負荷時もＰＷＭ駆動信号のキャリア周期（すなわち、キャリア周波数）は同じ周期（すなわち、同じ周波数）にする。[0137]
The embodiment of the present invention may be modified as follows.
In the first to third embodiments, when the motor 6 has a low load, the first transistor Q1 is turned off in S40. Instead of this, in S40, asynchronous rectification may be performed in which only the first transistor Q1 is subjected to PWM control and the second transistor Q2 is completely turned off. In this case, unlike in the fifth embodiment, the carrier period (that is, the carrier frequency) of the PWM drive signal is made the same period (that is, the same frequency) at the time of low load and high load.
【０１３８】
こうすると、第５実施形態において、モータ６が低負荷の場合、ＰＷＭ駆動信号のキャリア周波数を低周波数にしたことによるトランジスタの発熱抑制効果はない。[0138]
In this case, in the fifth embodiment, when the motor 6 has a low load, there is no heat generation suppressing effect of the transistor due to the carrier frequency of the PWM drive signal being set to the low frequency .
Claims (6)
前記電動機の負荷状態を判定する負荷状態判定手段を設け、
前記昇圧制御手段は、前記負荷状態判定手段の判定結果に応じて高負荷のときは、第１スイッチング素子及び第２スイッチング素子を同期整流し、低負荷のときは、前記両スイッチング素子の内、少なくとも第１スイッチング素子をオフ制御し、又は第１スイッチング素子のみをＰＷＭ制御して非同期整流することを特徴とする電動パワーステアリング装置。Motor driving means for driving the motor based on the motor control value; boosting means provided between the DC power supply and the motor driving means for boosting the power supply voltage; and boost control means for generating and outputting a PWM drive signal. The boosting means includes a boosting coil connected to an output terminal of a DC power supply, a first switching element and a second switching element both connected to an output terminal of the boosting coil, and the second switching element. And a step-up capacitor connected to the output terminal, wherein at least the first switching element of the two switching elements is PWM-driven to control the current supplied from the DC power supply to the step-up coil; In an electric power steering apparatus for charging a boosted voltage to a boosting capacitor,
Load state determination means for determining the load state of the motor is provided;
The boost control means synchronously rectifies the first switching element and the second switching element when the load is high according to the determination result of the load state determination means, and when the load is low, of the two switching elements, An electric power steering apparatus characterized in that at least a first switching element is turned off, or only a first switching element is PWM controlled to perform asynchronous rectification.
前記電動機の負荷状態を判定する負荷状態判定手段を設け、
前記昇圧制御手段は、前記負荷状態判定手段の判定結果に応じて高負荷のときは、ＰＷＭ駆動信号のキャリア周波数を高周波数にして前記両スイッチング素子をＰＷＭ駆動し、低負荷のときは、ＰＷＭ駆動信号のキャリア周波数を低周波数にして前記両スイッチング素子をＰＷＭ駆動することを特徴とする電動パワーステアリング装置。Motor driving means for driving the motor based on the motor control value; boosting means provided between the DC power supply and the motor driving means for boosting the power supply voltage; and boost control means for generating and outputting a PWM drive signal. The boosting means includes a boosting coil connected to an output terminal of a DC power supply, a first switching element and a second switching element both connected to an output terminal of the boosting coil, and the second switching element. And a step-up capacitor connected to the output terminal, wherein at least the first switching element of the two switching elements is PWM-driven to control the current supplied from the DC power supply to the step-up coil; In an electric power steering apparatus for charging a boosted voltage to a boosting capacitor,
Load state determination means for determining the load state of the motor is provided;
The step-up control means causes the carrier frequency of the PWM drive signal to be a high frequency when the load is high according to the determination result of the load state determination means, and PWM drives the switching elements while the load is low. An electric power steering apparatus characterized in that the carrier frequency of a drive signal is set to a low frequency to drive both switching elements by PWM.
前記電動機の負荷状態を判定する負荷状態判定手段を設け、
前記昇圧制御手段は、前記負荷状態判定手段の判定結果に応じて高負荷のときは、ＰＷＭ駆動信号のキャリア周波数を高周波数にして前記両スイッチング素子を同期整流し、低負荷のときは、前記両スイッチング素子の内、第１スイッチング素子のみを、ＰＷＭ駆動信号のキャリア周波数を低周波数にして非同期整流することを特徴とする電動パワーステアリング装置。Motor driving means for driving the motor based on the motor control value; boosting means provided between the DC power supply and the motor driving means for boosting the power supply voltage; and boost control means for generating and outputting a PWM drive signal. The boosting means includes a boosting coil connected to an output terminal of a DC power supply, a first switching element and a second switching element both connected to an output terminal of the boosting coil, and the second switching element. And a step-up capacitor connected to the output terminal, wherein at least the first switching element of the two switching elements is PWM-driven to control the current supplied from the DC power supply to the step-up coil; In an electric power steering apparatus for charging a boosted voltage to a boosting capacitor,
Load state determination means for determining the load state of the motor is provided;
The step-up control means makes the carrier frequency of the PWM drive signal a high frequency when the load is high according to the determination result of the load state determination means, and synchronously rectifies both switching elements, and when the load is low, the step An electric power steering apparatus characterized by asynchronously rectifying only the first switching element of the two switching elements with the carrier frequency of the PWM drive signal as a low frequency .
前記負荷状態判定手段は、前記操舵トルク検出手段が検出した操舵トルクが小のときは、電動機の負荷状態が低負荷であると判定し、操舵トルクが大のときは電動機の負荷状態が高負荷であると判定することを特徴とする請求項１乃至請求項３のうちいずれか１項に記載の電動パワーステアリング装置。A steering torque detecting means for detecting a steering torque;
The load state determination means determines that the load state of the motor is low when the steering torque detected by the steering torque detection means is small, and the load state of the motor is high when the steering torque is large. The electric power steering apparatus according to any one of claims 1 to 3, wherein it is determined that
前記負荷状態判定手段は、前記電動機回転数推定手段が推定した回転数が小のときは、電動機の負荷状態が低負荷であると判定し、回転数が大のときは、電動機の負荷状態が高負荷であると判定することを特徴とする請求項１乃至請求項３のうちいずれか１項に記載の電動パワーステアリング装置。Motor rotation speed estimation means for estimating the rotation speed of the motor;
The load state determination means determines that the load state of the motor is low when the rotation speed estimated by the motor rotation speed estimation means is small, and when the rotation speed is large, the load state of the motor is The electric power steering apparatus according to any one of claims 1 to 3, wherein it is determined that the load is high.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2002122874A JP3805714B2 (en) | 2002-04-24 | 2002-04-24 | Electric power steering device |
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2002122874A JP3805714B2 (en) | 2002-04-24 | 2002-04-24 | Electric power steering device |
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| JP2003312516A JP2003312516A (en) | 2003-11-06 |
| JP2003312516A5 true JP2003312516A5 (en) | 2005-01-06 |
| JP3805714B2 JP3805714B2 (en) | 2006-08-09 |
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| JP2002122874A Expired - Fee Related JP3805714B2 (en) | 2002-04-24 | 2002-04-24 | Electric power steering device |
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| JP2008245348A (en) * | 2007-03-26 | 2008-10-09 | Fujitsu Ten Ltd | Device and method for controlling booster circuit |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH0753508B2 (en) * | 1987-08-12 | 1995-06-07 | 株式会社日立製作所 | Electric power steering control system |
| JP3205651B2 (en) * | 1993-09-07 | 2001-09-04 | ティーアールダブリュ オートモーティブ ジャパン株式会社 | Electric power steering device with power supply voltage control device |
| JPH08127350A (en) * | 1994-10-31 | 1996-05-21 | Jidosha Kiki Co Ltd | Power steering system for vehicle |
| JPH08127352A (en) * | 1994-10-31 | 1996-05-21 | Jidosha Kiki Co Ltd | Power steering system for vehicle |
| JPH11278289A (en) * | 1998-03-27 | 1999-10-12 | Kayaba Ind Co Ltd | Electric power steering device |
| JP3675692B2 (en) * | 2000-03-17 | 2005-07-27 | 光洋精工株式会社 | Electric power steering device |
| JP2002098708A (en) * | 2000-09-25 | 2002-04-05 | Toyoda Mach Works Ltd | Device and method for measuring pulse signal characteristics, and control unit for electric power steering |
| JP3705166B2 (en) * | 2001-07-10 | 2005-10-12 | 三菱電機株式会社 | Steering control device |
| JP3865224B2 (en) * | 2002-03-15 | 2007-01-10 | 株式会社デンソー | Electric power steering device |
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2002
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