JP2003032009A - Nonradioactive dielectric line and millimeter wave transmitter-receiver - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide a nonradioactive dielectric line that can easily be manufactured by increasing a permissible range of an interval between end faces of dielectric line parts when the end faces of a plurality of the dielectric line parts are opposed and the dielectric line parts are electromagnetically coupled with each other. SOLUTION: In the nonradioactive dielectric line configured to interpose the dielectric line 22 between parallel flat conductors 21 and 23 placed at an interval of a half the wavelength of a high frequency signal or below, the dielectric line 22 is configured in a way that a plurality of the dielectric line parts 22a, 22b are approached and the end faces of the dielectric line parts 22a, 22b are opposed to each other resulting in being electromagnetically coupled with each other, and a projection is formed to one of the end faces of the dielectric line parts 22a, 22b opposed to each other and a recessed part 25 to which the projection 24 is inserted is formed to the other end face.

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a non-radiative dielectric line used in a high frequency band such as a millimeter wave,
The present invention relates to a non-radiative dielectric line that is preferably used by being incorporated in a microwave integrated circuit, a millimeter wave integrated circuit, a millimeter wave radar module, and the like, and a non-radiative dielectric line type millimeter wave integrated circuit, millimeter wave radar. The present invention relates to a millimeter wave transceiver such as a module.

[0002]

2. Description of the Related Art Conventional non-radiative dielectric lines for transmitting high-frequency signals such as microwaves and millimeter waves
ctric Waveguide, hereinafter referred to as NRD guide) S1
The basic configuration of is shown in FIG. As shown in the figure, the dielectric line 12 having a rectangular cross section is arranged between the parallel plate conductors 11 and 13 arranged in parallel at a predetermined interval. Is less than a half of the wavelength of the high frequency signal in the air, noise is prevented from entering the dielectric line 12 from the outside and the high frequency signal is not emitted to the outside. A high frequency signal can be propagated by.

When a high frequency transmitter / receiver such as a millimeter wave transmitter / receiver is constructed using such an NRD guide, a plurality of dielectric line portions are made to have their end faces opposed to each other in order to facilitate fabrication. The applicant of the present application has proposed that a dielectric line having a complicated shape having a curved portion is formed by continuously arranging at predetermined intervals and electromagnetically connecting the same (see Japanese Patent Laid-Open No. 2001-111131). An NRD guide S having such a structure is shown in FIG. In the figure, 1,
Reference numeral 3 is a parallel plate conductor arranged in parallel at an interval of ½ or less of the wavelength of the high frequency signal, and 2 is a dielectric line. The dielectric line 2 is composed of a plurality of dielectric line portions 2a, 2b, 2c, and the end faces thereof are arranged to face each other.
The distance between the end faces is one eighth or less of the wavelength of the high frequency signal.

[0004]

However, in the above-mentioned conventional NRD guide S, the distance L when the end surfaces of the plurality of dielectric line portions 2a to 2c are arranged facing each other is as follows.
It must be ⅛ or less of the wavelength of the high frequency signal used, and the higher the frequency, the smaller the interval L. With such a configuration, when using the short dielectric line portions 2a to 2c whose manufacturing dimensions are likely to vary, it is difficult to keep the actual distance L within 1/8 of the wavelength. Further, there is a problem that the shift in the lateral direction perpendicular to the transmission direction of the high frequency signal is likely to be large. Furthermore, the dielectric line portion 2
If fine dimensional control is attempted in order to suppress dimensional variations of a to 2c, there is a problem that the manufacturing cost increases and it cannot be put to practical use.

Therefore, the present invention has been completed in view of the above circumstances, and an object thereof is to shift the distance between the end faces when a plurality of dielectric line portions are electromagnetically connected with the end faces facing each other. By increasing the permissible range, the transmission characteristics of high frequency signals can be improved, and a dielectric line having a complicated shape can be easily constructed.

[0006]

The non-radiative dielectric line of the present invention is a non-radiative line formed by interposing a dielectric line between parallel flat plate conductors arranged at intervals equal to or smaller than ½ of the wavelength of a high-frequency signal. In the dielectric line, the dielectric line is configured such that end faces of a plurality of dielectric line parts are closely arranged and face each other so as to be electromagnetically coupled, and one of the facing end faces of the plurality of dielectric line parts is formed. A projection is formed on the end surface of the and the recess is formed on the other end surface into which the projection is inserted.

According to the present invention, according to the above structure, the protrusion formed on one of the facing end faces of the plurality of dielectric line portions is inserted into the recess formed on the other end face or is close to the recess. Therefore, the distance between the protrusion and the concave portion and the distance between the protrusion and the end surface facing each other are sure to be 8 wavelengths.
It is less than one-third. As a result, it is possible to increase the permissible range of the shift in the transmission direction and the lateral direction between the end faces facing each other of the plurality of dielectric line portions. The dielectric line can be easily constructed.

In the present invention, preferably, the shape of the dielectric line portion in a cross section perpendicular to the transmission direction of the high frequency signal is a substantially quadrangle, and the shape of the protrusion in the cross section is a height or a width of the substantially quadrangle. It is characterized in that it has a small size.

According to the present invention, the electromagnetic field distributions in the LSM mode and the LSE mode tend to be symmetrical in the vertical and horizontal directions, and the transmission characteristics in those modes are improved due to the above configuration. Further, the dielectric line portion can be easily manufactured by a press molding method or the like.

In the present invention, preferably, the center of the dielectric line portion in the cross section and the center of the protrusion in the cross section are substantially coincident with each other, and the center of the dielectric line portion in the cross section is the same as the center of the dielectric line portion in the cross section. It is characterized in that the center of the recess in the cross section substantially coincides.

According to the present invention, with the above-described structure, the facing end faces of the plurality of dielectric line portions can be arranged facing each other with almost no lateral shift, and as a result, the LSM can be arranged.
The electromagnetic field distributions of the mode and the LSE mode are symmetrical in the vertical and horizontal directions, and the transmission loss in the LSM mode or the LSE mode can be suppressed to a low level.

In the millimeter wave transceiver of the present invention, a high frequency diode oscillator is attached to one end between parallel plate conductors arranged at intervals of ½ or less of the wavelength of the millimeter wave signal, and output from the high frequency diode oscillator. A first dielectric line for propagating the generated millimeter wave signal, and a bias voltage application direction are arranged so as to match the electric field direction of the millimeter wave signal,
A variable-capacitance diode that outputs the millimeter-wave signal as a millimeter-wave signal for transmission by frequency-modulating the millimeter-wave signal by periodically controlling the bias voltage, and the first dielectric line are close to each other so that one end side is electromagnetically coupled. A second dielectric line that is arranged or has one end joined to propagate a part of the millimeter-wave signal to the mixer side, and a predetermined peripheral portion of a ferrite plate arranged in parallel with the parallel plate conductor. The millimeter wave input from one of the connecting portions, which has a first connecting portion, a second connecting portion, and a third connecting portion which are arranged at intervals and serve as input and output ends of the millimeter wave signal, respectively. A circulator that outputs a signal from another adjacent connecting portion in the plane of the ferrite plate in the clockwise or counterclockwise direction, wherein the first dielectric line has an output end for the millimeter wave signal at the first end. Connection A circulator joined to the circulator, a third dielectric line joined to the second connection portion of the circulator, which propagates the millimeter wave signal and has a transmission / reception antenna at the tip, and the reception / transmission antenna receives the signal. A fourth dielectric line that propagates through the third dielectric line and propagates a received wave that is output from the third connection section of the circulator to the mixer side, a middle part of the second dielectric line, and the second dielectric line. And a mixer section which is formed by electromagnetically coupling or joining the midway of the dielectric line of 4 and mixing a part of the millimeter wave signal and the received wave to generate an intermediate frequency signal. In the wave transceiver, at least one of the first to fourth dielectric lines constitutes the non-radiative dielectric line of the present invention.

The present invention, which has the above-described structure, is easy to manufacture and has an excellent high-frequency signal transmission characteristic, and has an increased detection distance when applied to a millimeter wave radar or the like.

A high frequency diode oscillator is attached to one end between parallel plate conductors arranged at intervals of ½ or less of the wavelength of the millimeter wave signal, and propagates the millimeter wave signal output from the high frequency diode oscillator. 1 dielectric line,
A variable capacitor that is arranged so that a bias voltage application direction matches the electric field direction of the millimeter wave signal, and outputs the millimeter wave signal as a millimeter wave signal for transmission that is frequency-modulated by periodically controlling the bias voltage. A second dielectric line that is disposed close to or is joined to the diode and the first dielectric line so that one end side is electromagnetically coupled to propagate a part of the millimeter wave signal to the mixer side. And a first connecting portion, a second connecting portion, and a first connecting portion which are arranged at a predetermined interval on a peripheral portion of a ferrite plate arranged in parallel with the parallel plate conductor and serve as input / output ends of the millimeter wave signal. Circular having three connecting portions and allowing the millimeter wave signal input from one of the connecting portions to be output from another connecting portion which is adjacent in the clockwise or counterclockwise direction in the plane of the ferrite plate. And a circulator to which the first connecting portion is connected to an output end of the millimeter wave signal of the first dielectric line, and a circulator connected to the second connecting portion of the circulator, And a third dielectric line having a transmitting antenna at the tip,
It is connected to a fourth dielectric line having a receiving antenna at the tip and a mixer at the other end, and the third connecting part of the circulator, and propagates a millimeter wave signal received and mixed by the transmitting antenna. At the same time, the fifth dielectric line that attenuates the millimeter wave signal at the non-reflective end provided at the tip, and the middle of the second dielectric line and the middle of the fourth dielectric line are brought close to each other. A millimeter wave transmitter / receiver provided with a mixer section for electromagnetically coupling or joining the millimeter wave signals and mixing a part of the millimeter wave signals with a received wave to generate an intermediate frequency signal. At least one of the dielectric lines constitutes the above-mentioned non-radiative dielectric line of the present invention.

The present invention, which has the above-described structure, is easy to manufacture and has excellent high-frequency signal transmission characteristics. When it is applied to a millimeter-wave radar or the like, a millimeter-wave signal for transmission passes through a circulator. No noise is mixed into the mixer, and as a result, the noise of the received signal is reduced and the detection distance is increased.

[0016]

BEST MODE FOR CARRYING OUT THE INVENTION The NRD guide of the present invention will be described in detail below. FIG. 1 shows an example of an embodiment of an NRD guide of the present invention, and FIGS.
Another example of the embodiment of the D guide will be described. In these figures, 21 and 23 are 1/2 of the wavelength of the high frequency signal.
Parallel plate conductors are arranged in parallel at the following intervals, 22 is a dielectric line, 22a and 22b are dielectric line parts, and 24 is formed on the end face of the dielectric line part 22a facing the end face of the dielectric line part 22b. The protrusion 25 is the dielectric line portion 22.
It is a recess provided on the end face of b.

In the present invention, the dielectric line 22 is configured such that the end surfaces of the plurality of dielectric line portions 22a and 22b are closely arranged and face each other so as to be electromagnetically coupled, and the dielectric line portions 22a and 22b are made to face each other. A protrusion 24 is formed on one end face of the facing end faces, and a recess 25 is formed on the other end face so that the protrusion 24 can be inserted. In this case, the distance between the end faces of the dielectric line portions 22a and 22b is preferably about 1/8 or less of the wavelength of the high frequency signal, and electromagnetic coupling and high frequency signal transmission characteristics are good.

Regarding the shape of the protrusion 24, the shape of the dielectric line portion 22a in a cross section perpendicular to the transmission direction of the high frequency signal is substantially quadrangular, and the shape of the protrusion 24 in that cross section is the cross sectional shape of the dielectric line portion 22a. It is preferable that the height or width of the substantially quadrangle is reduced to a substantially quadrangle shape. This allows the LSM propagating in the dielectric line 22.
The electromagnetic field distributions in the modes and the LSE mode are less likely to be disturbed, and the transmission loss in the LSM mode and the LSE mode is reduced.

In FIG. 1, the thickness of the projection 24 in the vertical direction is smaller than the thickness of the dielectric line 22, and the cross section of the projection 24 in a cross section perpendicular to the transmission direction is rectangular. . In FIG. 4, the width of the protrusion 24 is the width of the dielectric line 22.
The width of the projection 24 is smaller than the width of the projection 24, and the cross-sectional shape of the projection 24 in a cross section perpendicular to the transmission direction is rectangular. With these configurations, the dielectric line portion 22
The allowable range of the gap L between the end faces of a and 22b is increased, and the transmission characteristics of the LSM mode and the LSE mode are improved. Further, the dielectric line portions 22a and 22b can be easily manufactured by a press molding method or the like.

In FIGS. 5 and 6, the center of the dielectric line portion 22a in the cross section perpendicular to the transmission direction and the center of the projection 24 in the cross section perpendicular to the transmission direction are substantially equal to each other in FIGS. 1 and 4, respectively. In addition, the center of the dielectric line portion 22b in the cross section perpendicular to the transmission direction and the center of the recess 25 in the cross section perpendicular to the transmission direction are substantially aligned with each other. As a result, the dielectric line portion 22
The opposing end surfaces of a and 22b can be arranged to face each other with almost no lateral shift, and the electromagnetic field distributions of the LSM mode and the LSE mode are symmetrical in the vertical direction and the lateral direction. Propagation loss can be suppressed to a lower level.

The shape of the protrusion 24 does not need to be uniform in vertical thickness and lateral width, and the vertical thickness and lateral width can be adjusted toward the tip along the transmission direction. The shape may be such that the width gradually decreases.

The projection length of the protrusion 24 is preferably 1/20 to 1/2 of the wavelength of the high frequency signal, and is 1/20.
If it is less than the above, the effect of the present invention obtained by providing the protrusions 24 becomes small, and if it exceeds ½, the protrusions are too long to make the production difficult, and it becomes difficult to maintain a high yield in the production. .

1 and 5, the vertical thickness of the projection 24 is preferably 1/5 to 4/5 of the height of the dielectric line 22, and if the thickness is less than 1/5, the projection 24 will be thicker. The effect of the present invention obtained by providing the above becomes small, and when it exceeds 4/5, it becomes difficult to form the concave portion 25 into which the projection 24 can be inserted.

4 and 6, the lateral width of the protrusion 24 is preferably 1/5 to 4/5 of the width of the dielectric line 22, and if it is less than 1/5, the protrusion 24 is provided. As a result, the effect of the present invention obtained becomes small, and if it exceeds 1/5, it becomes difficult to form the concave portion 25 into which the protrusion 24 can be inserted.

The shape of the recess 25 formed on the end surface of the dielectric line portion 22b may be any shape as long as the projection 24 is inserted, but it is preferable that the projection 25 has an inner dimension slightly larger than the outer dimension of the projection 24. . In this case, the electromagnetic coupling property is improved, and the transmission characteristics of high frequency signals are improved.

In the present invention, the material of the dielectric line 22 is a resin-based dielectric material such as Teflon (registered trademark) or polystyrene, or cordierite (2M) having a low relative dielectric constant.
Ceramics such as gO.2Al ₂ O ₃ .5SiO ₂ ) ceramics, alumina (Al ₂ O ₃ ) ceramics, glass ceramics, forsterite (2MgO.SiO ₂ ) ceramics are preferable, and these have low loss in a high frequency band. In particular, the cordierite ceramics are preferable in terms of dielectric properties, workability, strength, miniaturization, reliability, and the like. Furthermore, for cordierite ceramics, Y, La, Ce, Pr, Nd, Sm, E
By containing at least one element selected from u, Dy, Ho, Er, Tm, Yb, and Lu, the dielectric characteristics such as Q value can be improved and a high-frequency signal can be transmitted with low loss.

The cordierite ceramics for the dielectric line 22 of the present invention is manufactured as follows. As the raw material powder, for example, MgCO ₃ powder, Al ₂ O ₃ powder, Si
Using O ₂ powder, these were weighed at a predetermined ratio, wet-mixed and then dried, and the mixture was dried in the atmosphere at 1100 to 100
After calcination at 1300 ° C., it is pulverized into powder. It is obtained by adding an appropriate amount of a resin binder to the obtained powder and shaping the powder, and firing the shaped body in the atmosphere at 1300 to 1450 ° C.

The raw material powder consisting of the elements of Mg, Al and Si contained in the raw material powder may be an inorganic compound such as oxide, carbonate or acetate, or an organic compound such as an organic metal. Any material that can be converted into an oxide by firing may be used.

The high frequency band referred to in the present invention is several to several hundreds.
Corresponding to the microwave band and millimeter wave band of the GHz band, for example, a high frequency band of 10 GHz or higher, particularly 30 GHz or higher, and further 70 GHz or higher is suitable.

Parallel plate conductor 2 for NRD guide of the present invention
1, 23 are C in terms of high electric conductivity and workability.
A conductor plate of u, Al, Fe, Ag, Au, Pt, SUS (stainless steel), brass (Cu-Zn alloy), etc., or an insulating plate made of ceramics, resin, etc., on which the conductor layers are formed. But it's okay.

The NRD guide of the present invention is used for a wireless LAN, a millimeter wave radar of an automobile, etc. by incorporating a high frequency diode such as a Gunn diode as a high frequency generating element. The object and other vehicles are irradiated with millimeter waves, the reflected waves are combined with the original millimeter waves to obtain an intermediate frequency signal, and by analyzing this intermediate frequency signal, the distance to obstacles and other vehicles, The moving speed of can be measured.

Thus, in the NRD guide of the present invention, the distance between the projection and the recess formed on the end surface of the dielectric line portion is surely 1/8 or less of the wavelength, and the plurality of dielectric line portions face each other. It is possible to increase the permissible range of misalignment between the end faces in the transmission direction and the lateral direction, and as a result, it is possible to easily maintain a high-frequency signal transmission characteristic and easily construct a dielectric waveguide having a complicated shape. Has an effect.

A millimeter wave transceiver using the NRD guide of the present invention will be described below. 15 and 16 show a millimeter wave radar as a millimeter wave transceiver of the present invention. FIG. 15 is a plan view of a transmission antenna and a reception antenna integrated with each other, and FIG. 16 shows a transmission antenna and a reception antenna. It is a top view of an independent thing.

In FIG. 15, reference numeral 51 is one parallel plate conductor (the other is omitted), and 52 is a voltage control type millimeter wave signal oscillator having a high frequency diode oscillator provided at one end of the first dielectric line 53. Part (voltage controlled oscillating part), which periodically biases the bias voltage of the variable capacitance diode arranged in the vicinity of the high frequency diode of the first dielectric line 53 so that the bias voltage application direction matches the electric field direction of the high frequency signal. By controlling and forming a triangular wave, a sine wave, or the like, the frequency-modulated millimeter wave signal for transmission is output.

Reference numeral 53 is a first dielectric line having a high-frequency diode oscillator attached to one end thereof, which propagates a millimeter-wave signal for transmission in which the millimeter-wave signal output from the high-frequency diode oscillator is modulated, and 54 is a first dielectric line. The circulator 55 made of a ferrite disk or the like having the first, second and third connecting portions 54a, 54b, 54c connected to the first, third and fourth dielectric lines 53, 55, 57, respectively, , Is connected to the second connection portion 54b of the circulator 54, propagates a millimeter wave signal, and has a transmitting / receiving antenna 5 at the tip.
Reference numeral 56 denotes a third dielectric line, and reference numeral 56 denotes a transmission / reception antenna configured by making the tip of the third dielectric line 55 tapered or the like.

The transmission / reception antenna 56 inputs / outputs a high-frequency signal through a through hole formed in the parallel plate conductor 51, and is installed on the outer surface of the parallel plate conductor 51 via a metal waveguide connected to the through hole. It may be a horn antenna or the like.

Numeral 57 is received by the transmission / reception antenna 56, propagates through the third dielectric line 55, and is circulator 54.
The received wave output from the third connection portion 54c of the mixer 5
The fourth dielectric line 58 for propagating to the 9 side is arranged close to the first dielectric line 53 so that one end side is electromagnetically coupled, and the second dielectric line 53 propagates a part of the millimeter wave signal to the mixer 59 side. Is a non-reflective termination (terminator) provided at one end of the second dielectric line 58 opposite to the mixer 59. In the figure, M1 mixes a part of the millimeter wave signal and the received wave by electromagnetically coupling the middle of the second dielectric line 58 and the middle of the fourth dielectric line 57 close to each other. It is a mixer unit that generates an intermediate frequency signal.

The circulator 54 of the present invention has a predetermined interval on the periphery of a pair of ferrite discs arranged in parallel between the parallel plate conductors 51, 51, for example, at an angle of 120 ° with respect to the center point of the ferrite discs. First connection parts 54a, which are arranged and are respectively used as input / output terminals of millimeter wave signals.
Has a second connecting portion 54b and a third connecting portion 54c,
The millimeter wave signal input from one connection portion is output from the other connection portion adjacent in the clockwise or counterclockwise direction in the plane of the ferrite disk. In addition, the parallel plate conductor 5
A magnet for rotating the wave front of the electromagnetic wave propagating through the ferrite disk passes through a portion of the outer main surface corresponding to the ferrite disk in the direction substantially perpendicular to the ferrite disk (generally the vertical direction). It is provided to do. The ferrite plate of the present invention is not limited to a disc shape, and may be a polygonal shape or the like.

Another embodiment of the millimeter wave transceiver of the present invention is shown in FIG. 1 in which the transmitting antenna and the receiving antenna are independent.
There are 6 types. In the figure, 61 is one parallel plate conductor (the other is omitted), and 62 is the first dielectric line 6
3 is a voltage control type millimeter wave signal oscillating section having a high frequency diode oscillator provided at one end of the first and second bias voltage applying directions so that the bias voltage application direction matches the electric field direction of the high frequency signal.
By periodically controlling the bias voltage of the variable capacitance diode arranged in the vicinity of the high frequency diode of the dielectric line 63 to generate a triangular wave, a sine wave, or the like, a frequency-modulated millimeter wave signal for transmission is output.

Reference numeral 63 is a first dielectric line having a high-frequency diode oscillator attached to one end thereof, which propagates a millimeter-wave signal for transmission in which the millimeter-wave signal output from the high-frequency diode oscillator is modulated, and 64 is a first dielectric line. A circulator made of a ferrite disk or the like having first, second and third connecting portions 64a, 64b and 64c connected to the first, third and fifth dielectric lines 63, 65 and 67 respectively, and 65 are , A second connecting portion 64b of the circulator 64, which propagates a millimeter wave signal and has a transmitting antenna 66 at the tip.
Is a transmitting antenna configured by tapering the tip of the third dielectric line 65, and 67 is connected to the third connecting portion 64c of the circulator 64. , A fifth dielectric line having a reflection-free termination portion 67a for attenuating a millimeter-wave signal for transmission provided at its tip.

A second dielectric line 68 is disposed close to the first dielectric line 63 so that one end side is electromagnetically coupled, and propagates a part of the millimeter wave signal to the mixer 71 side.
Reference numeral 68a denotes a non-reflecting end portion provided at one end portion of the second dielectric line 68 on the side opposite to the mixer 71, and 69 denotes a fourth portion for propagating the reception wave received by the reception antenna 70 to the mixer 71 side. It is a dielectric line. Further, M2 in the drawing is formed by electromagnetically coupling the middle of the second dielectric line 68 and the middle of the fourth dielectric line 69 close to each other to mix a part of the millimeter wave signal and the received wave. Is a mixer unit for generating an intermediate frequency signal.

The transmitting antenna 66 and the receiving antenna 70 allow a high frequency signal to be input or output through a through hole formed in the parallel plate conductor 61, and the parallel plate conductor 61.
It may be a horn antenna or the like installed on the outer surface of the metal via a metal waveguide connected to the through hole.

In the present invention, in FIG. 15, one end side of the second dielectric line 58 is arranged close to the first dielectric line 53 or one end is joined, but in the case of joining, at the joining part, It is preferable that the first dielectric line 53 is linear and the second dielectric line 58 is arcuate, and the radius of curvature r of the arcuate part is not less than the wavelength λ of the high-frequency signal. As a result, it is possible to reduce the loss of the high frequency signal and branch the high frequency signal with a uniform output. Further, the second dielectric line 58 may be linear and the first dielectric line 53 may be arcuate at the joint, and the radius of curvature r of the arcuate part may be equal to or greater than the wavelength λ of the high frequency signal. In this case, the same effect as above can be obtained.

Further, in the mixer 59, the second dielectric line 58 and the fourth dielectric line 57 can be joined together. In this case, the dielectric lines 58 and 5 can be joined in the same manner as described above.
It is preferable that any one of the junctions 7 and 7 has an arcuate shape, and the radius of curvature r of the arcuate portion is not less than the wavelength λ of the high-frequency signal. In addition, the second dielectric line 58 and the fourth dielectric line 5
7 and 7 are electromagnetically coupled to each other, the at least one of the second dielectric line 58 and the fourth dielectric line 57 is arranged in an arc shape in the adjacent portion, thereby providing the close arrangement. Can be configured.

Preferably, the radius of curvature r of the above-mentioned joining portion is 3 λ or less, and if it exceeds 3 λ, the joining structure becomes large and the advantage of miniaturization cannot be obtained. If the radius of curvature r of the joint is set to be smaller than the wavelength λ, the branching strength to the dielectric line having the arc-shaped joint becomes small.

Such a junction structure between the first dielectric line 53 and the second dielectric line 58, a junction structure between the second dielectric line 58 and the fourth dielectric line 57, and a second
The configuration of the dielectric line 58 and the fourth dielectric line 57 arranged close to each other is the same as in the case of FIG.

These various components are provided between parallel plate conductors arranged at intervals of not more than ½ of the wavelength λ at the working frequency, which is the wavelength of the millimeter wave signal in air.

In FIG. 15, a pulse modulation control can be performed by providing a switch in the middle of the first dielectric line 53 and turning it on and off. For example, as shown in FIG. 18, a second choke type bias supply line 112 is formed on one main surface of a wiring substrate 88, and a beam lead type PIN diode or a Schottky barrier diode mounted by soldering is provided in the middle thereof. It is a switch. In FIG. 18, E indicates the electric field direction of the high frequency signal propagating in the dielectric line 77, and 111 is a connection pad for connecting a pulse modulating diode such as a PIN diode or a Schottky barrier diode.

The wiring board 88 is connected to the first dielectric line 5
A pulse modulating diode such as a PIN diode or a Schottky barrier diode is provided between the signal branching part of the third dielectric line 58 and the circulator 54 in the direction of the electric field of the high frequency signal in the LSM mode. They are arranged so as to match with each other and are interposed in the middle of the first dielectric line 53. In addition, the first dielectric line 53
Another circulator is interposed between the first and third connection parts, the first dielectric line 53 is connected, and the second connection part is connected to another dielectric line. A switch provided with a Schottky barrier diode having the configuration shown in FIG. 7 may be installed on the end face of the tip portion.

In FIG. 16, the circulator 64 is eliminated and the transmitting antenna 6 is provided at the tip of the first dielectric line 63.
It is also possible to adopt a configuration in which 6 is connected. In this case, although the size is reduced, the type shown in FIG. 16 is preferable because part of the received wave easily mixes into the voltage controlled oscillator 62 and causes noise. In addition, in the type of FIG. 16, the second dielectric line 68 is arranged close to the third dielectric line 65 so that one end side is electromagnetically coupled or one end is joined to the third dielectric line 65. , The millimeter wave signal may be partly propagated to the mixer 71 side. This structure also has the same functions and effects as those of FIG.

In FIG. 16, a pulse modulation control can be performed by providing a switch having the same structure as that of FIG. 18 in the middle of the first dielectric line 63 and turning it on and off. For example, as shown in FIG. 18, the second choke type bias supply line 112 is formed on one main surface of the wiring substrate 88, and a beam lead type PIN diode or a Schottky barrier diode mounted by soldering is provided in the middle thereof. It is a switch. This wiring board 88 is provided with a signal branch portion of the first dielectric line 63 and the second dielectric line 68,
A PIN diode or a Schottky barrier diode is arranged between the circulator 64 and the circulator 64 so that the bias voltage application direction matches the electric field direction of the LSM mode high-frequency signal, and is interposed in the first dielectric line 63. .

Further, another circulator is interposed in the first dielectric line 63, the first dielectric line 63 is connected to the first and third connection parts thereof, and the other circulator is connected to the second connection part. Connect the dielectric line, and on the end face of the tip of the dielectric line,
You may install the switch provided with the Schottky barrier diode of a structure like FIG.

The millimeter wave transceivers of FIGS. 15 and 16 are of the FMCW (Frequency Modulation Cotinuous Waves) system, and the operating principle of the FMCW system is as follows. MODIN for inputting modulation signal of voltage controlled oscillator
An input signal whose voltage amplitude changes with time into a triangular wave or the like is input to the terminal, the output signal is frequency-modulated, and the output frequency deviation of the voltage controlled oscillator is shifted so as to form a triangular wave or the like. When an output signal (transmission wave) is radiated from the transmission / reception antenna 56 and the transmission antenna 66, if a target is present in front of the transmission / reception antenna 56 and the transmission antenna 66, a round-trip time difference in the propagation speed of the radio wave occurs,
The reflected wave (received wave) returns. At this time, mixer 5
The IFOUT terminals on the output side of 9, 71 output the frequency difference between the transmitted wave and the received wave. By analyzing the frequency components such as the output frequency of this IFOUT terminal, Fif = 4R
fm / Δf / c {Fif: IF (Intermediate Frequenc
y) output frequency, R: distance, fm: modulation frequency, Δf:
The distance can be obtained from the relational expression of frequency shift width, c: speed of light.

As described above, when the present invention is applied to a millimeter wave radar of an automobile or the like, the obstacle around the automobile and other automobiles are irradiated with the millimeter wave, the reflected wave is combined with the original millimeter wave, and the intermediate frequency signal is generated. By analyzing this intermediate frequency signal, the distance to obstacles and other vehicles, their moving speed, etc. can be measured.

The voltage controlled oscillators 52 and 62 using the high frequency diode oscillator of the present invention will be described below. 17 and 18 show an NRD guide type high frequency diode oscillator of the present invention. In these figures, 81 is a pair of parallel plate conductors, and 72 is a substantially rectangular parallelepiped metal block or the like for mounting the Gunn diode 73. The metal member 73 is a Gunn diode, which is a type of high-frequency diode that oscillates microwaves and millimeter waves. The choke-type bias supply line 74a is installed on one side surface of the metal member 72 and supplies a bias voltage to the Gunn diode 73 and functions as a low-pass filter for preventing leakage of high frequency signals.
A wiring board having a wiring formed thereon, 75 a strip-shaped conductor such as a metal foil ribbon connecting the choke type bias supply line 74a and the upper conductor of the Gunn diode 73, and 77 a Gunn diode 73.
Is a dielectric line (corresponding to the first dielectric lines 53 and 63) that is arranged in the vicinity of and receives high frequency signals and propagates them to the outside. In FIG. 17, B is the wiring board 8
Frequency modulation diode 110 (see FIG. 1).
8) The bias voltage application direction, and D is the high-frequency signal transmission direction.

In FIG. 17, in the choke type bias supply line 74a, the width of the wide line and the length of the narrow line are each approximately λ / 4, and the length of the strip conductor 75 is approximately {(3 / 4) + m} λ (m is an integer of 0 or more). This allows the metal strip line 7
The high frequency signal can be resonated by the choke type bias supply line 74a itself by omitting the metal strip resonator 76 forming 6a.

The length of the strip conductor 75 is preferably approximately 3λ / 4 to approximately {(3/4) +3} λ, and approximately {(3/4) +3} λ.
If the value exceeds the range, the band-shaped conductor 75 becomes long, and bending, twisting, and the like are likely to occur, and variations in characteristics such as the oscillation frequency between individual high-frequency diode oscillators increase, and various resonance modes occur, resulting in desired oscillation. There is a problem that a signal having a frequency different from the frequency is generated. More preferably, it is approximately 3λ / 4, approximately {(3/4) +1} λ. In addition, the reason for setting approximately {(3/4) + m} λ is {(3/4)
This is because resonance is possible even with a slight deviation from + m} λ. For example, the strip conductor 75 may be formed to be longer than {(3/4) + m} λ by about 10 to 20%. In that case, the choke type bias supply line 74a in contact with the strip conductor 75 is formed.
This is because it is considered that a part of the length λ / 4 of the first pattern contributes to resonance. Therefore, the length of the strip conductor 75 can be changed within the range of about {(3/4) + m} λ ± 20%.

These choke type bias supply lines 74a
The material of the band-shaped conductor 75 is Cu, Al, Au, A.
It is composed of g, W, Ti, Ni, Cr, Pd, Pt, and the like, and particularly Cu and Ag are preferable because they have good electric conductivity, small loss, and large oscillation output.

The strip conductor 75 is electromagnetically coupled to the metal member 72 at a predetermined distance from the surface of the metal member 72, and is bridged between the choke type bias supply line 74a and the Gunn diode 73. That is, one end of the strip conductor 75 is connected to one end of the choke type bias supply line 74a by soldering or the like, and the other end of the strip conductor 75 is connected to the upper conductor of the Gunn diode 73 by soldering or the like. The middle part except the connection part of is in a state of floating in the air.

Since the metal member 72 also serves as an electrical ground (earth) for the Gunn diode 73, it may be a metal conductor, and its material is not particularly limited as long as it is a metal (including alloy) conductor. Not brass (brass: Cu-
Zn alloy), Al, Cu, SUS (stainless steel), Ag, Au, Pt and the like. The metal member 72
Is a metal block consisting entirely of metal, an insulating substrate such as ceramics or plastic which is wholly or partially metal-plated, and an insulating substrate which is wholly or partially coated with a conductive resin material or the like. Is also good.

Also, the Gunn diode 73 and the dielectric line 7
The distance to 7 is preferably 1.0 mm or less, 1.0 m
When it exceeds m, the loss is reduced and the maximum separation width capable of electromagnetic coupling is exceeded.

Further, as the high frequency diode of the present invention, an impatt: impact ionization avalanch
e transit time ・ Diode, trapat
t: trapped plasma avalanche triggered transit) ・
Microwave diodes such as diodes and Gunn diodes and millimeter wave diodes are preferably used.

The switch shown in FIG. 18 is provided with a frequency modulation diode 110 composed of a variable capacitance diode such as a varactor diode, and a second choke type bias supply line 112 is formed on one main surface of the wiring board 88. , A frequency modulation diode 110 soldered in the middle thereof
Is a switch provided with. Frequency modulation diode 11
The oscillation frequency of the Gunn diode 73 can be controlled by controlling the bias voltage applied to 0. In FIG. 7, E indicates the electric field direction of the high frequency signal propagating in the dielectric line 77, and 111 is a connection pad for connecting the frequency modulation diode 110.

[0064]

EXAMPLES Examples of the NRD guide of the present invention will be described below.

(Example 1) An NRD guide having projections 24 as shown in FIG. 5 was constructed as follows. Two 6 mm thick Al plates as parallel plate conductors 1.8 mm
The cross-sectional shape is 1.8 mm between them.
A dielectric line 22 made of cordierite ceramics having a (height) × 0.8 mm (width) rectangular shape and a relative dielectric constant of 4.8 was installed. This dielectric line 22 has a dielectric line portion 22a having a protrusion 24 on the end face and a recess 25 on the end face.
And a dielectric line portion 22b having. Then, the protrusions 24 are partially inserted into the recesses 25 or face each other. However, the thickness a of the protrusion 24 is a = 1.0 mm, b =
The protrusion length c of the protrusion 24 was 0.4 mm, and the protrusion length c was 0.8 mm.

With respect to this dielectric line 22, the results of evaluating the propagation characteristics of the LSM mode and the LSE mode by changing the interval L are shown in FIGS. 8 and 9, respectively. LSE
The propagation characteristics of the modes were evaluated using an NRD guide that converts an electromagnetic wave excited in the LSM mode into the LSE mode and then into the LSM mode again. For example, one end of another dielectric line is connected to the end of the dielectric line through which the LSM mode propagates at right angles to the transmission direction of the LSE mode.
Convert to mode and connect another dielectric line to the other end of the other dielectric line at a right angle to the transmission direction of the other LSM.
LS with a structure such as converting to mode
The transmission characteristic (S ₂₁ ) was measured by inserting the object to be measured in the portion where the E mode was transmitted.

From FIG. 8, the propagation loss in the LSM mode is 1d.
The interval L when reaching B is 77 GHz (wavelength 3.9 mm), 80 GHz (wavelength 3.7 mm), 90 G
0.6 m at Hz (wavelength 3.3 mm)
It was found that they were m, 0.72 mm and 0.7 mm.
These lengths are about 6.5 times the wavelength and about 5.
It is half, about 4.8. Therefore, the high frequency signal could be propagated with a loss of 1 dB or less even at an interval larger than 1/8 of the wavelength.

Further, from FIG. 9, the interval L at which the propagation loss of the LSE mode reaches 1 dB is the frequency 77 GHz, 80 GH.
z, 90 GHz, 0.17 mm, 0.
It was found to be 18 mm and 0.25 mm. These lengths are about 1/23 and about 21 of the corresponding wavelengths, respectively.
It was one-third, about one-third.

Example 2 An NRD guide having protrusions 24 as shown in FIG. 6 was constructed in the same manner as in Example 1 and the evaluation results are shown in FIGS. 10 and 11. However, the lateral width a1 of the protrusion 24 is a1 = 0.4 mm, b1 = 0.
2 mm, and the protrusion length c1 of the protrusion 24 was 0.8 mm.

From FIG. 10, the propagation loss in the LSM mode is 1
The interval L when reaching dB is 77 GHz, 80 frequency.
0.47 mm at GHz and 90 GHz,
It was found to be 0.54 mm and 0.56 mm. Each of these lengths is about 8.3 times the corresponding wavelength,
It was about 1 / 6.9 and about 5.9.

Further, from FIG. 11, the interval L at which the propagation loss of the LSE mode reaches 1 dB is the frequency 77 GHz, 80 G.
At 0.9Hz and 90GHz, 0.94mm,
It was found to be 1.0 mm and 0.61 mm. These lengths are about 4.1, about 3.7, and about 5.5 times the corresponding wavelengths, respectively. Therefore, the high frequency signal could be propagated with a loss of 1 dB or less even at an interval larger than 1/8 of the wavelength.

(Comparative Example) An NRD guide S composed of dielectric line portions 2a, 2b, 2c having flat end faces as shown in FIG. 3 was produced in the same manner as in Example 1 above.
The evaluation results are shown in FIGS. 12 and 13.

From FIG. 12, the propagation loss in the LSM mode is 1
The interval L reaching dB is frequency 77 GHz, 80 GH
z, 90 GHz, 0.55 mm, 0.
It was found to be 6 mm and 0.4 mm. These lengths are about 7.1 times the corresponding wavelength and about 6.2, respectively.
It was one-third, about 8.3-fold.

Further, from FIG. 13, the interval L at which the propagation loss of the LSE mode reaches 1 dB is the frequency 77 GHz, 80 G.
0.28 mm at Hz and 90 GHz,
It was found to be 0.32 mm and 0.4 mm. These lengths are about 1/14 and about 1 of the corresponding wavelengths, respectively.
It was 1/2, about 8.3.

From the results of FIGS. 8, 10 and 12, LSM
It was found that in the case of the mode, the propagation characteristics can be improved when the thickness of the protrusions 24 in the vertical direction is smaller than the thickness of the dielectric line portion 22a (FIG. 8). This is because the LSM mode electric field is oriented in the width direction of the dielectric line portion 22a, and when the protrusion 24 has the shape of FIG. In order to satisfy the boundary condition, it is not necessary to deform the electric field distribution. On the other hand, when the protrusion 24 has a shape as shown in FIG. 6, the boundary condition with the electric field in the air on the left and right side surfaces of the protrusion 24 is satisfied. It can be understood that this is because a large deformation of the electric field distribution is required.

From the results shown in FIGS. 9, 11, and 13, L
It was found that in the SE mode, the propagation characteristics are improved when the width of the protrusion 24 is made smaller than the width of the NRD guide (FIG. 11). This is because the LSE mode electric field is directed in the vertical direction of the dielectric line portion 22a, and when the protrusion 24 has the shape shown in FIG.
In order to satisfy the boundary condition with the electric field in the air on the left and right side surfaces of No. 4, the electric field distribution does not need to be deformed. On the other hand, when the projection 24 has a shape as shown in FIG. It can be understood that a large deformation of the electric field distribution is required to satisfy the conditions.

As described above, in Examples 1 and 2, the interval L at which the same amount of attenuation is obtained is larger in the LSM mode and the LSE mode than in the comparative example.
In other words, the distance L between the dielectric line portions 22a and 22b
It was confirmed that the propagation characteristics of the LSM mode and the LSE mode with respect to the same value of were good, and therefore, the allowable range for the interval L was large when the limit was set by the amount of attenuation.

(Embodiment 3) A dielectric line portion 22a having protrusions as shown in FIG. 7 was produced and evaluated in the same manner as in Embodiment 1 above, and the results of evaluation are shown in FIG. However, the width a2 of the protrusion 24 is a2 = 0.4 mm, b2 = 0.4 mm,
The protrusion length c2 of 4 was set to c2 = 0.8 mm. From FIG. 14, the interval L at which the attenuation in the LSE mode reaches 1 dB is
At frequencies of 77 GHz, 80 GHz and 90 GHz,
It was found to be 0.8 mm, 0.5 mm and 0.22 mm, respectively.

From FIGS. 11, 13, and 14, the shape of FIG. 7 has a larger allowable range for the LSE mode propagation than the case where the end face is flat at the frequencies of 77 GHz and 80 GHz, and the shape of FIG. 90 GHz
It was found that the allowable range was further increased, including in the case of.

The present invention is not limited to the above embodiments, and various modifications can be made without departing from the gist of the present invention.

[0081]

According to the present invention, in the NRD guide, the dielectric lines are configured such that the end faces of the plurality of dielectric line parts are made close to each other so as to be electromagnetically coupled to face each other, and the plurality of dielectric line parts are opposed to each other. One end face of one of the facing end faces of the plurality of dielectric line portions is formed by forming a projection on one end face of the facing end faces and forming a recess into which the protrusion is inserted on the other end face. The protrusion formed on
It is inserted into the concave portion formed on the other end face or is disposed so as to be closely opposed to the concave portion, so that the interval between the protrusion and the concave portion is surely 1/8 or less of the wavelength. As a result, it is possible to increase the permissible range of the shift in the transmission direction and the lateral direction between the end faces facing each other of the plurality of dielectric line portions. The dielectric line can be easily constructed.

According to the present invention, preferably, the shape of the dielectric line portion in the cross section perpendicular to the transmission direction of the high frequency signal is substantially quadrangle, and the shape of the protrusion in the cross section is substantially quadrangle with a reduced height or width. As a result, the electromagnetic field distributions of the LSM mode and the LSE mode tend to be symmetrical in the vertical direction and the horizontal direction, and the transmission characteristics of those modes become good. Further, the dielectric line portion can be easily manufactured by a press molding method or the like.

Further, in the present invention, preferably, the center of the cross section of the dielectric line portion and the center of the cross section of the protrusion are substantially coincident with each other, and the center of the cross section of the dielectric line portion and the center of the cross section of the concave portion are substantially the same. By matching, the facing end faces of the plurality of dielectric line portions can be arranged facing each other with almost no lateral shift, and as a result, the electromagnetic field distributions in the LSM mode and the LSE mode can be set in the vertical direction and in the vertical direction. It becomes symmetrical in the lateral direction, and the transmission loss in the LSM mode or the LSE mode can be suppressed to a low level.

The high-frequency transmitter / receiver of the present invention, which has a transmitting / receiving antenna, is easy to manufacture and has excellent high-frequency signal transmission characteristics, and has an increased detection distance when applied to a millimeter-wave radar or the like. Becomes Also,
If the transmitting antenna and the receiving antenna are independent, the fabrication is easy and the transmission characteristics of high frequency signals are excellent.When applied to millimeter wave radar, etc., the millimeter wave signals for transmission are mixed via a circulator. The noise of the received signal is reduced and the detection distance is increased.

[Brief description of drawings]

FIG. 1 is a perspective view of an example of an embodiment of an NRD guide of the present invention, in which the inside is seen through.

FIG. 2 is a partially transparent perspective view showing the basic configuration of a conventional NRD guide S1.

FIG. 3 is a perspective view of the inside of a conventional NRD guide S seen through.

FIG. 4 is a perspective view of another example of the embodiment of the NRD guide of the present invention in which the inside is seen through.

FIG. 5 is a perspective view showing an example of an embodiment regarding a protrusion on an end face of a dielectric line portion in an NRD guide of the present invention.

FIG. 6 is a perspective view showing another example of the embodiment of the protrusion on the end face of the dielectric line portion in the NRD guide of the present invention.

FIG. 7 is a perspective view showing another example of the embodiment with respect to the projection on the end face of the dielectric line portion in the NRD guide of the present invention.

8 is a graph showing the relationship between the distance between the end faces of the dielectric line portion and the LSM mode transmission amount for the NRD guide having the protrusions of FIG.

9 is a graph showing the relationship between the distance between the end faces of the dielectric line portion and the amount of transmission in the LSE mode in the NRD guide having the protrusions of FIG.

FIG. 10 shows an NRD guide having protrusions of FIG.
6 is a graph showing the relationship between the distance between the end faces of the dielectric line portion and the amount of transmission in the LSM mode.

11 is a schematic diagram of an NRD guide having protrusions of FIG.
7 is a graph showing the relationship between the distance between the end faces of the dielectric line portion and the amount of transmission in the LSE mode.

FIG. 12 is a graph showing the relationship between the distance between the end faces of the dielectric line portions and the amount of transmission in the LSM mode for the NRD guide in which the opposite end faces of the plurality of dielectric line portions are flat.

FIG. 13 is a graph showing the relationship between the distance between the end faces of the dielectric line portions and the amount of transmission in the LSE mode for the NRD guide in which the opposite end faces of the plurality of dielectric line portions are flat.

FIG. 14 is a diagram showing an NRD guide having protrusions of FIG.
7 is a graph showing the relationship between the distance between the end faces of the dielectric line portion and the amount of transmission in the LSE mode.

FIG. 15 shows an example of an embodiment of a millimeter wave transceiver according to the present invention, and is a plan view in which the inside is seen through.

FIG. 16 shows another example of the embodiment of the millimeter wave transceiver of the invention, and is a plan view in which the inside is seen through.

FIG. 17 is a perspective view of the inside of a voltage controlled oscillator for a millimeter wave transceiver of the present invention seen through.

FIG. 18 is a perspective view of a frequency modulation switch provided with a variable capacitance diode as a frequency modulation diode of the present invention.

[Explanation of symbols]

21: Parallel plate conductor 22: Dielectric line 23: Parallel plate conductor 24: Protrusion 25: Recess

Claims (5)

[Claims] 1. A non-radiative dielectric line in which a dielectric line is interposed between parallel plate conductors arranged at intervals of ½ or less of the wavelength of a high-frequency signal, wherein the dielectric line comprises a plurality of dielectrics. The end portions of the line portions are configured to be close to each other so as to be electromagnetically coupled and face each other, and a protrusion is formed on one end face of the facing end faces of the plurality of dielectric line portions, and the protrusion is formed on the other end face. A non-radiative dielectric waveguide characterized in that a recess is formed to be inserted. 2. The shape of a cross section of the dielectric line portion perpendicular to the transmission direction of the high frequency signal is substantially quadrangular,
The non-radiative dielectric waveguide according to claim 1, wherein the shape of the cross section of the protrusion is a shape in which the height or width of the substantially quadrangle is reduced. 3. The center of the dielectric line portion in the cross section and the center of the protrusion in the cross section are substantially the same, and the center of the dielectric line portion in the cross section and the center of the recess in the cross section. 3. The non-radiative dielectric waveguide according to claim 2, wherein and are substantially the same. 4. A high frequency diode oscillator is attached to one end between parallel plate conductors arranged at intervals of ½ or less of the wavelength of the millimeter wave signal, and propagates the millimeter wave signal output from the high frequency diode oscillator. And a first dielectric line for transmitting, wherein the bias voltage applying direction is arranged so as to match the electric field direction of the millimeter wave signal, and the millimeter wave signal is frequency-modulated by periodically controlling the bias voltage. Of the variable capacitance diode for outputting as a millimeter wave signal, and one end side of the variable capacitance diode that is electromagnetically coupled to the first dielectric line, or one end of which is joined so that a part of the millimeter wave signal is on the mixer side. A second dielectric line that propagates to the parallel plate conductor and a ferrite plate that is arranged in parallel with the parallel plate conductor at a peripheral portion of the ferrite plate at a predetermined interval and receives and outputs the millimeter wave signal. It has a first connecting portion, a second connecting portion, and a third connecting portion which are ends, and the millimeter wave signal inputted from one of the connecting portions is rotated clockwise or counterclockwise in the plane of the ferrite plate. A circulator for outputting from another adjacent connecting portion in a clockwise direction, wherein the first connecting portion is joined to an output end of the millimeter wave signal of the first dielectric line; A third dielectric line which is joined to a second connecting part and which propagates the millimeter wave signal and which has a transmitting / receiving antenna at a tip thereof; and a third dielectric line which is received by the transmitting / receiving antenna and propagates through the third dielectric line. The fourth dielectric line for propagating the received wave output from the third connection part of the circulator to the mixer side, and the middle of the second dielectric line and the middle of the fourth dielectric line are arranged close to each other. Electromagnetic A millimeter wave transmitter / receiver provided with a mixer unit which is formed by combining or joining and mixing a part of a millimeter wave signal and a received wave to generate an intermediate frequency signal, wherein the first to fourth dielectrics are provided. A millimeter wave transceiver, wherein at least one of the body lines constitutes the non-radiative dielectric line according to any one of claims 1 to 3. 5. A high frequency diode oscillator is attached to one end between parallel plate conductors arranged at intervals of ½ or less of the wavelength of the millimeter wave signal, and propagates the millimeter wave signal output from the high frequency diode oscillator. And a first dielectric line for transmitting, wherein the bias voltage applying direction is arranged so as to match the electric field direction of the millimeter wave signal, and the millimeter wave signal is frequency-modulated by periodically controlling the bias voltage. Of the variable capacitance diode for outputting as a millimeter wave signal, and one end side of the variable capacitance diode that is electromagnetically coupled to the first dielectric line, or one end of which is joined so that a part of the millimeter wave signal is on the mixer side. A second dielectric line that propagates to the parallel plate conductor and a ferrite plate that is arranged in parallel with the parallel plate conductor at a peripheral portion of the ferrite plate at a predetermined interval and receives and outputs the millimeter wave signal. It has a first connecting portion, a second connecting portion, and a third connecting portion which are ends, and the millimeter wave signal inputted from one of the connecting portions is rotated clockwise or counterclockwise in the plane of the ferrite plate. A circulator that outputs from another adjacent connection portion in a clockwise direction, wherein the first connection portion is connected to an output end of the millimeter wave signal of the first dielectric line, and the circulator includes the circulator. A fourth dielectric line which is connected to the second connection part and which propagates the millimeter wave signal and has a transmission antenna at the tip, a reception antenna at the tip, and a mixer at the other end. Of the dielectric line and the third connection part of the circulator for propagating the millimeter wave signal mixed and received by the transmitting antenna and transmitting the millimeter wave signal at the non-reflective end part provided at the tip part. The fifth dielectric line to be attenuated and the midway of the second dielectric line and the midway of the fourth dielectric line are close to each other to be electromagnetically coupled or to be joined, and a part of the millimeter wave signal In a millimeter wave transmitter / receiver provided with a mixer unit that mixes a received wave with a received wave to generate an intermediate frequency signal, at least one of the first to fifth dielectric lines is according to any one of claims 1 to 3. A millimeter-wave transceiver comprising the non-radiative dielectric waveguide described.