GB2104330A

GB2104330A - Improvements in or relating to amplifiers

Info

Publication number: GB2104330A
Application number: GB08215791A
Authority: GB
Inventors: Kevin Peter Watts; Jeffrey Ian Robinson
Original assignee: Texas Instruments Ltd
Current assignee: Texas Instruments Ltd
Priority date: 1981-08-19
Filing date: 1982-05-28
Publication date: 1983-03-02
Also published as: EP0072705A2; EP0072705A3; EP0072705B1; DE3275264D1; US4588858A

Description

1

GB2104 330A 1

SPECIFICATION

.sion

Improvements in or relating to amplifiers

5 This invention relates to amplifiers and more specifically but not exclusively to an amplifier forming part of a semiconductor subscriber's line interface circuit (SLIC) for driving a telephone line.

10 In a telephone exchange each subscriber's line is terminated by a subscriber's line interface unit which receives signals from and transmits signals to the subscriber's line. This circuit conventionally includes a hybrid trans-15 former. Transformers are, however, bulky and expensive and attention recently has focussed on the use of transistor circuitry in place of transformers.

The main signal requirements to be met by 20 a semiconductor SLIC and the tests to measure the performance in respect of each requirement are as follows:-

a It should present a defined impedance (ZT) to the subscriber's line. A measure of the 25 accuracy to which it does this is given by the Return Loss test, a circuit for which is shown in Fig. 5 of the accompanying drawings. In this test circuit

L1 = 20 log/ V61

30 R51

R52

= 1 ± 0.05%,

Zx = impedance of the Test Network 35 ± 0.05%. In operation, signal voltage and source V51 is set to, say, OdBm and the return loss is given by

40

20 log

V,

IdB,

2V

52

where V52 is the signal voltage and measured between the junction of the impedance Zx and 45 the SLIC and the junction between the resistors R51 and R52.

b It should have a low common-mode-signal to differential-signal conversion coefficient at its output. Performance in this respect is mea-50 sure by a signal test known as the L, test, a circuit for which is shown in Fig. 6 of the accompanying drawings. This circuit consists of a pair of matched 300ohm resistors R61, R62 connected in series across the terminals 55 of the SLIC. A signal V61 is applied between the junction of these resistors and earth potential and the resultant voltage V62 across the terminals of the SLIC is measured. R61 and R62 should be matched so that

60

R61

—— = 1 ±0.00001.

R62

65 The performance L1 is given by the expres-

70

V62

cThe signal on the output ports of the SLIC should have a high degree of signal balance about earth. Performance in this respect is 75 measured by the L2 test, a circuit for which is given in Fig. 7. This circuit consists of a pair of 300ohm resistors R71 and R72 connected in series across the output port of the SLIC. A signal voltage V71 is applied across the out-80 put port of the SLIC and the voltage V72 developed between the junction of the resistors R71 and R72 and earth is measured. The L2 performance is given by the expression

85 L2 = 20 log

V-

71

v7

An object of the present invention is to 90 produce an amplifier for use in a semiconductor line interface circuit based on the requirements set out above.

According to a first aspect of the present invention there is provided an amplifier for 95 differentially driving a two wire line including an input circuit, a pair of output terminals, a reference impedance, feedback means coupled to each of the output terminals and to the input circuit for monitoring the signal on 100 the output terminals and deriving therefrom a negative-feedback signal representing the differential signal on the output terminals and for so applying the negative-feedback signal together with the signal at the input circuit to 105 the reference impedance as to cause a signal to appear across the reference impedance dependent on an additive combination of the feedback signal and the signal on the input circuit, and output drive means coupled to the 110 reference impedance and to the output terminals responsive to the current flowing in the reference impedance to apply respective currents, each being in proportion thereto, in respective opposite senses, to the output ter-115 minals.

According to a second aspect of the present invention there is provided a high common mode rejection performance differential input amplifier having two input conductors, impe-120 dance means so coupled between the conductors that a current flows in the impedance in proportion to the differential voltage of the signal on the conductors and current sensing means coupled to the impedance for sensing 125 the current flow through the impedance and for producing an output signal in proportion thereto.

According to a third aspect of the present invention there is provided a method of differ-130 entially driving a two wire line including the

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GB2 104 330A

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steps of monitoring the line and producing a negative feedback signal proportional to the differential voltage on the line,

5 applying across a reference impedance an arithmetic combination of the negative feedback signal and an input signal,

monitoring the current in the reference impedance and applying currents to the wires of 1 0 the line, each proportional to the current in the reference impedance and in respective opposite senses.

A telephone line drive amplifier embodying the invention will now be described by way of 1 5 example only making reference to the accompanying drawings in which:-

Figure 1 is a block diagram of a subscriber's line interface unit;

Figure 2 is a simplified schematic diagram 20 of a transmit unit suitable for use in the arrangement of Fig. 1;

Figure 3 is another schematic diagram a transmit unit suitable for use in the arrangement of Fig. 1 ;

25 Figure 4 is a diagram showing the arrangement of Fig. 3 implemented using an integrated circuit; and

Figure 5, 6 and 7 are circuit diagrams of various test circuits.

30 Referring to Fig. 1, a subscriber's line interface unit consists of a transmit circuit 10 connected to subscriber's line terminals A, B for transmitting speech signals over the line to a subscriber's telephone instrument in re-35 sponse to a speech signal on an input terminal 72. Also connected to the subscriber's line terminals A, B is a receive circuit 11 which receives any speech signal originating from the subscriber's instrument S and produces a 40 corresponding speech signal on an output terminal 1 3. The receive circuit 1 1 also takes a signal from the input terminal 1 2 of the transmit circuit 10 to enable it to eliminate or reduce side tone.

45 In addition to producing a speech signal the transmit circuit 10 also feeds a constant current to the line to power the subscriber's instrument S.

Referring to Fig. 2 a differential amplifier 50 for use in the transmit unit 10 of Fig. 1

includes an input terminal 21, which may be fed by speech signals from the telephone network. Coupled to the input terminal is one terminal of a reference impedance 22 and a 55 current sense circuit combination 23.

The differential amplifier produces output signals on output terminals A and B which in circuit may be connected to drive the A and B wires of the telephone line. Coupled to each 60 of output terminals A and B is an input of a line voltage sense amplifier 24 that is arranged to produce an output proportional to the differential voltage on the output terminals. The output of the senseamplifier 24 is 65 connected to the other terminal of the reference impedance 22.

The current sense circuit 23 produces an output on a line 25 which is in turn coupled to each of a pair of controllable current 70 sources G1 and G2 of opposite senses, and connected respectively to the output terminals A and B. In practice the current source G1 and G2 may be precision current mirrors.

In operation the line sense amplifier 24 75 monitors the differential signal between the output terminals A and B and produces an output signal VL which is subtracted from the incoming speech signal on the input terminal 21 at the reference impedance 22. The cur-80 rent flowing in this impedance is accurately monitored by the current sense circuit 23 and is differentially reflected into the output terminals A and B by the controlled current sources G1 and G2. An advanage of this arrangement 85 is that the output impedance of the amplifier is controlled by the value of the precision reference impedance 22, scaled by a factor dependent on the gain of the other circuit compoents. Also the simplicity of construction 90 ensures that the desired return loss specification is achievable with realistic component tolerances. Furthermore the common mode signal to differential conversion ratio and the signal balance about earth (i.e. L1 and L2 95 performance) are only limited by the accuracy of the two controlled current sources G1 and G2, which may be precision current mirrors.

Referring to Fig. 3 a subscriber's line interface circuit has an input terminal 31 con-100 nected via an input resistor R8 to the summing junction of an amplifier A7. This summing junction is also fed by a negative feedback path via a resistor R11 and a capacitor C3. This feedback path consists of amplifiers A5 105 and A8, a transistor Q4 and associated components.

The output of the amplifiers A7 is connected to earth via a reference impedance network 32. The current flow in this network 11 0 is sensed by an output amplifier combination A1 Q1 and which reflects it at the output terminal A via a lightning protection resistor 34.

The output terminal B is driven by an 1 1 5 output combination A4 Q2 one input of which is connected via an amplifier combination A3 Q3 to the output of differential input amplifier A2. The output of amplifier A2 is also connected via a resistor R3 to the output drive 1 20 amplifier combination A1, Q1 feeding the output terminal A.

The function of the amplifier A2 and the feedback loops consisting of amplifiers A1, A2 and A3, A4 is to ensure that the sum of 125 the voltages on the output terminals A and B is at all times equal to a reference value i.e. there are equal and opposite excursions on the output terminals. Such an arrangement is the subject of co-pending Patent Application 130 No: 80.33477. For best common mode rejec

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GB2 104 330A

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tion the gains of the feedback loops A1, A2 and A2, A3, A4 should be equal. In the course of ensuring equal and opposite excursions on the output terminals the amplifier A2 5 via the path including the amplifiers A3 and A4 ensures that a current in proportion to current in the reference impedance is applied to the output terminal B.

The feedback path consisting of the amplifi-10 ers A5 and A8 and the transistor Q4 has two input conductors 35 and 36. The input conductor 35 is connected via a resistor RA to the non-inverting input of the amplifier A5. The other input conductor 36 is connected via 15 an impedance network ZA to the inverting input of the amplifier A5. The output of the amplifier A5 is connected to the control electrode of a transistor Q4( the drain electrode of which is connected to the inverting input. This 20 provides unity negative feedback and ensures that the amplifier operates within its linear region. The source electrode of the transistor Q4 is connected to the virtual earth of an inverting amplifier A8 having a feedback resis-25 tor R12 between its inverting input and its output.

In operation the feedback path operates as follows: As the inputs of the amplifier A5 essentially take no current the voltage appear-30 ing on the non-inverting input of the amplifier A5 is the same as the voltage on the input conductor 35. The amplifier A5 is a very high gain amplifier working within its linear region, so the voltage on the inverting input must be 35 substantially equal to the voltage on the non-inverting input.

Accordingly, the differential voltage between the input conductors 35 and 36 appears across the impedance ZA. This causes a 40 current to flow that is proportional to this differential voltage. The current cannot flow through the inverting input of the amplifier, so it flows in the local feedback path of the amplifier A5 and through the transistor Q4. 45 This current is unaltered as it passes through the transistor Q4, which has substantially zero current flowing in its control electrode. From there the current passes to the virtual earth point of the amplifier A8. This produces a 50 voltage on the output terminal of the amplifier A8 equal to the product of the current and the feed-back resistor R12.

The combination of amplifiers A5, A8 and the transistor Q4 thus produce a differential 55 voltage sensing amplifier in which the gain is controlled solely by the impedance network ZA and the resistor R12, and is inherenetly equal for the signal on both input conductors. This circuit thus has an extremely good com-60 mon mode signal rejection performance which does not rely on the accurate matching of impedances.

Referring to Fig. 3 as a whole, the components indentifiable to the return loss perfor-65 mance are as follows:

(i) the accuracy of the 2 wire speech sense signal as determined by the precision of R12 and R5 in Fig. 3;

(ii) the accuracy of the speech drive signal 70 minus the 2 wire speech sense signal as determined by the accuracy of R8 and R11;

(iii) the accuracy of ZT defining the impedance;

(iv) the accuracy of the A wire transconduc-75 tance stage as determined by the precision of

R13, R14 and R15;

(v) the accuracy of the balance of the A and B wire current sources (refer to L2 loop).

The components identifiable to the L2 per-80 formance are the matching of sense resistors R1 and R2 and the loop gain assigned to this balancing loop. Error amplifier A2 provides compensation of the loop. The symmetric loading of the A and B wires to earth is also 85 an important consideration in achieving good L2 performance.

The compoents identifiable to the L1 performance involve the matching of the two signal paths from the A2 error amplifier output to 90 the currents flowing into the A and B wires. This involves only 3 pairs of precision matched resistors (i.e. R6, R7, R10, R3, R14, R15).

It is evident that the configuration allows an 95 excellent L2 performance essentially determined by the matching of R1 and R2 ( 60 dB with resistors matched to 0.1%). L1 performance is essentially the matching of 3 pairs of resistors, R7 to R10; R14 to R3 and R6 to 100 R15 50 dB with matching to 0.1%). Return loss performance is most degraded due to the number of components determining the ZT synthesis. However, this is usually the most generously specified of the 3 performance 105 factors.

Fig. 4 shows how the arrangement of Fig. 3 may be implemented in integrated circuit form.

Typically the integrated circuit may be man-110 ufactured by the BIDFET process. This process allows the construction on the same chip of field-effect and bipolar transistors. The amplifiers A1 to A10 employ a mixture of bipolar and field effect transistor constructions. The 115 transistors Q1 to Q4 are double diffused MOS transistors, sometimes known as DMOS.

These typically will have a VDS0 of 200 Volts. Use of this high voltage technology enables the integrated circuit to drive a telephone line 1 20 without the need for output buffer amplifiers.

The invention has wider application than in telephone line drive amplifiers and may also be used for example in high quality audio amplifiers, servo systems, control systems for 125 automatic plant, and the like.

It is also envisaged that an electrical dual of the circuit would be within the scope of the invention i.e. where currents are replaced by voltages and vice-versa.

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GB2 104 330A

4

Claims

1. An amplifier for differentially driving a two wire line including an input circuit, a pair of output terminals, a reference impedance,

5 feedback means coupled to each of the output terminals and to the input circuit for monitoring the signal on the output terminals and deriving therefrom a negative-feedback signal representing the differential signal on the out-1 0 put terminals and for so applying the nega-tive-feedback signal together with the signal at the input circuit to the reference impedance as to cause a signal to appear across the reference impedance dependent on an additive 1 5 combination of the feedback signal and the signal on the input circuit, and output drive means coupled to the reference impedance and to the output terminals responsive to the current flowing in the reference impedance to 20 apply respective currents, each being in proportion thereto, in respective opposite senses, to the output terminals.

2. An amplifier according to claim 1 wherein the feedback means includes a high

25 common mode rejection performance differential input amplifier having two input conductors coupled to respective ones of the output terminals, impedance means so coupled between the conductors that a current flows in 30 the impedance in proportion to the differential voltage of the signal on the conductors and current sensing means coupled to the impedance for sensing the current flow through the impedance and for producing the feedback 35 signal in proportion thereto.

3. An amplifier according to claim 2 wherein the high common mode rejection performance amplifier includes a differential input high gain amplifier one polarity input of

40 which is coupled to be held at the potential of one of the input conductors and the other polarity input is coupled via a second reference impedance to the other conductor, and local feedback means coupled around the 45 high gain amplifier for maintaining said differential input gain amplifier in its linear range of operation.

4. An amplifier according to claim 3 wherein the local feedback means inlcudes a

50 high current gain transistor and the inverting input of the differential input high gain amplifier is coupled to the second reference impedance and the electrode common to the input and output circuits of the transistor, the con-55 trol electrode of which is coupled to the output of the differential input high gain amplifier.

5. An amplifier according to claim 4 wherein the current sensing means includes a

60 high gain amplifier the summing junction of which is coupled to the reference impedance via the transistor for receiving the current ' flowing through the second reference impedance and producing its output the feedback 65 signal.

6. An amplifier according to claim 1 wherein the output drive means includes a respective output amplifier coupled to each of the output terminals and monitoring means 70 coupled to each of the output terminals for monitoring the voltage at the output terminals and for deriving therefrom an error signal representing the difference between the sum of the voltages on the output terminals and a 75 reference potential for so feeding the error signal to each of the output amplifiers to cause a voltage shift at the output terminals in a sense to bring the sum closer to the reference potential.

80

7. An amplifier according to claim 6 wherein for one output amplifier the current proportional to the current flowing in the reference impedance is controlled via the monitoring means and for the other it is 85 controlled directly.

8. A high common mode rejection performance differential input amplifier having two input conductors, impedance means so coupled between the conductors that a current

90 flows in the impedance in proportion to the differential voltage of the signal on the conductors and current sensing means coupled to the impedance for sensing the current flow through the impedance and,for producing an 95 output signal in proportion thereto.

9. An amplifier according to claim 8 including a differential input high gain amplifier one polarity input of which is coupled to be held at the potential of one of the input

1 00 conductors and the other polarity input is coupled via the impedance means to the other input conductor, and feedback means coupled around the high gain amplifier for maintaining said differential input high gain amplifier in its 105 linear range of operation.

10. An amplifier according to claim 9 wherein the feedback means includes a high current gain transistor and the inverting input of the differential input high gain amplifier is

1 1 0 coupled to the impedance means and the electrode common to the input and output circuits of the transistor, the control electrode of which is coupled to the outputof the differential input high gain amplifier. 115 11. An amplifier according to claim 10 wherein the current sensing means includes a high gain amplifier the summing junction of which is coupled to the reference impedance via the transistor for receiving the current 120 flowing through reference impedence and producing at the output signal in proportion thereto.

12. A method of differentially driving a two wire line including the steps of 125 monitoring the line and producing a negative feedback signal proportional to the differential voltage on the line,

applying across a reference impedance the arithmetic combination of the negative feed-1 30 back signal and an input signal.

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GB2104 330A 5

monitoring the current in the reference impedance and applying currents to the wires of the line, each proportional to the current in the reference impedance and in respective 5 opposite senses.

13. An amplifier for differentially driving a two wire line substantially as herein described with reference to Figs. 2, 5, 6 and 7, or Figs 3, 4, 5, 6 and 7 of the accompanying draw-

10 ings.

14. A high common mode rejection performance differential input amplifier substantially as herein described with reference to Fig. 3 of the accompanying drawings.

15

15. A method of differentially drawing a two wire line substantially as herein described with reference to Figs. 1, 2, 5, 6 and 7 or Figs. 1, 3, 4, 5, 6 and 7 of the accompanying drawings.

Printed for Her Majesty's Stationery Office by Burgess & Son (Abingdon) Ltd.—1983.

Published at The Patent Office, 25 Southampton Buildings,

London, WC2A 1AY, from which copies may be obtained.