Classifications

• • G—PHYSICS
  • G01—MEASURING; TESTING
  • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
  • G01R1/00—Details of instruments or arrangements of the types included in groups G01R5/00 - G01R13/00 and G01R31/00
  • G01R1/28—Provision in measuring instruments for reference values, e.g. standard voltage, standard waveform
• • G—PHYSICS
  • G05—CONTROLLING; REGULATING
  • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
  • G05F1/00—Automatic systems in which deviations of an electric quantity from one or more predetermined values are detected at the output of the system and fed back to a device within the system to restore the detected quantity to its predetermined value or values, i.e. retroactive systems
  • G05F1/10—Regulating voltage or current
  • G05F1/46—Regulating voltage or current wherein the variable actually regulated by the final control device is dc
• • G—PHYSICS
  • G01—MEASURING; TESTING
  • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
  • G01R35/00—Testing or calibrating of apparatus covered by the other groups of this subclass
  • G01R35/005—Calibrating; Standards or reference devices, e.g. voltage or resistance standards, "golden" references
• • G—PHYSICS
  • G01—MEASURING; TESTING
  • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
  • G01R35/00—Testing or calibrating of apparatus covered by the other groups of this subclass
  • G01R35/005—Calibrating; Standards or reference devices, e.g. voltage or resistance standards, "golden" references
  • G01R35/007—Standards or reference devices, e.g. voltage or resistance standards, "golden references"
• • H—ELECTRICITY
  • H03—ELECTRONIC CIRCUITRY
  • H03K—PULSE TECHNIQUE
  • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
  • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
  • H03K17/92—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of superconductive devices

Definitions

• the present invention relates to the technical field of voltage sources, more specifically high-precision voltage sources, in particular of metrological precision.
• the invention relates to a voltage source and a method for calibrating the voltage source.
• these sources do not allow a continuous adjustment of the voltage that it delivers, or at the very least do not allow a sufficiently fine or discontinuity-free adjustment.
• the adjustment step of these sources is less than the adjustment step of certain conventional, or non-metrological, voltage sources, that is to say, for example, a resolution less good than 10 microvolts for 1 volt.
• sources of the PJVS type (“Programmable Josephson Voltage Standard” in English, or “programmable Josephson voltage standard” in French)
• the adjustment of such sources generates signals which may have imprecise transient states.
• the present invention provides a solution to the aforementioned problems.
• an electrical voltage source comprising
• an integrated circuit comprising a first input terminal and a second input terminal configured to receive an electrical control signal, a first output terminal and a second output terminal configured to deliver an output voltage, a junction module comprising at least one Josephson junction and which is coupled to the first and second input terminals and to the first and second output terminals in such a way that the value of the output voltage depends on the frequency of the electrical control signal,
• cryogenic module configured to maintain the integrated circuit under conditions in which the integrated circuit is in a superconducting state
• a microwave generator coupled to the first and second input terminals and configured to deliver the electric control signal
• the electric voltage source comprises an adjustment module configured to adjust the amplitude of the electric signal command according to its frequency according to a predetermined rule.
• the predetermined rule comprises the association of at least certain frequency values of the control signal with a respective optimum amplitude value.
• the predetermined rule comprises the association of each frequency of a set of frequencies of the control signal with an optimal amplitude of the control signal for which a Shapiro current of the junction module is non-zero. and preferably greater than a predetermined threshold.
• the predetermined threshold is determined based on the load coupled to the voltage source and/or based on current fluctuations through the junction module caused by its electromagnetic environment. This predetermined threshold is preferably greater than the current consumed by the load, and typically by at least 10 nA in a laboratory cryostat at a temperature of 10 mK.
• the adjustment module is configured to adjust the frequency of the electrical control signal in a predetermined frequency band.
• the predetermined frequency band has a width of at least 5 GHz.
• the predetermined frequency band covers frequencies between 9 and 40 GHz.
• the adjustment module is configured to adjust the frequency of the electrical control signal with an adjustment step less than or equal to 100 kHz.
• the adjustment step is less than or equal to 1 Hz.
• the junction module is coupled to the first and second input terminals via a broadband coupling circuit.
• a broadband coupling circuit is understood here as a circuit configured to transmit a microwave frequency signal with an attenuation variation rate of less than 5dB/10MHz throughout the predetermined frequency band.
• the broadband coupling circuit comprises an electrical path which couples the junction module to the first and second input terminals and whose length is less than the wavelength of the control signal in the integrated circuit, at the maximum frequency of said predetermined frequency band.
• the first input terminal and the second input terminal are coupled to the microwave generator via a microwave transmission line.
• a transmission line is understood here as a material means of transmitting a microwave frequency signal, characterized by a constant characteristic impedance along its length, thus avoiding the appearance of internal reflections creating longitudinal modes, therefore resonances.
• a transmission line may include components such as attenuators or amplifiers, provided that they do not produce an impedance discontinuity.
• the transmission line is a coaxial cable, for example having a characteristic impedance of 50 Ohm.
• the junction module comprises a first junction electrode coupled to the first output terminal and coupled to the first input terminal via a first decoupling capacitor, and a second junction electrode coupled to the second output terminal and coupled to the second input terminal via a second decoupling capacitor.
• the decoupling capacitors can be made directly on the integrated circuit or by any other method ensuring good coupling of the alternating signal between the transmission line and the junction module, while minimizing the coupling of the direct current.
• the junction module comprises a plurality of Josephson junctions.
• At least two of the junctions of the plurality of junctions are mounted in parallel. This makes it possible to increase the maximum current delivered by the source.
• At least two of the junctions of the plurality of junctions are connected in series. This makes it possible to increase the voltage delivered by the source.
• the predetermined rule comprises the association of at least certain frequency values of the control signal with a respective optimum amplitude value by the use of a correspondence table, the modulus of the adjustment being configured to change the voltage source from a first configuration in which the control signal has a first frequency value and a first corresponding optimum amplitude value of the correspondence table, to a second configuration in which the control signal has a second frequency and a corresponding second optimum amplitude from the look-up table.
• a correspondence table is particularly advantageous for linking frequency and amplitude values of the control signal in the absence of a mathematical relationship between these two quantities.
• the adjustment module is configured to interpolate an intermediate amplitude value as a function of at least two amplitude values associated with consecutive frequency values in the correspondence table.
• a method for calibrating a voltage source comprising, for each frequency of a set of frequencies of the control signal, a determination of an optimal amplitude of the signal control for which a Shapiro current of the junction module 12 is non-zero, for example greater than a predetermined threshold, and preferably maximum, and the establishment of a predetermined rule making it possible to associate each frequency with an optimal amplitude corresponding.
• the predetermined threshold is determined based on the load coupled to the voltage source and/or based on current fluctuations through the junction module caused by its electromagnetic environment.
• This predetermined threshold is preferably greater than the current consumed by the load, and typically by at least 10 nA in a laboratory cryostat at a temperature of 10 mK.
• the predetermined rule comprises the association of at least certain frequency values of the control signal with a respective optimum amplitude value by the use of a correspondence table.
• the Shapiro current is a Shapiro current of order 1 or a Shapiro current of order 2.
• the Shapiro current of order n of a Josephson junction is the direct current which circulates between the electrodes of a Josephson junction when an alternating voltage is applied to said electrodes in the presence of a direct component of the voltage between the electrodes of the junction equal to
• Vn n ⁇ f
• the determination of the optimum amplitude comprises a. a polarization of the junction module so that the output voltage is zero and that a non-zero current passes through the junction module, b. a measurement of the output voltage, the measurement being characterized by a measurement uncertainty, c. a determination of a minimum amplitude value of the control signal at which the output voltage varies with a predetermined amplitude, d. an application of a predetermined coefficient to the minimum amplitude value so as to obtain said optimum amplitude value.
• the predetermined amplitude is equal to four times the measurement uncertainty.
• said frequencies of the set of frequencies are spaced apart by a maximum of 100 MHz.
• Figure 1 is a diagram illustrating a voltage source according to the invention
• Figure 2 is an electrical diagram of an integrated circuit of a voltage source according to the invention which supplies an electronic device
• Figure 3 illustrates a first mask used in a manufacturing step of the integrated circuit of Figure 2
• Figure 4 illustrates a second mask used in a second manufacturing step of the integrated circuit of Figure 2
• Figure 5 is a topographic top view of the integrated circuit of Figure 2
• Figure 6 illustrates a first face of a printed circuit board incorporating the integrated circuit of Figure 2
• Figure 7 illustrates a second face of the printed circuit board of Figure 6,
• FIG. 8 illustrates a bias circuit employed in a method for calibrating the voltage source according to the invention
• FIG. 9 illustrates a voltage source calibration system according to the invention
• FIG. 10 illustrates a method for calibrating the voltage source according to the invention
• FIG. 11 illustrates the evolution of the output voltage of the voltage source and of the switching threshold of a junction during an implementation of the method according to the invention
• FIG. 12 illustrates current-voltage characteristics of a junction module of the voltage source of FIG. 1 for different frequency values of the control signal
• Figure 13 illustrates the result of an indirect measurement of the accuracy of the voltage source of Figure 1
• Figure 14 illustrates the results of measurements of the voltage delivered by the voltage source of Figure 1
• Figure 15 illustrates an alternative embodiment of the integrated circuit of Figure 2
• Figure 16 illustrates another alternative embodiment of the integrated circuit of Figure 2.
• the voltage source 1 illustrated in FIG. 1 comprises an integrated circuit 2 placed inside a cryogenic module 3, a microwave generator 4 and an adjustment module 5.
• An electrical device DUT is here powered by voltage source 1.
• the integrated circuit 2 is produced on a semiconductor or insulating substrate, for example here undoped silicon, and comprises conductive portions, for example here aluminum, and insulating portions, for example here aluminum oxide.
• the materials of the integrated circuit 2 are chosen here so that the integrated circuit 2 can be in a superconducting state, subject to suitable temperature conditions imposed in particular by the cryogenic module.
• This circuit 2 is configured to deliver an output voltage Vs and will be described in more detail below.
• the cryogenic module 3 is here a dilution cryostat conventionally comprising a thermally insulating box housing a vacuum chamber comprising a mixing space fed by a circuit for pumping and circulating fluids.
• the fluids used here are conventionally two isotopes of helium, helium 3 and helium 4.
• the cryogenic module 3 makes it possible to reach, in its lower part comprising the integrated circuit 2, temperatures below 100 mK, in particular here a temperature of lOmK.
• the integrated circuit 2 is in a superconducting state, that is to say a state in which its conductive elements do not present any electrical resistance.
• the integrated circuit 2 is controlled by the microwave generator 4 which delivers a control signal 6, here an alternating voltage, which can take on frequency values below 300 GHz.
• the adjustment module 5 is here configured to adjust the amplitude of the electrical control signal 6 as a function of its frequency, according to a predetermined rule.
• the adjustment module 5 is configured to control the microwave generator 4, in particular by imposing the frequency and the amplitude of the control signal 6.
• the adjustment module 5 is a computer conventionally comprising a processor, a memory housing a program code, and a man-machine interface allowing a user to enter certain parameters, in particular the value of the voltage desired Vs output.
• the program code is configured to implement an algorithm translating the desired output voltage value Vs, entered by the user, into a pair of frequency and optimal amplitude values of the control signal 6, linked together by the predetermined rule.
• the adjustment module is configured to deliver to the microwave generator an adjustment signal 7 comprising adjustment instructions relating to the values of the frequency-amplifier pair. optimal study of the control signal 6.
• the possible values of the optimum frequency-amplitude couple of the control signal are here recorded in a correspondence table stored in the memory of the adjustment module 5.
• the correspondence table here defines the predetermined rule.
• the correspondence table comprises a list of frequencies included in a predetermined frequency band whose width is at least 5 GHz, and in particular here whose width is 40 GHz and which extends in this example between 0 and 40 GHz.
• the frequencies of the correspondence table are spaced here by a step of 100 MHz, each of these frequencies being associated with a corresponding optimum amplitude.
• the adjustment module 5 is here configured to interpolate the intermediate frequencies, that is to say the frequencies included in the predetermined frequency band but not present in the correspondence table, as well as the intermediate optimum amplitudes corresponding at intermediate frequencies.
• the adjustment module 5 can adjust the control signal with other frequency and amplitude values than those present in the table correspondence, by means of an interpolation using the amplitude values associated respectively with at least two frequencies of the correspondence table, for example here two frequencies.
• the adjustment module 5 is configured to adjust the frequency of the control signal with a step of 10 KHz.
• the microwave generator 4 is configured to generate the control signal 6 in the predetermined frequency band.
• the integrated circuit 2 illustrated schematically in Figure 2, comprises a first input terminal 8 and a second input terminal 9 configured to receive the control signal 6.
• the integrated circuit 2 further comprises a first output terminal 10 and a second output terminal 11 configured to deliver the output voltage Vs.
• the integrated circuit 2 comprises a junction module 12 here comprising a Josephson junction 13, of which a first junction electrode 14 is conductively coupled, that is to say by a connection with contact (non-capacitive) to the first output terminal 10 and to the first input terminal 8 via a first decoupling capacitor 16, and of which a second electrode junction 15 is conductively coupled to the second output terminal 11 and to the second input terminal 9 via a second decoupling capacitor 17.
• the first decoupling capacitor 16 here has a capacitance of 10 pF and the second decoupling capacitor 17 here has a capacitance of 10 pF.
• a capacitive module 18 is coupled between the first output terminal 10 and the second output terminal 11.
• the capacitive module 18 comprises a third capacitor 19 and a fourth capacitor 20 coupled in series between the first output terminal 10 and the second output terminal 11.
• the role of the capacitive module 18 is to reduce the AC component of the current flowing through the junction module by providing a low impedance path to the high frequency signals, thus reducing the possible chaotic effects resulting from the feedback between the junction module and the control signal.
• the third capacitor 19 and the fourth capacitor 20 have values at least 100 times greater than the value of the intrinsic capacitance of the junction module 12, for example here values of at least 10 picofarads.
• Vs is the DC component of the voltage between the junction electrodes 14 and 15.
• the first and second input terminals 8, 9 are coupled to the microwave generator 4 via a microwave transmission line 21 comprising a first conductor 22 coupled to the first input terminal. 8 and a second conductor 23 coupled to the second input terminal 9 and to ground GND.
• the transmission line 21 is a coaxial cable with an impedance of 50 Ohms.
• the first output terminal 10 and the second output terminal 11 are here coupled to the electronic device DUT so that it is powered by the voltage source 1.
• the output voltage Vs depends on the frequency of the control signal 6.
• the output voltage Vs depends on the frequency of the control signal in such a way that a variation of 1 Hz in the frequency of the control signal 6 causes a variation in the output voltage Vs of 2.06783383 femtovolts.
• Figures 3 to 5 illustrate the manufacturing steps of the integrated circuit 2.
• a first stack of the circuit is deposited through a first mask M1 (shown in FIG. 3) made up of two layers of superimposed resins, the lower layer having a thickness of about 2 ⁇ m and the upper layer, of a thickness of about 1.5 ⁇ m, being photosensitive.
• the mask M1 has a first opening M10 and a second opening M11 produced by optical lithography followed by development.
• the two-layer structure of the first mask M1 allows the formation of a bridge PT formed by the upper resin layer, that is to say an area of approximately 1 ⁇ m by 4 ⁇ m which separates the two openings M10 and Mil, with the bottom resin layer fully dissolved below deck.
• This bridge known in particular under the name "Dolan bridge” allows the realization of a Josephson junction, as described below.
• the formation of the first stack of the circuit comprises a deposition of a first sub-layer of aluminum 30 nanometers thick at a non-zero deposition angle, so that part of the deposition takes place under the bridge PT.
• the deposition angle is an angle of +26°, defined by rotation around the longitudinal axis of the bridge PT, the zero angle corresponding to a direction perpendicular to the substrate.
• the first manufacturing step further comprises oxidation of the first aluminum sub-layer under 200 millibars of oxygen for 10 minutes, so as to form a layer of aluminum oxide on the first aluminum sub-layer.
• a first portion of the first stack of the circuit, located above a first zone of the substrate corresponding to the first opening M10, will form, once the manufacturing process is completed, the first output terminal 10, a first electrode of the first capacitor 16, a first electrode of the third capacitor 19, and the first junction electrode 14.
• a second portion of the first stack of the circuit, located above a second zone of the substrate corresponding to the second opening Mil, will form the second output terminal 11, a first electrode of the second capacitor 17, a first electrode of the fourth capacitor 20, and the second junction electrode 15.
• two successive depositions are carried out using a second mask M2 (shown in FIG. 4) comprising a first opening M20, a second opening M21 and a third opening M22 , a second stack of the circuit comprising a lower insulating layer with a thickness of 100 nanometers, for example here an aluminum oxide layer, and an upper layer with a thickness of 200 nanometers, for example here an aluminum layer.
• a second mask M2 shown in FIG. 4
• the mask M2 is then dissolved in order to get rid of the material evaporated during the second step on the undeveloped areas of the mask.
• a first portion of the second stack of the circuit forms the first input terminal 8 and forms, where it partially covers the first portion of the first stack of the circuit above the first zone of the substrate, the dielectric and a second electrode of the first capacitor 16.
• a second portion of the second stack of the circuit forms the second input terminal 9 and forms, where it partially covers the second portion of the first stack of the circuit above the second zone of the substrate, the dielectric and the second electrode of the second capacitor 17.
• a third portion of the second stack of the circuit partially covers the first portion and partially the second portion of the first stack above a third zone 34 of the substrate corresponding to the third opening M22 and thus forms the second electrode of the third capacitor 19 and the second electrode of the fourth capacitor 20°.
• FIG. 5 A top view of the integrated circuit 2 obtained by the manufacturing process described above is illustrated in Figure 5.
• the integrated circuit 2 extends here over a surface of 280x205 square micrometers, and could as a variant extend over any surface insofar as the circuit allows broadband coupling of the control signal between the input terminals 8, 9 and the junction electrodes 14, 15.
• the dimensions of the openings of the masks M1 and M2, and therefore the dimensions of the integrated circuit 2 are chosen in such a way that an electric signal flowing between the first input terminal 8 or the second input terminal 9 and the junction module 12 travel a distance less than the wavelength of the control signal 6 at the maximum frequency of the band of predetermined frequencies (here 40 GHz). For example here, this distance is equal to 140 micrometers.
• Figures 6 and 7 respectively illustrate a first face 35 and a second face 36 of a printed circuit board 37 to which the integrated circuit 2 is fixed and connected.
• the printed circuit board 37 can be equipped connectors and placed in a protection and electrical shielding box.
• the first output terminal 10 and the second output terminal 11 are here electrically coupled respectively to a first metal track 38 of the card 37 via a first conductive wire 40 and to a second metal track 39 of the card 37 by a second conductive wire 41.
• the metal tracks 38, 39 are here made of copper and the conductive wires 40, 41 are here made of aluminum and made by micro-welding.
• the wires 45 and 46 have a length of less than 1 millimeter.
• the first and second metal tracks 38, 39 extend here on the first face 35 of the printed circuit board 37, respectively up to a first crossing via 42 and a second crossing via 43 configured to allow electrical contact. from the second face 36 of the card.
• the through vias 42, 43 are for example here configured to allow the connection of a connector on the second face 36 of the card.
• the first input terminal 8 and the second input terminal 9 are each coupled to a connector 44 for a microwave transmission line, here a connector for coaxial cable, respectively by a third conductive wire 45 and a fourth conductive wire 46, for example here aluminum wires produced by microwelding.
• the connector 44 is here connected at the surface by compression at the level of the second face 36, and electrically coupled to the first face 35 by a via suitable for transmitting microwave frequency signals.
• FIG. 8 illustrates a bias circuit 47 configured to be coupled to the integrated circuit 2 during a calibration method according to the invention.
• the bias circuit 47 is in particular configured to cause a current to flow through the junction module 12 and to vary the value of this current.
• the bias circuit 47 comprises a first bias terminal 48 and a second bias terminal 49 configured to be coupled respectively to the first output terminal 10 and to the second output terminal 11.
• the bias circuit 47 is here coupled to a voltage generator 50 configured to deliver a bias voltage Vb and comprises a first resistor R1 and a second resistor R2 with a value of 10 kilo-ohms each, a third resistor R3 and a fourth resistor R4 with a value of 50 ohms each, and a fifth resistor R5 with a value of 20 ohms.
• a first terminal BC1 of the fifth resistor R5 is common to the first resistor R1 and to the third resistor R3 and a second terminal BC2 of the fifth resistor R5 is common to the second resistor R2 and to the fourth resistor R4.
• a second terminal of the first resistor R1 is coupled to the positive terminal of the voltage generator 50, a second terminal of the second resistor R2 is coupled to the negative terminal of the voltage generator.
• a second terminal of third resistor R3 is coupled to first bias terminal 48 and a second terminal of fourth resistor R4 is coupled to second bias terminal 49.
• the calibration system 51 illustrated in FIG. 9 comprises the voltage source 1 as previously described in connection with FIG. 1, a calibration box 52 comprising the bias circuit 47, the voltage generator 50, a module measurement 54, here an oscilloscope, configured to measure the output voltage Vs and the current through the junction module 12, which is equal to the voltage across the terminals of the resistor R3 divided by the value of the resistor R3, and to transmit the measured values to the adjustment module 5, as well as a switching module 53 configured to switch the system from a first configuration in which the system 51 can be calibrated to a second configuration in which the system 51 is, from a functional point of view, identical to the current source 1 illustrated in figure 1.
• a calibration box 52 comprising the bias circuit 47, the voltage generator 50, a module measurement 54, here an oscilloscope, configured to measure the output voltage Vs and the current through the junction module 12, which is equal to the voltage across the terminals of the resistor R3 divided by the value of the resistor R3, and to transmit the measured values to the adjustment module 5, as well as a switching
• the switching module 53 comprises for example an electrical system for controlling an electromechanical relay making it possible to simultaneously open or close the electrical path between terminal 48 of the polarization module and terminal 10 of the junction module, and the electrical path between terminal 49 of the bias module and terminal 11 of the junction module.
• the switching module 53 controls the coupling of the bias circuit 47 to the integrated circuit 2.
• the voltage generator 50 and the switching module 53 are controlled by the adjustment module 5.
• the voltage source 1 calibration method is implemented here by the calibration system 51. It comprises, for each frequency of the control signal 6 in the predetermined frequency band, a determination of the optimum amplitude of the control signal 6 for which the Shapiro current of order 1 of the junction module 12 is maximum, or alternatively greater than a predetermined threshold, for example a threshold chosen according to the current fluctuations through the junction module caused by its electromagnetic environment.
• a predetermined threshold for example a threshold chosen according to the current fluctuations through the junction module caused by its electromagnetic environment.
• This predetermined threshold is preferably greater than the current consumed by the load, and typically by at least 10 nA in a laboratory cryostat at a temperature of 10 mK.
• the method further comprises a recording in a correspondence table stored in the memory of the computer 50 of each optimal frequency-amplitude pair thus determined.
• FIG. 10 illustrates steps E1 to E7 of an example of implementation of the method according to the invention.
• the amplitude of the control signal 6 is set to a zero value.
• the amplitude is adjusted by adjustment module 5 via adjustment signal 7, which deactivates microwave source 4.
• the adjustment module 5 adjusts the voltage generator 50 so that the bias voltage Vb is such that the junction module has a zero voltage between its electrodes 14, 15 and is traversed by a low current, or calibration current Ib.
• the bias voltage Vb is chosen so that the value of the current Ib is less than the critical current Ie of the junction, for example less than a tenth of the critical current Ie of the junction.
• the calibration current is equal to one thirtieth of the value of the critical current Ie, that is to say here equal to a value of 10 nA.
• the output voltage Vs is thus zero.
• the value of the bias voltage Vb is for example determined according to the values of the resistors R1, R2, R3, R4 and R5 of the bias circuit 47, the characteristics of the junction module 12, in particular the number of junctions, the material and the dimensions of each junction and according to the performance of the measurement system 54.
• the critical current Ie of a Josephson junction is conventionally defined as being the maximum supercurrent value that can cross the junction or the junction module, that is to say here the maximum value of the current that can flow between the junction electrodes 14 and 15 at zero voltage.
• the value of the critical current of the junction module 12 is equal to 300 nanoamperes.
• the adjustment module 5 adjusts the frequency of the control signal 6 so that the control signal has a current frequency whose value is chosen from the predetermined frequency band.
• the adjustment module 5 varies the amplitude of the control signal 6, between an initial amplitude value Ai, for example here -60 dBm and a final amplitude value Af, for example here 0 dBm.
• the amplitude variation can be done continuously, or discretely, for example by choosing the amplitude values from a pre-established list.
• the variation can be linear or logarithmic between the initial amplitude value Ai and the final value Af.
• the application of the control signal 6 to the junction module 12 has the effect of modifying the switching threshold 10 of the supercurrent, that is to say the supercurrent threshold for which the junction module switches.
• the switching of a Josephson junction initially traversed by a Shapiro current of order n corresponds to a change of state of the junction during which, in particular, the DC component of the voltage between the electrodes of the junction , here the output voltage Vs, changes from its current value Vn, here the zero value, to another value.
• the switchover is triggered by an increase in the Shapiro current of order n, here the supercurrent (order 0), so as to reach the switchover threshold.
• the switching threshold 10 of the supercurrent is varied.
• the curve with a solid line represents the evolution of the switching threshold 10 of the supercurrent as a function of the amplitude A of the control signal 6; the broken line curve schematically represents the evolution of the output voltage Vs as a function of the amplitude A.
• the value of the output voltage Vs is measured so as to determine the minimum amplitude value of the control signal 6 for which the switching threshold 10 of the supercurrent is equal to or less than the value of the calibration current Ib flowing in the junction, here called the first cancellation amplitude.
• the junction module 12 switches, that is to say here behaves like an open circuit, and the voltage between junction electrodes 14, 15 increases and becomes non-zero.
• non-zero voltage values Vs are measured here around three amplitude values A1, A2, A3. More precisely here, around each of these three amplitude values A1, A2, A3, the voltage Vs presents a measurable deviation forming a voltage plateau. Thus, at these points, the junction module behaves like an open circuit and the output voltage Vs is non-zero. It can therefore be deduced that around these three amplitude values Al, A2, A3, the switching threshold 10 of the supercurrent is less than or equal to the calibration current Ib.
• the minimum amplitude value is the Al value.
• the values Al, A2 and A3 can be estimated as the values located in the middle of each of the tension plates.
• the Al value is a reasonable approximation of the first cancellation amplitude.
• a first predetermined coefficient is applied to the first cancellation amplitude Al, so as to obtain the optimum amplitude value for which, at the current frequency, the Shapiro current of order 1 of the junction module is maximum, or alternatively greater than the predetermined threshold.
• the first predetermined coefficient is determined heuristically at the start of calibration at any frequency value and corresponds to the ratio between the first optimum amplitude and the first cancellation amplitude.
• the predetermined coefficient is identical for all the frequencies of the predetermined frequency band.
• the predetermined coefficient is less than 1.
• the heuristic determination of the predetermined coefficient can be made on the basis of a measurement of the current-voltage characteristic of the junction module, as a function of the amplitude of the control signal, by iteratively searching for the amplitude of the control signal that minimizes the supercurrent.
• a good starting value for the search for the predetermined coefficient is for example 0.7656.
• the current-voltage characteristic of a junction module is defined as the set of points (l,V) such that V is the DC voltage across the terminals of the junction module and I is the DC current passing through the junction module. , equal to the voltage across resistor R3 divided by the value of resistor R3 of bias circuit 47.
• the current-voltage characteristic is obtained by measuring the values l,V for several values of the bias voltage Vb produced by the generator 50 in an appropriate assembly.
• a suitable set of bias voltages Vb for measuring the current-voltage characteristic is for example a set of 1000 values between a minimum value and a maximum value, the minimum value and the maximum value being preferably opposite, the maximum value resulting in a voltage value at the terminals of the junction module equal to at least 2*D/e, with e the load of the electron and D the energy of the superconducting gap of the material of the electrodes of the junction module.
• the current frequency/optimal amplitude pair is recorded in the correspondence table.
• a seventh step E7 if the value of the current frequency is not equal to the maximum frequency value of the predetermined frequency band, the value of the current frequency is incremented and the method resumes at the third step.
• the incrementation of the value of the current frequency is here an incrementation of 100 MHz, but can take any value suitable for the implementation of an interpolation, for example 50 Hz, 10 KHz or even 1 Hz.
• the calibration method ends when steps E3 to E6 have been implemented for all the possible frequency values of the predetermined frequency band, taking into account the chosen incrementation.
• the voltage source 1 as described previously can be used according to the following steps.
• the failover module disconnects the bias circuit 47 from the voltage source 1.
• a desired output voltage value Vss is entered via the adjustment module 5, for example via the man-machine interface of the adjustment module 5.
• the control signal 6 having the frequency f and the cancellation amplitude Al is applied to the junction module 12, in order to minimize the supercurrent switching threshold.
• the zero voltage switching threshold being zero
• the current fluctuations, in particular the parasitic fluctuations produced by the experimental environment cause the junction to switch to a non-zero voltage state.
• the amplitude of the control signal 6 is then adjusted to the optimum value, so that the switching threshold of the Shapiro current of order 1 is maximum, which allows the voltage source 1 to supply a current maximum.
• the presence of a maximum current minimizes the source's susceptibility to spurious fluctuations that could cause the junction module to switch to a different, undefined voltage, thus preventing a malfunction of voltage source 1.
• the adjustment module selects an optimum frequency/amplitude pair from the correspondence table and applies the control signal having these frequency and amplitude values.
• the passage time from one pair of values to another is preferably less than 1 ms.
• FIG. 12 illustrates the current-voltage characteristics of the junction module 12 for five frequency values: one curve (No MW) corresponds to the absence of a control signal and four other curves correspond to frequency values of 10 GHZ, 20 GHz, 30 GHz and 40 GHz, where at each frequency the amplitude of this signal is adjusted to maximize the Shapiro current of order 1.
• Each curve superimposes two current-voltage characteristics: one measured at voltage Vs increasing, the other at decreasing voltage Vs. They differ due to the hysteretic nature of the Josephson junctions.
• FIG. 12 four broken lines represent the current-voltage values for which a Shapiro current of order 1 appears. Only seven features are shown in Figure 12 for simplicity; however, measurements carried out for all the possible frequencies of the control signal make it possible to deduce that at least for any frequency greater than or equal to 8 GHz, it is possible to maintain a non-zero Shapiro current, making possible the step of locking previously described.
• Figure 13 illustrates the result of a measurement of the accuracy of the voltage source
• a measurement device is coupled between the first output terminal 10 and the second output terminal 11, instead of the electrical device DUT.
• the measuring device is here configured to receive a direct voltage and to deliver an alternating voltage, the spectral density of which is representative of the precision of the voltage source 1.
• the measurement module operates analogously to the voltage source, with the difference that its input signal is a direct voltage and that it delivers an alternating voltage.
• An emission peak is observed here at approximately 15380 MHz which corresponds to a voltage Vs of 31.8 pV.
• the width of this emission peak is proportional to the DC voltage noise provided by voltage source 1. It can be deduced from the width at mid-height emission peak, here 60 kHz, that the relative precision of the source of voltage is at least 4*10 -6 , that is to say that the voltage source provides a noise of 125 picovolts for 31.8 microvolts of signal.
• FIG. 14 represents two measurements of the output voltage of voltage source 1 as a function of time when the frequency of the control signal is varied.
• a first curve El relates to a measurement carried out over a period of approximately 70 seconds when the voltage source operates according to the embodiment described previously, that is to say when the current of Shapiro of order 1 of the junction module is maximal, when the frequency of the control signal varies from 12 GHz to 40 GHz.
• the duration of 70 seconds corresponds to the duration of data acquisition and does not indicate a time limit for latching the voltage source.
• the mode of implementation of the calibration method described here is in no way limiting and it is possible to apply the calibration method to a higher order Shapiro current.
• the use of a Shapiro current of order n makes it possible to divide by n the frequency of the control signal required to obtain the same voltage
• the calibration method according to the invention comprises, for each frequency of the control signal 6 in the predetermined frequency band, a determination of the optimum amplitude of the control signal 6 for which the second-order Shapiro current of the junction module 12 is maximum.
• step E6 a second optimal value is determined, which corresponds to the amplitude of the control signal which maximizes the second order Shapiro current, or alternatively for which the second order Shapiro current is greater than a second predetermined threshold.
• the second optimum value is equal to the first cancellation amplitude to which a second predetermined coefficient has been applied, which is determined analogously to the first predetermined coefficient, with the difference that it corresponds to the ratio between the second amplitude optimal and the first cancellation amplitude.
• An indicative value of this coefficient is 1.2700.
• the second optimal amplitude values are recorded in the correspondence table so as to be each associated with their respective current frequency.
• voltage source 1 can be used analogously to what was described previously in connection with operation on a Shapiro current of order 1, with the difference that:
• the control signal 6 having the frequency f and the first cancellation amplitude is applied to the junction module 12, in order to minimize the supercurrent switching threshold.
• An additional step includes a minimization of the Shapiro current of order 1 by applying a second cancellation amplitude, that is to say here the non-zero minimum amplitude of the control signal 6 which cancels the Shapiro current of order 1.
• the Shapiro current of order 2 is non-zero and current fluctuations cause the junction to switch to a stable state at the desired voltage value.
• the second cancellation amplitude is equal to the first cancellation amplitude to which a third predetermined coefficient has been applied.
• the third coefficient is determined analogously to the first predetermined coefficient, except that it corresponds to the ratio between the second cancellation amplitude and the first cancellation amplitude.
• An indicative value of this coefficient is 1.5933.
• the Shapiro current of order 2 is maximized by adjusting the amplitude of the control signal 6 to the second optimum value.
• the adjustment module 5 selects an optimum frequency/second amplitude pair in the table correspondence and applies the control signal having these values.
• the curve E2 of FIG. 14 relates to a measurement of the output voltage Vs carried out for approximately 8 seconds when the voltage source 1 operates according to this last embodiment, that is to say when the current second order Shapiro of the junction module is maximal, by varying the frequency of the control signal from 9 to 39.5 GHz. It is observed that the output voltage Vs varies from approximately 37 microvolts to approximately 163 microvolts, according to a second metrological proportionality coefficient equal to 2*h/2e*f. The duration of 8 seconds corresponds to the duration of data acquisition and does not indicate a time limit for latching the voltage source. The part of the curve E2 close to zero voltage comes from the fact that the data acquisition started a fraction of a second before locking.
• the correspondence tables described previously comprise the optimal frequency/amplitude pairs, the optimal amplitudes of each pair being obtained by applying a predetermined coefficient to the first cancellation values. Go- laughing, it would be possible for the correspondence tables to include the frequency/first cancellation amplitude pairs, and for the adjustment means to be configured to automatically apply the adapted predetermined coefficient during operation of the voltage source.
• the source so that it sequentially delivers different output voltage values, each output voltage value being obtained by the method described previously.
• the junction module 12 comprises a single Josephson junction 13.
• the junction module 12 could comprise a plurality of Josephson junctions connected in series or, as shown in Figure 16 the junction module 12 could comprise a plurality of Josephson junctions connected in parallel.
• the junction module 12 may also comprise both Josephson junctions mounted in series and Josephson junctions mounted in parallel.
• the Josephson junctions are preferably made so as to be identical to each other so that the switching events occur. simultaneously for all junctions of the module.
• the invention is compatible with any type of cryostat insofar as this makes it possible to place the integrated circuit 2 in a state superconductor, that is to say subject to possibly adapting the materials of the integrated circuit 2.
• the invention is for example compatible with a helium bath cryostat and with a pulsed tube cryostat which make it possible to achieve temperatures close to 4K, the conductive elements of the integrated circuit then being made for example of Nobium.
• the procedure for producing the insulating barrier separating the two electrodes 14, 15 from the junction 12 can then include depositing a few nanometers of insulating material, or depositing a few nanometers of aluminum followed by total or almost total oxidation.
• the adjustment module 5 described previously makes it possible to adjust the amplitude and the frequency of the control signal by controlling the microwave generator 4.
• the adjustment module 5 does not not control the microwave generator 4 but comprises attenuators and/or amplifiers configured to receive the control signal 6, to carry out amplification and/or attenuation operations, and to transmit the amplified control signal and /or attenuated to the integrated circuit 2.
• the adjustment module 5 comprises a computer which controls said attenuators and/or said amplifiers.
• the calibration method described above comprises a measurement of the output voltage Vs and a detection of a variation of the output voltage Vs which corresponds, after application of a predetermined coefficient, to a optimum amplitude value for which the Shapiro current of order 1 of the junction module 12 is maximum
• it would be possible, in order to determine this amplitude value to determine the current-voltage characteristic of the junction module for each amplitude possible or for a plurality of possible amplitudes of each current frequency of the control signal, and to determine for each frequency value, the current-voltage characteristic established having the highest Shapiro current value of order 1 in order to obtain the optimal amplitude directly.

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• 2020
  • 2020-09-17 FR FR2009405A patent/FR3114171B1/fr active Active
• 2021
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