EP4200963A1 - Procédé et appareil de détermination d'un courant d'arrêt moyen ou d'une tension d'entrée ou de sortie dans un convertisseur élévateur ou abaisseur - Google Patents

Procédé et appareil de détermination d'un courant d'arrêt moyen ou d'une tension d'entrée ou de sortie dans un convertisseur élévateur ou abaisseur

Info

Publication number
EP4200963A1
EP4200963A1 EP21755455.9A EP21755455A EP4200963A1 EP 4200963 A1 EP4200963 A1 EP 4200963A1 EP 21755455 A EP21755455 A EP 21755455A EP 4200963 A1 EP4200963 A1 EP 4200963A1
Authority
EP
European Patent Office
Prior art keywords
voltage
time
potential
parameter
current
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
EP21755455.9A
Other languages
German (de)
English (en)
Inventor
Markus Michels
Dennis Bura
Michael JIPTNER
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Robert Bosch GmbH
Original Assignee
Robert Bosch GmbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Robert Bosch GmbH filed Critical Robert Bosch GmbH
Publication of EP4200963A1 publication Critical patent/EP4200963A1/fr
Pending legal-status Critical Current

Links

Classifications

    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R19/00—Arrangements for measuring currents or voltages or for indicating presence or sign thereof
    • G01R19/25—Arrangements for measuring currents or voltages or for indicating presence or sign thereof using digital measurement techniques
    • G01R19/2503—Arrangements for measuring currents or voltages or for indicating presence or sign thereof using digital measurement techniques for measuring voltage only, e.g. digital volt meters (DVM's)
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0009—Devices or circuits for detecting current in a converter
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R19/00—Arrangements for measuring currents or voltages or for indicating presence or sign thereof
    • G01R19/175—Indicating the instants of passage of current or voltage through a given value, e.g. passage through zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • Method and device for determining a parameter, the parameter characterizing a voltage or a current in a circuit arrangement
  • the invention relates to a method and a device for determining a parameter, the parameter characterizing a current or a voltage in a circuit arrangement. Furthermore, the invention relates to a voltage estimator, a drive train with a corresponding device and a vehicle with a drive train as well as a computer program and a machine-readable storage medium.
  • Circuit arrangements for active voltage converters for use in vehicles are known from the prior art. High demands are placed on the power density and the efficiency of the voltage converters. In order to minimize the size of the passive components, in particular the inductors, chokes or transformers, the voltage converters are operated with high switching frequencies in the range of a few 100 kHz. In order to ensure high efficiency at the same time, the switching elements or power semiconductors used in the active voltage converters are switched on softly, which is also known as "zero voltage switching" (ZVS). The regulation of such systems while at the same time ensuring the ZVS represents a major technical challenge.
  • ZVS zero voltage switching
  • ZCD zero current detection
  • a method for determining a parameter is provided, the parameter characterizing a current or a voltage in a circuit arrangement.
  • the circuit arrangement includes an inductor, with an alternating inductor current flowing through the inductor.
  • the method comprises the steps: determining at least a period of time between two zero crossings of the inductor current or a period of time between a zero crossing and a corner point of the inductor current; Determination of the parameter as a function of the determined period of time.
  • a method is provided in which a parameter is determined, the parameter characterizing a current or a voltage in a circuit arrangement.
  • the circuit arrangement includes an inductor.
  • the inductance is preferably a choke or a primary or secondary winding of a transformer, which is preferably used in a DC voltage converter or in a charging device, preferably for galvanic isolation of the input and output.
  • An alternating choke current flows through the inductance. Alternating means that the inductor current alternately assumes negative and positive values. So that the inductor current alternates, the inductor is connected alternately to a first potential, preferably positive potential, and a second potential, preferably negative potential, at a first connection of the inductor. The result is a choke current through the inductance, which alternately increases linearly up to a positive maximum and then decreases linearly to a negative minimum and so on.
  • the point in time at which the inductor current reaches the positive maximum is referred to below as the positive corner point.
  • the point in time at which the inductor current reaches the negative minimum is referred to below as the negative corner point.
  • the change from linearly increasing to linearly decreasing, or vice versa takes place when changing the one-sided connection of the inductance from the first potential to the second potential, or vice versa.
  • the sign of the inductor current changes from positive to negative at a so-called, preferably first, zero crossing of the inductor current.
  • the first connection of the inductance is preferably connected to the first potential and the second potential by means of a half-bridge with two switching elements, a first switching element being connected to the first potential on the one hand and being connected to a center tap of the half-bridge on the other hand, and a second switching element on the one hand to is connected to the second potential and on the other hand is connected to the center tap of the half-bridge, the inductor being connected on one side to the first terminal with the center tap.
  • one switching element is preferably alternately switched on while the other is switched off.
  • the timing of the triggering erns at least one of the switching elements at one of the points in time at which the inductor current reaches either the positive maximum or the negative minimum.
  • the inductance is preferably connected to a second connection with a third potential. So that the first and the second potential are different, an input voltage between two potentials of the first, second or third potential is preferably present.
  • the input voltage is preferably an AC voltage or a DC voltage.
  • the frequency of the input voltage is preferably very much lower, preferably at least one order of magnitude lower, than the frequency of the alternating inductor current. An approximately constant voltage then preferably results during a period of the alternating inductor current.
  • At least one time period between two zero crossings of the inductor current is determined by means of one step of the method.
  • the time period between a first zero crossing of the inductor current, at which the sign changes from positive to negative, and an immediately following second zero crossing of the inductor current, at which the sign changes from negative to positive or vice versa is preferably determined.
  • a period of time between a zero crossing and a corner point of the inductor current, preferably between a second zero crossing and a positive corner point of the inductor current is determined.
  • a zero crossing is understood as a point in time at which the sign of the alternating inductor current changes from positive to negative or vice versa.
  • the parameter is determined as a function of the determined time period.
  • a method is advantageously provided which makes it possible to determine a parameter as a function of a time variable which is determined in connection with the zero crossings of an inductor current, the parameter characterizing a current or a voltage in a circuit arrangement.
  • No current or voltage sensor is required for this. Instead, the time period between two zero crossings or the time period between the corner point and the zero crossing is advantageously used in order to obtain information such as a mean value or peak values of the inductor current or a voltage internally. to be determined within the circuit arrangement.
  • the parameter to be determined is preferably the mean current value of the inductor current, with the mean current value preferably corresponding to or correlating with the value of the input current of the circuit arrangement.
  • Both ZCD methods make use of the fact that the mean value of the (ripple-prone) inductor current in L is equal to the input current l_avg.
  • a status estimate is preferably set up based on these newly obtained parameters or measured values.
  • one or more whole periods can advantageously elapse before the state estimator reacts. Therefore, a plausibility check and error detection of a ZCD signal can preferably be carried out, which increases the quality.
  • a less expensive microcontroller can advantageously be used since more time is available for the required computing operations.
  • further regulators preferably a voltage regulator, can preferably be used for a number of variables.
  • a regulation for the current reversal points or the switching frequency can preferably also be set up independently of the mean value of the inductor current. Using this method, the inductor current to be regulated can preferably be detected in a highly dynamic manner (every switching period).
  • the current sensor that would otherwise be required can be saved, or a cheaper sensor with a smaller bandwidth can be used. Additional state estimates based on the zero-crossing times advantageously result in potential savings for additional sensors.
  • the parameter for controlling a voltage converter is preferably used as the feedback variable of a control circuit, preferably a voltage regulator.
  • the method in another embodiment, relates to determining a parameter, the parameter characterizing a voltage between a first potential and a second potential in the circuit arrangement.
  • the circuit arrangement includes a half-bridge with a first switching element and a second switching element.
  • the first switching element is connected to a first potential on the one hand and is connected to a center tap of the half-bridge on the other hand.
  • the second switching element is connected to a second potential on the one hand and to the center tap of the half-bridge on the other hand.
  • the inductor is connected to a first connection with the Center tap connected and connected to a second terminal with a third potential. An input voltage is present between the first potential and the third potential.
  • the method comprises the steps: Alternately driving, or switching on and off, the first and the second switching element with a definable duty cycle, resulting in the alternating inductor current through the inductance; Determining a first time period between a first zero crossing of the current and the activation of at least one of the switching elements and determining a second time period between the activation of the at least one switching element and a second zero crossing of the current, determining the parameter as a function of the input voltage, the first time period and the second duration.
  • a method for a circuit arrangement is advantageously provided which makes it possible to determine a parameter as a function of a time variable which is determined in connection with the zero crossings of the inductor current, the parameter characterizing a voltage present in the circuit arrangement.
  • a first capacitor is connected to the first and the second potential and the parameter to be determined is a mean voltage value of the voltage that is present at the first capacitor.
  • determining the first time period and the second time period includes determining a first point in time of a first zero crossing of the inductor current and determining a second point in time of a control process of at least one of the switching elements and determining a third point in time of a second zero crossing of the inductor current.
  • Determining the first period of time and the second period of time preferably includes determining the first point in time at which the sign of the inductor current changes from negative to positive, then determining a nes second point in time at which at least one of the switching elements is activated, and the subsequent determination of a third point in time at which the sign of the inductor current changes from positive to negative, or vice versa.
  • the instants of the zero crossings are preferably determined by means of a sensor which detects the zero crossing, preferably by means of a current sensor or by means of a signal obtained inductively.
  • a method for determining the first, second and third points in time is advantageously provided.
  • a counter preferably a microcontroller, is used to determine the first period of time between the first and second points in time and/or the second period of time between the second and third points in time.
  • a time duration that can be determined using simple technical means is the use of a counter, preferably a microcontroller.
  • Each microcontroller has a counter that continues to count at equidistant time intervals. The elapsed time period can consequently be determined from the difference in the counter readings from the second to the first point in time and/or from the third to the second point in time.
  • a method is advantageously provided for determining the length of time between the points in time.
  • the invention also relates to a computer program, comprising instructions which, when the program is executed by a computer, cause the latter to execute the methods described or the steps of the method.
  • the invention relates to a computer-readable storage medium, comprising instructions which, when executed by a computer, cause the latter to carry out the methods described or the steps of the method. Furthermore, the invention relates to a voltage estimator for determining and outputting an estimated voltage between a first potential and a second potential, the voltage estimator comprising a logic unit and an estimator, the logic unit being set up to use a method for determining a parameter according to claims 1 to 5, the estimator being set up to predict a model-based voltage between the first potential and the second potential as a function of input variables, and to determine and output the estimated voltage as a function of the predicted model-based voltage and the determined parameter.
  • a voltage estimator for determining and outputting an estimated voltage.
  • the voltage estimator includes a logic unit for determining a parameter according to the method described.
  • the voltage estimator also includes an estimator, preferably a state estimator, for example using a Kalman filter or a Lüneberger observer, which is based on a preferably dynamic, mathematical model of the circuit arrangement used.
  • a model state is predicted, for example a voltage in the circuit arrangement between a first potential and a second potential.
  • This predicted model state is the predicted model-based stress.
  • the estimator is also set up to adjust or correct this predicted model-based voltage as a function of the parameter determined using the method described, for example using a weighting. The result of this adjustment is the estimated voltage determined by the voltage estimator, which is preferably output by the voltage estimator.
  • a voltage estimator is advantageously provided, which takes into account a parameter determined by means of a time period between zero crossings as a correction variable.
  • An estimated voltage with increased quality is advantageously provided.
  • An extended method for determining the estimated voltage is preferably provided with a state estimator that has a dynamic Contains a model that maps the behavior of the voltage to be estimated and also corrects the voltage calculated by the model, and a logic unit that is set up to execute a described method, the determined parameters being taken into account for the correction step of the state estimator.
  • the invention also relates to a voltage regulator for regulating a voltage between a first potential and a second potential, with a logic unit and a regulator, the logic unit being set up to carry out a described method, the determined parameter being taken into account by the regulator as a feedback variable for the regulation and the current specification in the potentials, the difference between which defines the voltage to be regulated, is output as a controlled variable.
  • Said current specification in the potentials can be converted by a further controller, preferably by means of a subordinate current controller.
  • a voltage regulator is provided for regulating a voltage in the circuit arrangement.
  • the controller takes into account a parameter determined using the methods described as a feedback variable.
  • the current specification is preferably output as a control variable in the potentials whose difference defines the voltage to be controlled.
  • another variable can also be output as a controlled variable, which has an indirect impact on the current in the potentials, the difference between which defines the voltage to be controlled.
  • a voltage regulator is advantageously provided, which takes into account a parameter determined by means of a time period between zero crossings as a feedback variable.
  • a voltage sensor can be dispensed with in this regulation.
  • the invention relates to a device, in particular a DC voltage converter or a charging device, with an inductance, the inductance being arranged in a circuit arrangement, the device being set up to carry out a described method.
  • the parameter determined in this way is used further as a measured variable within the device, for example when checking the plausibility of a determined or calculated, estimated, observed or measured quantity.
  • the parameter determined is transmitted to the outside of the device via an interface, preferably by means of a cable, without contact, by radio or optical waveguide.
  • a device in which the circuit arrangement is integrated and in which the method for determining the parameter is carried out.
  • the determined parameter is either used further within the device for the operation of the device or is transmitted outside for further use outside, preferably in a further device or a control unit.
  • the invention relates to a drive train with a described device and in particular with power electronics and/or an electric drive.
  • a drive train is used, for example, to drive an electric vehicle. Safe operation of the drive train is made possible by means of the method and the device.
  • the invention relates to a vehicle with a described drive train.
  • a vehicle is thus advantageously provided which comprises a device described.
  • FIG. 1 shows a schematic representation of a circuit arrangement
  • FIG. 2 shows a schematic representation of an extended circuit arrangement
  • FIG. 3 shows a schematic current/time diagram with an alternating inductor current
  • FIG. 4 shows a diagrammatically represented voltage regulator or status observer
  • FIG. 5 shows a diagrammatically illustrated device with an inductance, the inductance being located in a circuit arrangement
  • FIG. 6 shows a schematically illustrated vehicle with a drive train
  • FIG. 7 shows a schematically illustrated flowchart for a method for determining a parameter, the parameter characterizing a current or a voltage in a circuit arrangement.
  • FIG. 1 shows a circuit arrangement 200, the circuit arrangement 200 comprising an inductor L through which an alternating inductor current I_L flows.
  • the inductance is preferably a choke or a primary or secondary winding of a transformer, which is preferably used in a DC voltage converter or in a charging device, preferably for galvanic isolation of the input and output.
  • the high-frequency alternating inductor current l_L preferably at a frequency of several 100 kHz, causes a current in the leads of the inductance L.
  • Parameters with which this current is characterized are preferably a mean current value l_avg, negative minimums l_N and/or positive maximums l_P of the inductor current l_L or peak values of the inductor current l_L.
  • the inductor current I_L through the inductance L also causes electrical voltages in the circuit arrangement.
  • a parameter with which an electrical voltage is characterized, preferably when a load or impedance is connected to the inductance L, is preferably a voltage V_c, which is present between the first and the second potential P1, P2.
  • l_avg, l_N, l_P, V_c can be determined depending on the time period TN1 between two zero crossings N_-, N_+ of the inductor current l_L or a time period TN El between a zero crossing N_-, N_+ and a corner point E_-, E_+ des inductor current l_L.
  • the circuit arrangement 200 preferably includes a half-bridge with a first switching element S1 and a second switching element S2.
  • the first switching element S1 is connected on the one hand to a first potential PI and on the other hand to a center tap M of the half-bridge.
  • the second switching element S2 is connected on the one hand to a second potential P2 and on the other hand to the center tap M of the half-bridge.
  • the inductance L is connected to a first connection to the center tap M and to a second connection to a third potential P3.
  • An input voltage VJn is preferably present between the first potential PI and the third potential P3. Alternatively, this input voltage VJn can also be present between the third and the second potential or between the first potential PI and the second potential P2.
  • the alternating inductor current I_L can be generated through the inductance L by suitable activation, preferably high-frequency, of the switching elements S1 and S2.
  • the input voltage VJn is preferably a DC voltage or an AC voltage, the frequency of the input voltage being much lower than the frequency of the inductor current I_L, the frequency preferably being approximately 50 Hz or at least below 1 kHz.
  • An AC voltage is preferably rectified by means of a diode rectifier to form a DC voltage as the input voltage.
  • Figure 2 shows an expanded circuit arrangement 200 of the circuit arrangement 200 shown in Figure 1.
  • the circuit arrangement 200 according to Figure 2 further comprises a first capacitor CI, which is arranged between the first potential PI and the second potential P2 and connected to them respectively.
  • the first capacitor CI is preferably an intermediate circuit capacitor and is preferably designed as an electrolytic capacitor.
  • a parameter that characterizes the voltage V_c at this first capacitor CI can preferably be determined as a function of a period of time TN El and/or TNE2 between a zero crossing N_-, N_+ and a corner point E_-, E_+ of the inductor current l_L (cf. also Figure 3).
  • the circuit arrangement preferably includes a second and/or a third capacitor C2, C3.
  • the second capacitor C2 is connected to the first potential PI on the one hand and to the third potential P3 on the other hand.
  • the third capacitor C3 is connected to the third potential P3 on the one hand and to the second potential P2 on the other hand.
  • These capacitors C2, C3 are used to smooth the current profile of the currents and the voltage profile of the voltages in the circuit arrangement 200, preferably when the switching elements S1 and S2 are alternately closed and opened.
  • FIG. 3 shows a schematic current/time diagram.
  • the alternating choke current I_L through the choke or inductance L is shown in the diagram.
  • the course of the inductor current I_L shown results when the switching elements S1 and S2 are alternately closed and opened.
  • a period of time S2on is drawn in, during which the second switching element S2 is switched on. Consequently, the first switching element S1 is open during this period of time S2on.
  • a period of time Sion is also drawn in, during which the first switching element S1 is closed and consequently the second switching element S2 is open.
  • This sequence of time durations S2on and Sion is repeated. The switching elements switch over between the time durations S2on and Sion or S2on and Sion.
  • the period duration T results from the sum of the durations S2on and Sion.
  • the ratio of the length of time Sion to T is referred to as the duty cycle al.
  • a current average results for the high-frequency inductor current l_L value l_avg, which can be determined by graphical analysis of the regular, high-frequency inductor current l_L in the diagram as a function of a time period TN1 between two zero crossings N_-, N_+ of the inductor current l_L, preferably as a function of the input voltage V Jn , the size of the inductance L, a Duty cycle al and the time duration TN1 between the zero crossings of the inductor current l_L, and the period duration T.
  • the detection of V_c is simpler than the detection of VJn, the formulas described below can also preferably be set up as a function of V_c.
  • the negative or the positive peak value l_N, l_P of the inductor current l_L can be determined by the inductance L:
  • a highly dynamic "sensor" for the mean value of the switched current is thus preferably implemented by the method.
  • the desired inductor current can be adjusted.
  • the determined average current value l_avg of the inductor current l_L is already available after one switching period, which makes it possible to make the controller acting on it very efficient. This allows to stabilize the fast switched current dynamics.
  • conclusions can be drawn about other states for other topologies on the basis of the measured time durations between the zero crossings or between the zero crossing and the corner point, which leads to a reduction in the number of sensors required and entails direct cost savings.
  • FIG. 4 shows a diagrammatically illustrated voltage estimator 280 for determining and outputting an estimated voltage U_est between a first potential PI and a second potential P2.
  • the parameter is determined in a logic unit 290 as a function of the determined time durations TN E1 and TN E2 and an input voltage VJn.
  • the parameter which is preferably a mean voltage value V_c, determined according to the method described as a function of the durations TNEl and TNE2, is taken into account by the estimator 295 of the voltage estimator 280 as a correction variable for the estimate.
  • the estimator 295 is supplied with input variables U, preferably system inputs and/or the detectable system states, with which the model stored in the estimator 295 predicts a model-based voltage.
  • the model-based voltage is then corrected using the mean voltage value V_c calculated from the logic unit 290, whereupon the estimated voltage U_est is available.
  • This estimated voltage can then be fed to a voltage controller which, on the basis of the difference between the voltage setpoint and U_est, manipulates a control variable which has access to the current in the potentials, the difference between which defines the voltage to be controlled.
  • FIG. 5 shows a diagrammatically illustrated device 300 with an inductance L, the inductance being located in a circuit arrangement 200 .
  • the device 300 is designed in particular as a DC voltage converter and/or as a charging device.
  • Device 300 is set up for this, according to the method described, as a function of a period of time TN1 between two zero crossings N_ ⁇ , N_+ of inductor current I_L or a first period of time TN El and a second period of time TNE2 to determine a parameter, preferably a parameter as a mean current value l_avg, a negative peak value l_N or a positive peak value l_P.
  • the determined parameter l_avg, l_N, l_P, V_c is further used as a measured variable within the device 300 or is transmitted outside of the device 300 via an interface.
  • FIG. 6 shows a schematically illustrated vehicle 500, preferably a motor vehicle, ship or aircraft with a drive train 400.
  • the drive train preferably includes a battery 410, an inverter 420, an electric machine 430 and/or a charging socket 310.
  • the battery 410 supplies the inverter 420 with electric power.
  • the inverter 420 preferably converts the electrical energy of the battery 410 into a multi-phase AC voltage for supplying the electrical machine 430.
  • the device 300 is preferably designed as a DC voltage converter or charging device.
  • the DC-DC converter preferably converts the electrical energy of the battery 410 into a low voltage, preferably for supplying an on-board network of a vehicle 500, and/or vice versa.
  • the charger preferably converts electrical energy supplied via the charging socket 310 into high-voltage energy, preferably for charging the electric battery 410 or vice versa.
  • FIG. 7 shows a schematically illustrated flowchart for a method 100 for determining a parameter I_avg, I_N, I_P, V_c, the parameter I_avg, I_N, I_P, V_c characterizing a current or a voltage in a circuit arrangement 200.
  • the method begins with step 105.
  • the first and the second switching element SI, S2 are preferably driven alternately, so that an alternating inductor current I_L through the inductance L results.
  • step 120 at least one period of time TN1 between two zero crossings N_-, N_+ of the inductor current I_L or a period of time TN El between a zero crossing N_-, N_+ and a corner point E_-, E_+ of the inductor current I_L is determined.
  • step 130 a parameter I_avg, I_N, I_P, V_c is determined as a function of the determined time period TN1, TNEl. With step 135 the method is ended.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Dc-Dc Converters (AREA)

Abstract

L'invention concerne un procédé (100) pour la détermination d'un paramètre (l_Avg, l_N, l_P, V_c), ledit paramètre ( l_avg, l_N, l_P, V_c) caractérisant un courant ou une tension dans un agencement de circuit (200). L'agencement de circuit (200) comprend un inducteur (L) à travers lequel s'écoule un courant d'arrêt alternatif (I_L). Le procédé comprend les étapes consistant à : - déterminer (120) au moins une durée (TN1) entre deux passages par zéro (N_-, N_+) du courant d'arrêt (I_L) ou une durée (TNE1) entre un passage par zéro (N_-, N_+) et un sommet (E_-, E_+) du courant d'arrêt (I _L) ; - déterminer (130) le paramètre (l_avg, l_N, l_P, V_c) en fonction de la durée déterminée (TN1, TNE1).
EP21755455.9A 2020-08-20 2021-08-04 Procédé et appareil de détermination d'un courant d'arrêt moyen ou d'une tension d'entrée ou de sortie dans un convertisseur élévateur ou abaisseur Pending EP4200963A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102020210573.1A DE102020210573A1 (de) 2020-08-20 2020-08-20 Verfahren und Vorrichtung zur Ermittlung eines Parameters, wobei der Parameter eine Spannung oder einen Strom in einer Schaltungsanordnung charakterisiert.
PCT/EP2021/071756 WO2022037942A1 (fr) 2020-08-20 2021-08-04 Procédé et appareil de détermination d'un courant d'arrêt moyen ou d'une tension d'entrée ou de sortie dans un convertisseur élévateur ou abaisseur

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EP4200963A1 true EP4200963A1 (fr) 2023-06-28

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EP21755455.9A Pending EP4200963A1 (fr) 2020-08-20 2021-08-04 Procédé et appareil de détermination d'un courant d'arrêt moyen ou d'une tension d'entrée ou de sortie dans un convertisseur élévateur ou abaisseur

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US (1) US20230296653A1 (fr)
EP (1) EP4200963A1 (fr)
CN (1) CN115868106A (fr)
DE (1) DE102020210573A1 (fr)
WO (1) WO2022037942A1 (fr)

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Publication number Priority date Publication date Assignee Title
CH701856B1 (de) 2009-09-17 2014-01-31 Eth Zuerich Verfahren zum Ansteuern einer aktiven Wandlerschaltung und korrespondierende Schaltung.
US9502980B2 (en) * 2011-12-27 2016-11-22 Infineon Technologies Americas Corp. Circuit and method for producing an average output inductor current indicator
JP2013207914A (ja) * 2012-03-28 2013-10-07 Toyota Motor Corp 電圧変換装置の制御装置
JP6361479B2 (ja) * 2014-02-07 2018-07-25 株式会社デンソー 電力変換装置
US10361554B1 (en) * 2016-09-27 2019-07-23 Altera Corporation Techniques for determining inductances

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DE102020210573A1 (de) 2022-02-24
US20230296653A1 (en) 2023-09-21
WO2022037942A1 (fr) 2022-02-24
CN115868106A (zh) 2023-03-28

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