EP3533291B1 - Convertisseur abaisseur pour une diode électroluminescente - Google Patents

Convertisseur abaisseur pour une diode électroluminescente Download PDF

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Publication number
EP3533291B1
EP3533291B1 EP17780748.4A EP17780748A EP3533291B1 EP 3533291 B1 EP3533291 B1 EP 3533291B1 EP 17780748 A EP17780748 A EP 17780748A EP 3533291 B1 EP3533291 B1 EP 3533291B1
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EP
European Patent Office
Prior art keywords
switch
down converter
conductive state
choke
current
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EP17780748.4A
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German (de)
English (en)
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EP3533291A1 (fr
Inventor
Lukas Saccavini
Frank Lochmann
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Tridonic GmbH and Co KG
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Tridonic GmbH and Co KG
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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/375—Switched mode power supply [SMPS] using buck topology
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/10—Controlling the intensity of the light

Definitions

  • Various examples of the invention generally relate to a step-down converter for a light-emitting diode with a first switch and a second switch which are operated alternately and periodically in the conductive state by a controller.
  • Various examples of the invention relate in particular to a step-down converter in which the controller operates the first switch and the second switch as a function of a dimming signal.
  • lights typically have an operating device.
  • the operating device typically contains a buck converter, which is set up to reduce the amplitude of a DC supply voltage for operating the light-emitting diode.
  • the down converter can be set up to change the operation of the light-emitting diode as a function of a dimming signal, which indicates the desired brightness of the lamp.
  • step-down converters typically have a switch which is connected in series with a storage choke between a supply voltage connection and an output connection.
  • a choke current flows through the storage choke, which is fed by the supply voltage, and energy is stored in the storage choke.
  • a choke current flows which is fed by the energy previously stored in the storage choke.
  • a buck converter according to the preamble of claim 1 is from the document US 2015/0373805 A1 known.
  • discontinuous mode operating mode
  • continuous mode the inductor current does not drop to zero during the switch-off time.
  • borderline mode which corresponds to the transition between intermittent operation and continuous operation.
  • step-down converters it may be necessary to activate intermittent operation as a function of the dimming signal.
  • intermittent operation in particular, in connection with a low desired brightness of the luminaire, it may be necessary to activate the intermittent operation with a particularly long switch-off time. Then the brightness of the lamp is modulated with a comparatively low frequency.
  • the light-emitting diode is typically switched off in the meantime, i.e. the load current can drop to zero.
  • this type of operation of the luminaire is also referred to as pulse width modulation. This can have various negative effects on the surroundings of the luminaire: for example, interference with optical devices can occur.
  • step-down converters it may also be necessary to switch between intermittent operation and limit operation depending on the dimming signal.
  • this can mean that, depending on the dimming signal, there is a particularly strong jump in the frequency with which the switch is switched. This can require complex and expensive control technology.
  • a step-down converter for a light-emitting diode comprises a first switch and a second switch.
  • the second switch is connected in series with the first switch between a supply voltage connection and ground.
  • the buck converter also includes a Storage choke.
  • the storage choke is connected in series with the first switch between the supply voltage connection and an output connection.
  • the output connection is set up to output a load current to the light-emitting diode based on a choke current through the storage choke.
  • the buck converter also includes a controller. The controller is set up to operate the first switch and the second switch alternately and periodically in the conductive state as a function of a dimming signal.
  • a step-down converter with a first switch and a second switch according to the above example is also referred to as a synchronous converter.
  • the first switch is also referred to as a high-side switch because it is arranged at potential.
  • the second switch is sometimes also referred to as a low-side switch because it is arranged between potential and ground.
  • the first switch and / or the second switch can be implemented by a semiconductor switch element.
  • semiconductor switch elements include: a transistor; a bipolar transistor; a field effect transistor; a metal oxide field effect transistor; an insulated gate field effect transistor.
  • one side of the storage choke can be connected to a point which is arranged between the first switch and the second switch.
  • the second side of the storage choke can be connected to the output connection.
  • the storage choke can be implemented as a coil with several windings.
  • the storage choke can provide an inductance. Based on the law of induction, the voltage across the storage choke (choke voltage) can thus be equal to the inductance of the storage choke multiplied by the change in the choke current over time. In other words, the storage choke can counteract particularly rapid changes in the choke current
  • the output connection can, for example, comprise a smoothing capacitor which has the effect that the load current which is output to the light-emitting diode corresponds to a time average value of the inductor current.
  • the output connection could, for example, also have a plug contact, solder contact, clamping contact, etc. in order to establish an electrical connection to the light-emitting diode.
  • the control can be implemented, for example, as an application-specific integrated circuit (ASIC) or as a microcontroller.
  • ASIC application-specific integrated circuit
  • the controller could also be implemented as an FPGA or processor.
  • the control could also be implemented at least partially by an analog circuit.
  • the controller could receive the dimming signal via a communication interface, for example.
  • the brightness of the light-emitting diode can be controlled flexibly as a function of the dimming signal. In particular, it can be unnecessary to activate the intermittent operation when the brightness of the light-emitting diode is low. For example, it would be possible for continuous operation to be activated throughout - i.e. for all brightness levels of the dimming signal.
  • the controller it is possible for the controller to be set up to operate the second switch in the conductive state for an on time.
  • the on-time of the second switch is dimensioned in such a way that the polarity of the inductor current changes from positive to negative and the voltage at the midpoint of the two switches (midpoint voltage) swings around, i.e. for example from positive to negative polarity or in relation to another reference voltage, such as for example a bus voltage.
  • This can mean that the second switch is operated in the conductive state until the direction of the inductor current is reversed.
  • the inductor current could be fed with negative polarity by discharging a capacitor of the output connection.
  • the inductor current has a negative polarity at least temporarily, a particularly small time average value of the inductor current can be achieved.
  • a load current of small dimensions can in turn be output to the light-emitting diode.
  • low brightnesses can also be achieved for corresponding dimming signals for the light-emitting diode.
  • low brightness levels can be achieved without interrupting the operation of the light-emitting diode in accordance with the pulse-width modulation method.
  • a discontinuous mode can be avoided. Interfering influences on the environment - e.g. a flickering of the light-emitting diode - can be reduced or avoided.
  • the controller can be configured to implement a dead time during which the first switch and the second switch are operated in the non-conductive state. For example, a certain safety area can be provided by the dead time so that short circuits are avoided.
  • the first switch can first be switched to the non-conductive state before the second switch is switched to the conductive state ("break before make").
  • a corresponding dead time can be designed to be particularly short and, for example, be in the range from 100 ns to 1000 ns.
  • the dead time it can be desirable for the dead time to be lengthened or dimensioned to be comparatively long.
  • the dead time could not be less than 5% of the on time of the second switch, optionally not less than 10% of the on time of the second switch, further optionally not less than 25% of the on time of the second switch.
  • the controller it can be set up to switch the first switch in a time-synchronized manner with the reversal of the midpoint voltage from the non-conductive state to the conductive state (zero voltage switching, ZVS).
  • the first switch can optionally be switched without current (zero current switching).
  • Such a current-free switching of the first switch has the advantage of low power dissipation. As a result, the energy consumption of the buck converter can be reduced.
  • the controller could implement a control loop. It can thereby be achieved that the brightness of the light-emitting diode can be set particularly precisely and stably by generating the load current.
  • the controller could be set up to operate the first switch and the second switch in a regulated manner.
  • the corresponding control loop can take the time mean value of the inductor current into account as a controlled variable. Alternatively or additionally, it would also be possible to take the load current into account as a controlled variable.
  • the corresponding control loop could also take into account a reference variable that is determined based on the dimming signal. For example, it would be possible to use a look-up table to determine the reference variable based on the dimming signal in such a way that it can be compared directly with the load current as a controlled variable. In this way it can be possible to set the desired brightness in accordance with the dimming signal particularly precisely.
  • the controller could be set up to operate the first switch and the second switch in a regulated manner.
  • the corresponding control loop can have at least one Consider the peak value of the choke current as a manipulated variable.
  • the peak value of the inductor current with positive polarity could be taken into account as a manipulated variable.
  • the controller may be set up to operate the first switch and the second switch in a regulated manner, the peak value of the inductor current being taken into account as a manipulated variable in the case of positive polarity, but the peak value of the inductor current being kept constant in the case of negative polarity .
  • the voltage-free switching of the first switch can be implemented in a particularly simple manner.
  • a period of time between the switching of the second switch from the conductive state to the non-conductive state and the switching of the first switch from the non-conductive to the conductive state can also be kept constant at a fixed peak value of the inductor current with negative polarity.
  • the down converter can have a sensor circuit, for example.
  • the sensor circuit By means of the sensor circuit it can be possible to obtain a measurement signal which is indicative of the controlled variable.
  • the measurement signal could be indicative of the inductor current.
  • the measurement signal could be indicative of the time average value of the inductor current:
  • a low-pass filter could be provided in the sensor circuit, for example.
  • the measurement signal is indicative of the inductor current with a large bandwidth, which corresponds to the change in the inductor current due to the law of induction based on the inductance of the storage inductor.
  • the measurement signal it would also be possible for the measurement signal to be indicative of a choke voltage across the storage choke.
  • the sensor circuit can be set up, for example, to bring about a zero point offset between the measurement signal and the inductor current. It can thereby be achieved that the measurement signal has only positive or only negative polarity. A zero crossing of the measurement signal can - despite the zero crossing of the inductor current - be avoided.
  • a zero point offset can be implemented, for example, by providing a further current source that provides a reference current. Such a zero point offset could also be achieved, for example, by means of a suitable voltage divider. Since the measurement signal has only positive polarity or only negative polarity, a particularly simple regulation based on the measurement signal can be implemented.
  • an operating device for a luminaire comprises the down converter according to the various examples described herein.
  • Yet another example relates to the luminaire with the operating device which has the down converter.
  • the operating device could also have an AC / DC converter.
  • the AC / DC converter can be set up to convert an AC supply voltage into the DC supply voltage, which is then fed to the step-down converter.
  • a method in another example, includes receiving a dimming signal for a light emitting diode. The method further comprises, as a function of the dimming signal, the alternating and periodic operation of a first switch of a step-down converter and a second switch of the step-down converter in the conductive state. The second switch is connected in series with the first switch between a supply voltage connection of the step-down converter and ground. The method also includes outputting a load current to the light emitting diode via an output terminal of the buck converter. This takes place based on a choke current of a storage choke of the step-down converter. The storage choke is connected in series with the first switch between the supply voltage connection and the output connection.
  • effects can be achieved which are comparable to the effects which can be achieved for a buck converter according to various examples described herein.
  • the techniques described herein are particularly concerned with stepping down the DC supply voltage, i.e., down-converting.
  • the techniques described herein can be used in particular in connection with the operation of light-emitting diodes. In other examples, however, it would also be possible for the techniques described herein to be used in other areas of application. Examples concern, for example, charge storage devices, power supply units for electronic devices, or other forms of light sources, etc.
  • the supply voltage is converted depending on a dimming signal for the light-emitting diode.
  • the dimming signal can be indicative of a desired brightness of the light-emitting diode.
  • the conversion can output a certain load current to the light-emitting diode, wherein the load current can be greater (lower) for greater (lower) desired brightnesses.
  • This architecture of the buck converter uses a first switch which is arranged at potential and a second switch which is arranged between potential and ground.
  • a first switch which is arranged at potential
  • a second switch which is arranged between potential and ground.
  • particularly energy-efficient operation can be achieved in this way: in particular, the voltage drop across the diode can be avoided by using the second switch.
  • the techniques described here make it possible to implement different brightnesses for the light-emitting diode without using pulse width modulation. This can prevent the light-emitting diode from flickering at low levels of brightness.
  • the techniques described herein can enable simple regulation in which there is no need to switch between continuous operation or limit operation of the step-down converter and intermittent operation of the step-down converter.
  • FIG. 1 illustrates aspects relating to an operating device 100 for a light-emitting diode 110.
  • the operating device 100 could be part of a lamp.
  • the luminaire could furthermore comprise a housing, heat sink, an emergency battery, etc.
  • the operating device 100 comprises an AC / DC converter 104, which is set up to convert an AC supply voltage 151 into a DC supply voltage 153.
  • the AC supply voltage 151 is received via a network connection 152.
  • the AC supply voltage 151 could have an amplitude in the range from 100V to 300V.
  • the AC / DC converter 104 could have a rectifier bridge circuit (in FIG. 1 not shown).
  • the AC / DC converter 104 is optional: in other examples, the operating device 100 could receive a DC supply voltage directly.
  • the operating device 100 also includes a DC / DC converter 101.
  • the DC / DC converter 101 is set up to convert the DC supply voltage 153.
  • the DC / DC converter 101 is set up to convert the DC supply voltage downwards. Therefore, the DC / DC converter 101 will hereinafter be referred to as the buck converter 101.
  • the light-emitting diode 110 is operated based on the DC supply voltage. For this purpose, a load current can be provided by the step-down converter 101 and output to the light-emitting diode 110.
  • the down converter 101 is activated by a controller 102.
  • the controller 102 could, for example, implement a regulated operation of the step-down converter 101.
  • the operation of the light-emitting diode 110 can be stabilized.
  • the operation of the light-emitting diode 110 can be controlled by external specifications.
  • the controller 102 receives a dimming signal 161 via a communication interface 103.
  • the dimming signal 161 is received via a dedicated transmission medium 162, for example a DALI interface.
  • the dimming signal 161 it would also be possible for the dimming signal 161 to be received via the network connection 152 (in FIG. 1 not shown).
  • the dimming signal 161 could be modulated onto the AC supply voltage 151.
  • An example would be a phase cut modulation.
  • the controller 102 can control the operation of the light-emitting diode 110 as a function of the dimming signal 161 as an external specification or control variable. For example, the controller 102 control the down converter 101 in such a way that the load current assumes different values depending on the dimming signal 161.
  • the dimming signal can, for example, also be specified by a resistor connected to the operating device 100, the resistance value preferably specifying the nominal current of the light-emitting diode.
  • a potentiometer could also be connected as a variable resistor, which would also enable the nominal current to be changed or set.
  • FIG. 2A and 2B illustrate aspects relating to buck converter 101.
  • the buck converter 101 in greater detail.
  • FIG. 2A FIG. 10 is a circuit diagram of the buck converter 101.
  • the down converter 101 is set up to receive the DC supply voltage 153 via a supply voltage connection 211.
  • a field effect transistor 201 with a freewheeling diode 205 implements a switch 291.
  • a field effect transistor 202 with a freewheeling diode 206 implements a switch 292.
  • the switch 291 and the switch 292 are connected in series between the supply voltage terminal 211 and ground 215.
  • the down converter 101 also includes a storage inductor 212.
  • the storage inductor 212 and the switch 291 are connected in series between the supply voltage connection 211 and an output connection 219 to the light-emitting diode 110.
  • a choke current 701 through the storage choke 212 is also illustrated.
  • An orientation of the choke current 701 in the direction of the output connection 219 is hereinafter referred to as the positive polarity of the inductor current 701.
  • the output connection 219 has a smoothing capacitor 213 with a resistor 214. Therefore, the load current 702, which is provided based on the inductor current 701 of the light-emitting diode 110, corresponds to a time average value of the inductor current 701.
  • a control signal 601 is applied to a control contact of the field effect transistor 201 of the switch 291.
  • the control signal 601 it is possible to operate the switch 291 either in the conductive state or in the non-conductive state. It is also possible to switch the switch 291 from the conductive state to the non-conductive state and to switch it from the non-conductive state to the conductive state.
  • the control signal 601 can be generated by the controller 102. As a result, the controller 102 can operate the switch 291 either in the conductive state or in the non-conductive state.
  • a control signal 602 is applied to a control contact of the field effect transistor 202 and thus switch 292.
  • the control signal 602 it is possible to operate the switch 292 either in the conductive state or in the non-conductive state. It is also possible to switch the switch 292 from the conductive state to the non-conductive state and to switch it from the non-conductive state to the conductive state.
  • the control signal 602 can be generated by the controller 102. As a result, the controller 102 can operate the switch 292 either in the conductive state or in the non-conductive state.
  • the controller 102 is set up to operate the switch 291 and the switch 292 alternately and periodically in the conductive state as a function of the dimming signal 161.
  • Figure 2B shows an alternative implementation of a buck converter.
  • the light-emitting diode 110 with the parallel capacitor 213 is not connected to the ground point 215, but to the supply voltage connection 211.
  • the storage choke 212 is magnetized during the on-time of the switch 292.
  • the time phase of the positive rise in the inductor current 701 is the on time of the switch 292.
  • the freewheeling phase, i.e. the phase of demagnetization of the storage inductor 212, takes place via the switch 291.
  • the time phase of the negative increase in the inductor current 701 is the on time of the switch 291
  • FIG. 3 illustrates aspects relating to operating the switches 291, 292 alternately and periodically in the conductive state.
  • FIG. 3 schematically illustrates the timing of control signal 601 and control signal 602.
  • FIG. 3 further schematically illustrates the resulting time profile of the inductor current 701.
  • FIG. 3 it can be seen that the switch 291 is operated in the conductive state during repeated on times 651.
  • the switch 291 is operated in the non-conductive state during repeated off times 652.
  • the switch 292 is accordingly operated in the conductive state during repeated on times 661.
  • the switch 292 is operated in the non-conductive state during repeated off times 662.
  • the period 670 is shown.
  • FIG. 3 it can also be seen that the switch 292 is always in the conductive state when the switch 291 is in the non-conductive state.
  • the switch 291 is always in the conductive state when the switch 292 is in the non-conductive state. Accordingly, the switches 291, 292 are alternately operated in the conductive state.
  • the on-time 661 of the switch 292 is dimensioned such that the polarity of the inductor current 701 changes from positive to negative at time 755.
  • the inductor current 701 With an at least temporarily negative polarity, it can be achieved that the time average value 712 (horizontal dashed line in FIG. 3 ) of the inductor current 701 - and thus the load current 702 - assumes particularly low values close to zero. As a result, low brightnesses of the light-emitting diode 110 can be achieved.
  • FIG. 4th illustrates aspects relating to operating the switches 291, 292 alternately and periodically in the conductive state.
  • the example of FIG. 4th basically corresponds to the example of FIG. 3 .
  • the FIG. 4th a comparatively long dead time 670 is provided.
  • the dead time 670 is approximately 25% of the on time 661 and approximately 20% of the off time 652.
  • both the switch 291 and the switch 292 are operated in the non-conductive state. Therefore, the switch 292 is switched from the conductive state to the non-conductive state at a different value of the inductor current 701 than the switch 291, which is switched from the non-conductive state to the conductive state.
  • the switch 291 is time-synchronized with the reversal of the midpoint voltage of both switches 291 and 292 from the non-conductive state switched to the conductive state.
  • the switch 291 can be switched from the non-conductive state to the conductive state in a time-synchronized manner with a zero crossing 753 of the inductor current 701.
  • a dead time in FIG. 4th not shown. This dead time between switching off the switch 291 and switching on the switch 292 can be dimensioned in order to avoid a short circuit through both switches 291 and 292.
  • switches 291, 292 - for example, according to the implementations of FIG. 3 and 4th - can be regulated in some examples.
  • the time mean value 712 of the inductor current 701 could be taken into account as a controlled variable, since this can be directly proportional to the load current 702.
  • the dimming signal 161 or a variable derived therefrom could be taken into account as a reference variable. A deviation between the reference variable and the controlled variable can then be minimized by suitable operation 291, 292.
  • manipulated variables could be taken into account in a corresponding regulation.
  • the duty cycle for the operation of the switch 291 in the conductive state and / or for the operation of the switch 292 in the conductive state could be taken into account as a manipulated variable.
  • the peak value 751 of the inductor current 701 in the case of positive polarity and / or the peak value 752 of the inductor current 701 in the case of negative polarity could be taken into account as a manipulated variable.
  • FIGs. 5A and 5B illustrate aspects relating to buck converter 101.
  • the examples of FIGs. 5A and 5B basically correspond to the example of FIG. 2A .
  • a sensor circuit 301 and a sensor circuit 311 are also shown.
  • the sensor circuit 301 is set up to output a measurement signal at the connection 302, which is indicative of a current value of the inductor current 701.
  • the inductor current 701 is detected by means of the resistor 214.
  • the sensor circuit 301 is also set up to output a measurement signal at the connection 303 which is indicative of the time average value 712 of the inductor current 701: a low-pass filter is provided for this purpose.
  • the sensor circuit 301 it would be possible for the sensor circuit 301 to be set up to provide a zero point offset between the measurement signal at connection 302 and the choke current 701). It can thereby be achieved that the measurement signal does not have alternating polarities - corresponding to the inductor current 701: this can simplify the determination of the peak values 751, 752 and / or an implementation of the control loop.
  • the zero point offset can be implemented, for example, by means of a power source that can preferably be integrated into the controller. This example is in the Figure 5A shown.
  • the zero point offset can be implemented by means of a pull-up resistor (sometimes also referred to as a pull-up resistor), which is preferably connected to a supply voltage such as the supply voltage Vcc of the operating device.
  • a pull-up resistor sometimes also referred to as a pull-up resistor
  • the sensor circuit 311 comprises a coil which is inductively coupled to the storage choke 212.
  • the sensor circuit 311 is set up to output a measurement signal at the connection 312, which is indicative of the throttle voltage and thus also of the voltage at the midpoint of the two switches 291 and 292.
  • the midpoint voltage of the two switches 291 and 292 can also be measured using a voltage divider which taps off the voltage at the midpoint of the two switches 291 and 292.
  • the voltage at the midpoint of the two switches 291 and 292 swings to the voltage of the supply voltage connection 211.
  • the midpoint voltage of the two switches 291 and 292 can swing around against the voltage at the ground point 215.
  • FIG. 6th Figure 3 is a flow diagram of a method according to various examples.
  • a dimming signal is received.
  • the dimming signal can be indicative of a desired brightness of a light-emitting diode of a lamp.
  • the dimming signal can be received in analog form or digital form, for example.
  • the dimming signal could be received by phase-cutting modulation of an AC supply voltage.
  • a first switch and a second switch of a step-down converter are then operated alternately and periodically in the conductive state. It would optionally be possible to provide dead times during which both the first switch and the second switch are operated in the non-conductive state. For example, it would be possible that current-free switching of the first switch and / or current-free switching of the second switch is achieved on the basis of a corresponding dimensioning of the dead times.
  • a choke current through a storage choke of the step-down converter can be modified.
  • the storage choke can be alternately charged and discharged by switching the switch.
  • a load current is then output to the light-emitting diode in block 1003.
  • the load current can correspond, for example, to an average value of the inductor current.
  • the load current is fed alternately by the supply voltage and the storage choke.
  • FIG. 7th Figure 3 is a flow diagram of a method according to various examples.
  • FIG. 7th illustrates details relating to the regulated operation of the first switch and the second switch. For example, the procedure according to FIG. 7th executed as part of block 1002.
  • a reference variable is determined based on the dimming signal.
  • a time average value of the inductor current is determined as a controlled variable.
  • the load current could also be taken into account as a controlled variable.
  • the aim of the control can be to minimize deviations between the controlled variable and the reference variable.
  • One or more manipulated variables can be changed for this purpose.
  • the peak value of the inductor current could be changed as a manipulated variable with positive polarity.
  • the peak value of the inductor current could also be changed as a manipulated variable in the case of negative polarity. This is done in block 1013.

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Claims (8)

  1. Convertisseur abaisseur (101) pour une diode électroluminescente (110), qui comprend :
    - une borne de tension d'alimentation (211),
    - une borne de sortie (219), qui peut être raccordée à la diode électroluminescente (110),
    - un premier commutateur (201, 205, 291),
    - un second commutateur (202, 206, 292), qui est connecté en série entre la borne de tension d'alimentation (211) et la masse (215) avec le premier commutateur (201, 205, 291),
    - une bobine d'accumulation (212), dans lequel la bobine d'accumulation (212) et le premier commutateur (201, 205, 291) sont connectés en série entre la borne de tension d'alimentation (211) et la borne de sortie (219), dans lequel la borne de sortie (219) est conçue pour, sur la base d'un courant de bobine (701) circulant dans la bobine d'accumulation (212), émettre un courant de charge (702) vers la diode électroluminescente (110) et
    - une commande (102), qui est conçue pour faire fonctionner le premier commutateur (201, 205, 291) et le second commutateur (202, 206, 292) à l'état conducteur de manière alternée et périodique en fonction d'un signal d'atténuation (161),
    dans lequel la commande (102) est en outre conçue pour faire fonctionner le second commutateur (202, 206, 292) dans l'état conducteur pendant un temps de fonctionnement (661),
    caractérisé en ce que le temps de fonctionnement (661) du second commutateur (202, 206, 292) est dimensionné de sorte que la polarité du courant de bobine (701) passe de positive à négative pendant le temps de fonctionnement (661) du second commutateur (202, 206, 292) et une tension au point médian de la connexion en série du premier commutateur (201, 205, 291) et du second commutateur (202, 206, 292) s'inverse.
  2. Convertisseur abaisseur (101) selon la revendication 1,
    dans lequel la commande (102) est conçue pour mettre en œuvre un temps mort, pendant lequel le premier commutateur et le second commutateur sont amenés à fonctionner dans l'état non conducteur.
  3. Convertisseur abaisseur (101) selon l'une quelconque des revendications précédentes,
    dans lequel la commande (102) est conçue pour passer le premier commutateur (201, 205, 291) de manière temporellement synchronisée avec l'inversion d'une tension de point médian entre le premier commutateur (201, 205, 291) et le second commutateur (202, 206, 292) de l'état non conducteur à l'état conducteur.
  4. Convertisseur abaisseur (101) selon l'une quelconque des revendications précédentes,
    dans lequel la commande (102) est conçue pour faire fonctionner le premier commutateur (201, 205, 291) et le second commutateur (202, 206, 292) de manière régulée avec la valeur moyenne temporelle du courant de bobine (701) en guise de grandeur de régulation et avec une grandeur de guidage déterminée sur la base du signal d'atténuation (161).
  5. Convertisseur abaisseur (101) selon l'une quelconque des revendications 1 à 3,
    dans lequel la commande (102) est conçue pour faire fonctionner le premier commutateur (201, 205, 291) et le second commutateur (202, 206, 292) de manière régulée avec au moins une valeur de crête du courant de bobine (701) en guise de grandeur de réglage.
  6. Convertisseur abaisseur (101) selon la revendication 5,
    dans lequel la commande (102) est conçue pour faire fonctionner le premier commutateur (201, 205, 291) et le second commutateur (202, 206, 292) de manière régulée avec la valeur de crête du courant de bobine (701) lors d'une polarité positive en guise de grandeur de réglage et avec une grandeur de crête constante du courant de bobine (701) lors d'une polarité négative.
  7. Convertisseur abaisseur (101) selon l'une quelconque des revendications précédentes, qui comprend en outre :
    - un circuit de capteur (301), qui est conçu pour émettre un signal de mesure, qui indique le courant de bobine (701), dans lequel le circuit de capteur est conçu pour entraîner un décalage du point zéro entre le signal de mesure et le courant de bobine (701).
  8. Procédé d'émission d'un courant de charge par l'intermédiaire d'une borne de sortie (219) d'un convertisseur abaisseur (101) vers une diode électroluminescente (110), le procédé comprenant :
    - la réception d'un signal d'atténuation (161) pour la diode électroluminescente (110)
    - en fonction du signal d'atténuation (161) : le fonctionnement alterné et périodique d'un premier commutateur (201, 205, 291) du convertisseur abaisseur (101) et d'un second commutateur (202, 206, 292) du convertisseur abaisseur (101), dans lequel le second commutateur (202, 206, 292) est connecté en série entre une borne de tension d'alimentation (211) du convertisseur abaisseur (101) et la masse (215) avec le premier commutateur (201, 205, 291), dans lequel le fonctionnement du second commutateur (202, 206, 292) est effectué dans l'état conducteur pendant une période de fonctionnement (661) et
    - sur la base d'un courant de bobine (701) d'une bobine d'accumulation (212) : l'émission du courant de charge (702) vers la diode électroluminescente (110) par l'intermédiaire de la borne de sortie (219), dans lequel la bobine d'accumulation (212) et le premier commutateur (201, 205, 291) sont connectés en série entre la borne de tension d'alimentation (211) et la borne de sortie (219),
    caractérisé par le dimensionnement du temps de fonctionnement (661) du second commutateur (202, 206, 292) de sorte que la polarité du courant de bobine (701) passe de positive à négative pendant le temps de fonctionnement (661) du second commutateur (202, 206, 292) et la tension au point médian de la connexion en série du premier commutateur (201, 205, 291) et du second commutateur (202, 206, 292) s'inverse.
EP17780748.4A 2016-10-31 2017-10-09 Convertisseur abaisseur pour une diode électroluminescente Active EP3533291B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102016221398.9A DE102016221398A1 (de) 2016-10-31 2016-10-31 Abwärtswandler für eine leuchtdiode
PCT/EP2017/075619 WO2018077599A1 (fr) 2016-10-31 2017-10-09 Convertisseur abaisseur pour une diode électroluminescente

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EP3533291A1 EP3533291A1 (fr) 2019-09-04
EP3533291B1 true EP3533291B1 (fr) 2021-04-07

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AT (1) AT17349U1 (fr)
DE (1) DE102016221398A1 (fr)
WO (1) WO2018077599A1 (fr)

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DE102018115174B4 (de) * 2018-06-25 2024-01-11 Tridonic Gmbh & Co Kg LED-Konverter als Audioverstärker

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US7944153B2 (en) * 2006-12-15 2011-05-17 Intersil Americas Inc. Constant current light emitting diode (LED) driver circuit and method
US8723446B2 (en) * 2008-05-13 2014-05-13 Nxp B.V. Method and circuit arrangement for cycle-by-cycle control of a LED current flowing through a LED circuit arrangement, and associated circuit composition and lighting system
US8026704B2 (en) * 2008-06-06 2011-09-27 Infineon Technologies Austria Ag System and method for controlling a converter
US9185755B2 (en) * 2011-08-19 2015-11-10 Marvell World Trade Ltd. Regulator for LED lighting color mixing
JP5986921B2 (ja) * 2012-12-27 2016-09-06 日立アプライアンス株式会社 点灯装置
CN104066246B (zh) * 2014-06-24 2017-01-04 成都芯源系统有限公司 发光元件驱动方法和发光元件驱动器及其控制器

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EP3533291A1 (fr) 2019-09-04
AT17349U1 (de) 2022-01-15
WO2018077599A1 (fr) 2018-05-03
DE102016221398A1 (de) 2018-05-03

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