EP2690703B1 - Frequenzanpassbarer Bandpassfilter für Hyperfrequenzwelle - Google Patents

Frequenzanpassbarer Bandpassfilter für Hyperfrequenzwelle Download PDF

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Publication number
EP2690703B1
EP2690703B1 EP13177704.7A EP13177704A EP2690703B1 EP 2690703 B1 EP2690703 B1 EP 2690703B1 EP 13177704 A EP13177704 A EP 13177704A EP 2690703 B1 EP2690703 B1 EP 2690703B1
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Prior art keywords
dielectric
input
output
cavity
filter
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English (en)
French (fr)
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EP2690703A1 (de
Inventor
Aurélien Perigaud
Damien Pacaud
Nicolas Delhote
Olivier Tantot
Stéphane BILA
Serge Verdeyme
Laetitia Estagerie
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Thales SA
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Thales SA
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/207—Hollow waveguide filters
    • H01P1/208—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure
    • H01P1/2084—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure with dielectric resonators
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/207—Hollow waveguide filters
    • H01P1/208—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure
    • H01P1/2084—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure with dielectric resonators
    • H01P1/2086—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure with dielectric resonators multimode
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P7/00—Resonators of the waveguide type
    • H01P7/10—Dielectric resonators

Definitions

  • the present invention relates to the field of frequency filters in the field of microwave waves, typically frequencies between 1GHz to 30GHz. More particularly, the present invention relates to frequency tunable band pass filters.
  • microwave wave for example received by a satellite
  • the processing of a microwave wave requires the development of specific components, allowing the propagation, amplification, and filtering of this wave.
  • a microwave received by a satellite must be amplified before being sent back to the ground.
  • This amplification is only possible by separating all the frequencies received into channels, each corresponding to a given frequency band. The amplification is then carried out channel by channel. Channel separation requires the development of bandpass filters.
  • tunable bandpass filters in the microwave domain is the use of passive semiconductor components, such as PIN diodes, continuously variable capacitors, or capacitive switches.
  • passive semiconductor components such as PIN diodes, continuously variable capacitors, or capacitive switches.
  • MEMS micro electromechanical systems
  • the technology of the filters based on dielectric elements is known. It allows non-tunable band pass filters.
  • the figure 1 describes an example of a filter based on dielectric elements for non-tunable microwave wave.
  • An input excitation means 10 introduces the wave into the cavity, this element is typically a conducting medium such as a coaxial cable (or probe).
  • the cavity 13 is a closed cavity made of metal, typically aluminum or invar.
  • An output excitation means 11 typically a conducting medium such as a coaxial cable (or probe), makes it possible to cause the wave to exit the cavity.
  • the dielectric element 12 is round or square in shape and disposed inside the metal cavity 13.
  • the dielectric material is typically zirconia, alumina or BMT.
  • a filter typically comprises at least one resonator comprising a metal cavity and a dielectric element.
  • a resonance mode of the filter corresponds to a particular distribution of the electromagnetic field which is excited at a particular frequency.
  • a bandpass filter allows the propagation of a wave over a certain frequency range and attenuates this wave for the other frequencies. This defines a bandwidth and a central frequency of the filter. For frequencies around its center frequency, a bandpass filter has high transmission and low reflection.
  • these filters may be composed of a plurality of resonators coupled together.
  • the center frequency and the filter bandwidth depend on both the geometry of the cavities and the dielectric elements, as well as the coupling resonators between them as well as couplings to the input and output excitation means of the filter.
  • Coupling means are for example openings or slots called iris, electrical or magnetic probes or microwave lines.
  • the bandwidth of the filter is characterized in different ways depending on the nature of the filter.
  • Parameter S is a parameter that accounts for filter performance in terms of reflection and transmission.
  • S11, or S22 corresponds to a measurement of the reflection and S12, or S21, to a measurement of the transmission.
  • a filter performs a filtering function.
  • This function can generally be approximated via mathematical models (iterative functions such as Chebychev, Bessel, etc. functions). These functions are usually based on polynomial relationships.
  • the filter bandwidth is determined at S11 (or S22) equi-ripple, for example at 15 dB or 20 dB of reflection reduction with respect to its level. out of band.
  • the band is taken at -3dB (when S21 crosses S11).
  • FIG. 2 An example of a characteristic of the parameters S11 and S12 of a filter is illustrated figure 2 .
  • the curve 21 corresponds to the reflection S11 of the wave on the filter as a function of its frequency.
  • the bandwidth equi-ripple at 20 dB of reflection is noted 26.
  • the filter has a center frequency corresponding to the frequency of the middle of the bandwidth.
  • Curve 22 of the figure 2 corresponds to the transmission S12 of the filter as a function of the frequency.
  • the filter thus passes a signal whose frequency is located in the bandwidth, but the signal is nevertheless attenuated by the losses of the filter.
  • the tuning of the filter making it possible to obtain a transmission maximum for a given frequency band is very difficult to produce and depends on all the parameters of the filter. It is moreover dependent on the temperature.
  • the resonance frequencies of the filter resonators can be very slightly modified using metal screws, but this process carried out empirically, is very expensive in time and allows a very low frequency tunability, typically of the order of a few%.
  • the objective is not the tunability but the obtaining of a precise value of the central frequency, and it is desired to obtain a reduced sensitivity of the frequency of each resonator with respect to the depth of the screw.
  • the circular or square symmetry of the resonators simplifies the design of the filter and the selection of the mode (TE for Transverse Electric or TM for Transverse Magnetic) that propagates in the filter.
  • the document US 7705694 discloses a bandwidth-tunable filter composed of a plurality of dielectric resonators coupled together, non-uniformly radially and uniformly shaped along an axis z perpendicular to the direction of propagation. Each resonator is able to rotate about the z-axis between two positions, which induces a change in the value of the width of the bandwidth, typically from 51Mz to 68Mz.
  • This device allows tunability on the value of the width of the bandwidth of the filter, but not on its central frequency.
  • the document EP1684374 and the document JPS61136302 describe dielectric resonators that change their resonant frequency by dielectric rotation or by an external screw.
  • the object of the present invention is to provide tunable filters in central frequency that do not have the aforementioned drawbacks.
  • the input dielectric element and the output dielectric element are respectively located substantially in the center of the input cavity and the output cavity.
  • the input and output dielectric elements are U-shaped.
  • the filter comprises coupling means adapted to couple the input and output resonators directly.
  • the filter further comprises at least one intermediate resonator arranged in series between the input resonator and the output resonator, comprising an intermediate metal cavity and an intermediate dielectric element disposed inside the cavity and capable of disturbing the resonance mode of the microwave wave in the cavity, each dielectric element having a flattened shape having a height of at least a factor of 3 to the smallest dimension in a plane perpendicular to the direction carrying the height and being able to rotate about an axis of intermediate rotation, the filter comprising coupling means adapted to couple the intermediate resonators in pairs in series.
  • the coupling means are slots.
  • the dielectric elements have an identical angular position corresponding to an identical rotation, a value of the angle of rotation corresponding to a central frequency value of the filter.
  • the axes of rotation are parallel to each other.
  • the axes of rotation are perpendicular to the Z axis.
  • the intermediate dielectric elements are substantially identical.
  • the dielectric elements are integral with respective dielectric rods capable of rotating along the corresponding axis of rotation.
  • the rotational angles are variable as a function of the temperature so as to maintain the values of the central frequencies constant during a temperature variation.
  • the invention also relates to a microwave circuit comprising at least one such filter.
  • the invention consists in producing a tunable band pass filter in central frequency by rotation of dielectric elements in metal cavities, the input and output dielectric elements having a specific shape.
  • the filter according to the invention operates in a disturbed cavity mode.
  • An empty metal cavity has, according to its geometry, one or more resonance modes characterized by a frequency f of the microwave wave present in the cavity and by a particular distribution of the electromagnetic field.
  • resonance modes TE for Transverse Electrique
  • TM for Transverse Magn
  • a cavity containing a dielectric element (called disturbing element) disturbing the electromagnetic field inside the cavity is also able to resonate.
  • the figure 4 discloses a frequency-tunable bandpass filter 100 according to one aspect of the invention.
  • the microwave wave propagates along a Z axis.
  • the filter 100 comprises an input resonator R1 comprising a metal inlet cavity C1 and an input dielectric element E1 disposed inside the cavity.
  • the dielectric element E1 is able to disturb the resonance mode of the microwave wave in the input cavity.
  • the intrinsic nature of the mode, corresponding to the resonance mode of the cavity without the dielectric element, is not modified, but the mode of the cavity is very disturbed by the addition of the dielectric element E1.
  • the element E1 adds a capacitive effect which disturbs the resonance mode of the microwave wave in the cavity, and modifies the resonant frequency of the initial resonator formed by the cavity without the dielectric element.
  • the filter 100 also includes an output resonator RN comprising a metallic CN output cavity and an output dielectric element EN disposed within the CN cavity.
  • the output dielectric element EN has the same properties as those of the input dielectric element E1.
  • a TM mode is chosen on which it is easier to obtain a capacitive effect.
  • a TM mode is chosen on which it is easier to obtain a capacitive effect.
  • a parallel association resistance-capacitance-inductance resonator RLC
  • This circuit has a resonance frequency function of the product L.C. When playing on the capacitive effect, the resonance frequency varies.
  • the filter 100 comprises an input excitation means S1 of elongate shape along the Z axis penetrating inside the input cavity C1 .
  • This excitation means is typically a probe, such as a coaxial probe, of elongate shape, such as a cable.
  • the filter 100 comprises an Z-shaped elongated output excitation means Z penetrating inside the output cavity CN.
  • This excitation means is typically a probe, such as a coaxial probe, of elongate shape, such as a cable.
  • the inlet and outlet cavities are coupled to each other and respectively coupled to the input and output excitation means, so that the microwave wave introduced by the input excitation means into the filter 100 , propagates in the resonators in a resonance mode, and comes out of the filter.
  • the input and output dielectric elements according to the invention have a specific shape which has a recess.
  • the input energizing means penetrates inside the recess 41 of the input dielectric element so that the input dielectric element disturbs the electromagnetic field in the vicinity of the excitation means. 'Entrance.
  • the output excitation means penetrates inside the recess 42 of the output dielectric element so that the output dielectric element disturbs the electromagnetic field in the vicinity of the output excitation means.
  • the input dielectric element is adapted to rotate about an input rotation axis X1, the recess being adapted to allow rotation of the dielectric element while maintaining the element of input excitation inside the recess.
  • the output dielectric element is adapted to rotate about an output rotation axis XN, the recess being adapted to allow rotation of the dielectric element while maintaining the excitation element of exit inside the recess.
  • the excitation element inside the recess makes it possible to maintain a strong disturbance of the electromagnetic field in the vicinity of the element while ensuring a controlled coupling between excitation and resonator. This is essential for controlling the bandwidth, and for adapting the filter.
  • the distance between the excitation elements S1, SN and the respective dielectric elements E1, EN inside the recess is chosen as a function of the desired filter.
  • a broad bandpass filter requires strong coupling and therefore a distance as small as possible, limited by mechanical manufacturing tolerances and costs, typically a hundred microns.
  • a narrow bandwidth filter requires a lower coupling and therefore a slightly larger distance, typically from 1 to a few mm.
  • the rotations of the dielectric elements modify the capacitive effect, disturbing the electric field differently depending on the angular position of the dielectric elements.
  • the filter operates for a TM mode.
  • TM mode the magnetic field is perpendicular to the propagation direction Z and the electric field E is collinear with Z.
  • the preferred TM mode is of the TM 010 type.
  • the maximum of the electric field E is concentrated in the center of the cavity of the resonator.
  • the cavities of the resonators of the filter according to the invention are aligned, and the Z direction corresponds to the axis passing through the center of the cavities. The maximum field E is concentrated near Z.
  • the capacitive effect induced by the presence of a disturbing dielectric is a function of the amount of dielectric material (dielectric permittivity) "seen" by the field E. Increasing the amount of dielectric "seen” by the electric field increases the capacitive effect of the resonator. the contrast obtained on the capacitive effect is maximized when this variation is localized on a maximum of electric field.
  • a plane Pe is defined for each dielectric element. This plane is perpendicular to the height h (smaller dimension) of the dielectric element.
  • h small dimension
  • the quantity of material traversed by the field E in the vicinity of Z is much smaller than when the planes Pe of the dielectric elements comprise the Z axis. A high contrast of effect capacitive between the two positions is obtained, which induces a central frequency variation of the larger filter.
  • the rotation of a dielectric element takes place at a teta angle with respect to a given reference point.
  • the value of the center frequency of the filter fc is a function of the teta angle that the element E1 makes and the tetab angle that the element E2 makes.
  • a center frequency corresponds to an angular position of the dielectric elements.
  • the dielectric element E1 has a flattened shape respectively having a height h1 smaller than the external dimensions in a plane Pe perpendicular to the direction carrying the height h1.
  • the outer dimensions are the largest dimensions (I1 and L1 in the example of the figure 4 ) dielectric elements not taking into account the recess.
  • the dielectric element EN has a flattened shape respectively having a height hN less than the external dimensions (IN and LN in the example of FIG. figure 4 ) in a plane Pe perpendicular to the direction carrying the height hN.
  • the height is at least a factor 3 smaller than the smallest dimension in the plane Pe perpendicular to the direction carrying the height.
  • the figure 7a describes an example of a filter according to the invention when E1 and EN make an identical angle teta0, and equal to 0 ° by convention, corresponding to a central frequency value fc0.
  • the figure 7b describes the filter according to the invention when E1 and E2 make an identical teta90 angle, and equal to 90 ° with respect to the first position of E1 and E2, corresponding to a central frequency value fc90.
  • the filter according to the invention is a band pass filter whose central frequency can be chosen in a frequency range depending on the angular orientation of the dielectric elements.
  • the center frequency can be chosen continuously in the range of variation.
  • a correction (readjustment of the central frequency) according to the temperature is possible.
  • the adjustment of the angular positions is effected by means of control means, such as a motor.
  • the input dielectric element E1 and the output dielectric element EN are respectively located substantially in the center of the input cavity and of the output cavity. A maximum concentration of the electric field is thus obtained in the vicinity of the input and output excitation means, which makes it possible to ensure the sufficient and controlled coupling of the excitations with the resonators 1 and N.
  • the input dielectric elements E1 and output EN are U-shaped.
  • the shape comprises a body and two branches so as to make the recess 41 or 42; the dielectric elements are thus easy to manufacture. There is no flatness constraint on the shape of the dielectric elements.
  • the input and output excitation means are coaxial probes arranged along the same axis Z.
  • the filter comprises only two resonators, the input resonator R1 and the output resonator RN.
  • the two resonators are coupled together by coupling means, such as one or more slots.
  • the input dielectrics E1 and output EN are substantially identical, in shape and in material.
  • the figure 5 describes a preferred embodiment of an aspect of the invention for which the filter 100 further comprises at least one intermediate resonator Ri, a resonator being indexed according to an index i ranging from 2 to N-1, depending on the number of resonators intermediate.
  • the figure 5a describes a perspective view of the filter.
  • Each intermediate resonator Ri comprises an intermediate metal cavity Ci and an intermediate dielectric element Ei disposed inside the cavity Ci and capable of disturbing the resonance mode of the microwave wave in the cavity, the dielectric element Ei being adapted to rotate around an intermediate axis of rotation Xi.
  • each intermediate dielectric element Ei also has a flattened shape having a height hi less than the dimensions Li and Li (with Ii ⁇ Li for the example of the figure 5 ) in a plane Pe perpendicular to the direction bearing hi.
  • the height hi is at least a factor of 3 smaller than the smallest dimension li in the plane Pe perpendicular to the direction carrying the height hi. .
  • the intermediate dielectric elements have a flattened solid shape which does not necessarily have a recess as they are coupled to each other and not to an elongated excitation element such as the input and output dielectric elements.
  • the resonators are coupled two to two i / i + 1 in series, by coupling means, such as slots. These slots make it possible to couple at the same time a part of the electric field E and a part of the magnetic field H.
  • a coupling by field E has a sign opposite to a coupling by field H. identical proportions, the two couplings cancel each other out.
  • the positions and the dimensions of the slots are determined by optimization so that the resulting bandwidth is substantially constant during the rotation of the dielectric elements.
  • the input means S1 is a coaxial probe.
  • the axes of rotation of X1, X2 .. X1 to XN are perpendicular to the Z axis.
  • the axes of rotation X1, X2 .. Xi to XN are concurrent with the Z axis.
  • the intermediate elements symmetrical with respect to the medium of the filter are identical in shape, size and material.
  • the intermediate elements Ei are substantially identical in shape, size and material.
  • the filter is easier to calculate and to manufacture.
  • the rectangular shape of the dielectric elements shown is purely schematic and does not correspond to a preferred form.
  • the figure 6a corresponds to an element Ei intermediate in a cavity Ci in top view, the figure 6b in profile view.
  • the dotted area 61 illustrates a configuration where the capacitive effect is low.
  • the Figure 6c corresponds to the input dielectric element E1 in the cavity C1 when viewed from above, the figure 6d in profile view.
  • Dotted area 62 illustrates a configuration where the capacitive effect is low.
  • the figure 7a corresponds to an element Ei intermediate in a cavity Ci in top view, the figure 7b in profile view.
  • Dotted area 71 illustrates a configuration where the capacitive effect is strong.
  • the Figure 7c corresponds to the input dielectric element E1 in the cavity C1 when viewed from above, the figure 7d in profile view.
  • the dashed area 72 illustrates a configuration where the capacitive effect is strong.
  • a gradual and synchronous rotation of the dielectric elements E1, E1, EN makes it possible to continuously vary the central frequency fc of the filter.
  • each dielectric element E1, Ei, EN varies the amount of material traversed by the electric field E in the center of the cavities of the resonators, which has the effect of varying the capacitive effect of the resonator.
  • the figures 8 and 9 illustrate an embodiment of a filter according to the invention and the filter characteristics obtained.
  • the filter comprises 3 resonators R1, R2, RN comprising cavities C1, C2, CN of substantially square shape.
  • the size of the cavities C1 and CN is 16 mm, the dimension of C2 is 17 mm.
  • the 3 cavities have a height of 4.5 mm.
  • the dielectric elements E1, E2, EN are made of zirconia.
  • the input dielectric elements E1 and output EN have a dimension of 3.8 mm ⁇ 6.1 mm ⁇ 1.2 mm.
  • the height h of 1.2 mm is small compared to other dimensions by about a factor of 3 with the smaller of the other two dimensions.
  • the intermediate dielectric element E2 has dimensions of 4 mm x 4.1 mm x 1.2 mm (height h of 1.2 mm).
  • Resonators R2 and RN are connected by two slots of dimension 7mm x 2.5 mm, 5.5 mm apart. Unrepresented screws (6 per cavity) allow fine tuning of TM mode resonance and couplings.
  • the figure 8a represents a profile view of the filter and the figure 8b a perspective view.
  • the figure 9a represents a profile view of the filter and the figure 9b a perspective view
  • the flattened shapes of the dielectric elements are optimized to maximize the difference in capacitive effect and thus the frequency shift.
  • the dielectric elements E1, E2, EN are integral with holding means, preferably respective rods T1, T2, TN also of dielectric material capable of rotating
  • a rod and the dielectric element which is integral therewith form a single block of the same dielectric material which is manufactured in one piece.
  • the rod is made of dielectric material, it contributes to the disruptive effect of the dielectric element.
  • the rods Ti pass right through the associated disturbing element Ei and the cavity Ci, which ensures a better mechanical retention of the dielectric element in the cavity than with a single point of maintenance.
  • the curve S21 (0 °) corresponds to the transmission of the filter and the curve S11 (0 °) to reflection.
  • the bandwidth at -20 dB is deltaf (0 °) and the center frequency fc (0 °) is equal to 11.5 GHz.
  • Curve S21 (90 °) corresponds to the transmission of the wire and curve S11 (90 °) to reflection.
  • the bandwidth at -20 dB is deltaf (90 °) and the center frequency fc (90 °) is equal to 9.65 GHz.
  • the center frequency has changed from 9.65 GHz to 11.5 GHz.
  • the figure 10 illustrates another embodiment of a filter according to the invention in the same spirit as the described filter figures 8 and 9 .
  • the figure 10a discloses a perspective view of the filter for dielectric elements generally parallel to the Z axis and the figure 10b discloses a perspective view of the filter for dielectric elements generally perpendicular to the Z axis.
  • the filter comprises 6 resonators.
  • the figure 10c describes the transmission of the filter S12 for different angular positions of the dielectric elements between 0 ° and 90 °.
  • the center frequency varies according to the angle of inclination of the dielectric elements, between 9.65 GHz and 11.5 GHz.
  • the adaptation is of the order of 15 dB and the losses of the filter between 0.3 and 0.5 dB whatever the value of the angle of rotation.
  • the input and the output play a symmetrical role.
  • the temperature variations (typically a few tens of degrees) in the filter induce fluctuations in the dimensions of the cavities and dielectric elements, which generates central frequency variations for the same filter geometry.
  • rotation angles of the dielectric elements have variable values as a function of the temperature so as to correct the effects of the temperature on the central frequencies and thus maintain the values of these central frequencies. constant during a temperature change.
  • each central frequency value corresponds to an identical rotation angle for all the dielectric elements of the filter according to the invention and the value of this angle is temperature-controlled so as to maintain the central frequency at a determined value independent of the temperature. .
  • the invention also relates to a microwave circuit comprising at least one filter according to the invention.

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Claims (13)

  1. Frequenzanpassbarer Bandpassfilter (100) für Hyperfrequenzwelle, welcher eine Mittelfrequenz (fc) aufweist, wobei die Hyperfrequenzwelle sich entlang einer Achse Z fortpflanzt, wobei der Filter Folgendes beinhaltet:
    - einen Eingangsresonator (R1), welcher einen metallenen Eingangshohlraum (C1) und ein dielektrisches Eingangselement (E1) beinhaltet, welches im Innern des Eingangshohlraums angeordnet und in der Lage ist, den Resonanzmodus der Hyperfrequenzwelle in dem Eingangshohlraum zu stören,
    - einen Ausgangsresonator (RN), welcher einen metallenen Ausgangshohlraum (CN) und ein dielektrisches Ausgangselement (EN) beinhaltet, welches im Innern des Ausgangshohlraums angeordnet und in der Lage ist, den Resonanzmodus der Hyperfrequenzwelle in dem Ausgangshohlraum zu stören,
    - ein Eingangs-Erregungsmittel (S1) länglicher Form entlang der Achse Z, welches in den Eingangshohlraum (C1) eindringt, um es der Hyperfrequenzwelle zu ermöglichen, in den Eingangshohlraum einzudringen,
    - ein Ausgangs-Erregungsmittel (SN) länglicher Form entlang der Achse Z, welches in den Ausgangshohlraum (CN) eindringt, um es der Hyperfrequenzwelle zu ermöglichen, den Ausgangshohlraum zu verlassen,
    - wobei die Eingangs- (R1) und Ausgangsresonatoren (RN) gekoppelt sind, und
    - wobei die dielektrischen Eingangs- (E1) und Ausgangselemente (EN) eine Aussparung (41, 42) aufweisen,
    - wobei das Eingangs-Erregungsmittel (S1) in das Innere der Aussparung (41) des dielektrischen Eingangselementes (E1) so eindringt, dass das dielektrische Eingangselement (E1) das elektromagnetische Feld in der Nähe des Eingangs-Erregungsmittels (S1) stört,
    - wobei das Ausgangs-Erregungsmittel (SN) in das Innere der Aussparung (42) des dielektrischen Ausgangselementes (EN) so eindringt, dass das dielektrische Ausgangselement (EN) das elektromagnetische Feld in der Nähe des Ausgangs-Erregungsmittels stört,
    - wobei das dielektrische Eingangselement (E1) in der Lage ist, eine Drehung rund um die Eingangsdrehachse (X1) zu bewerkstelligen, wobei die Aussparung (41) geeignet ist, um die Drehung des dielektrischen Elementes (E1) zu ermöglichen und gleichzeitig das Eingangs-Erregungsmittel (S1) im Innern der Aussparung (41) zu halten,
    - wobei das dielektrische Ausgangselement (EN) in der Lage ist, eine Drehung rund um die Ausgangsdrehachse (XN) zu bewerkstelligen, wobei die Aussparung (42) geeignet ist, um die Drehung des dielektrischen Elementes (E2) zu ermöglichen und gleichzeitig das Ausgangs-Erregungsmittel (SN) im Innern der Aussparung (42) zu halten,
    - wobei jedes dielektrische Element (E1, EN) eine abgeflachte Form aufweist, welche eine Höhe besitzt, die mindestens dreifach geringer als die kleinste Außenabmessung in einer rechtwinkligen Ebene zur Höhenrichtung ist, - wobei die Drehungen der dielektrische Elemente (E1, EN) die Modifizierung der Mittelfrequenz des Filters ermöglichen.
  2. Filter nach dem vorhergehenden Anspruch, bei welchem das dielektrische Eingangselement (E1) und das dielektrische Ausgangselement (EN) jeweils im Wesentlichen im Mittelpunkt des Eingangshohlraums (C1) und des Ausgangshohlraums (CN) angeordnet sind.
  3. Filter nach einem der vorhergehenden Ansprüche, bei welchem die dielektrischen Eingangs- (E1) und Ausgangselemente (EN) U-förmig sind.
  4. Filter nach einem der vorhergehenden Ansprüche, beinhaltend Kopplungsmittel, welche geeignet sind, die Eingangs- (R1) und Ausgangsresonatoren (RN) direkt zu koppeln.
  5. Filter nach einem der Ansprüche 1 bis 3, zudem beinhaltend mindestens einen Zwischenresonator (Ri), welcher in Reihe zwischen dem Eingangsresonator (R1) und dem Ausgangsresonator (RN) angeordnet ist, beinhaltend einen metallenen Zwischenhohlraum (Ci) und ein dielektrisches Zwischenelement (Ei), welches innerhalb des Hohlraums (Ci) angeordnet und in der Lage ist, den Resonanzmodus der Hyperfrequenzwelle in dem Hohlraum zu stören, wobei jedes dielektrische Element (Ei) eine abgeflachte Form aufweist, welche eine Höhe besitzt, die mindestens dreifach geringer als die kleinste Außenabmessung in einer rechtwinkligen Ebene zur Höhenrichtung ist und in der Lage ist, eine Drehung rund um eine Zwischendrehachse (Xi) zu bewerkstelligen, wobei der Filter Kopplungsmittel beinhaltet, die zur Kopplung der Zwischenresonatoren jeweils paarweise in Reihe geeignet sind.
  6. Filter nach einem der vorhergehenden Ansprüche, bei welchem die Kopplungsmittel Schlitze sind.
  7. Filter nach einem der vorhergehenden Ansprüche, bei welchem die dielektrischen Elemente (R1, RN, Ri) eine identische Winkelposition besitzen, welche einer identischen Drehung entsprechen, wobei ein Wert des Drehwinkels einem Mittelfrequenzwert des Filters entspricht.
  8. Filter nach einem der vorhergehenden Ansprüche, bei welchem die Drehachsen (X1, XN, Xi) parallel zueinander sind.
  9. Filter nach einem der vorhergehenden Ansprüche, bei welchem die Drehachsen (X1, XN, Xi) rechtwinklig zur Achse Z sind.
  10. Filter nach einem der Ansprüche 5 bis 9, bei welchem die dielektrischen Zwischenelemente (Ei) im Wesentlichen identisch sind.
  11. Filter nach einem der vorhergehenden Ansprüche, bei welchem die dielektrischen Elemente (E1, EN, Ei) fest mit jeweiligen dielektrischen Stäben (T1, TN, Ti) verbunden sind, welche in der Lage sind, eine Drehung um die entsprechende Drehachse (X1, XN, Xi) zu bewerkstelligen.
  12. Filter nach einem der vorhergehenden Ansprüche, bei welchem die Werte der Drehwinkel von der Temperatur abhängen, so dass die Werte der Mittelfrequenzen bei einer Temperaturschwankung konstant gehalten werden.
  13. Hyperfrequenzschaltung, beinhaltend mindestens einen Filter nach einem der vorhergehenden Ansprüche.
EP13177704.7A 2012-07-27 2013-07-23 Frequenzanpassbarer Bandpassfilter für Hyperfrequenzwelle Active EP2690703B1 (de)

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FR1202127A FR2994028B1 (fr) 2012-07-27 2012-07-27 Filtre passe bande accordable en frequence pour onde hyperfrequence

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CN106558747A (zh) * 2015-09-28 2017-04-05 中兴通讯股份有限公司 一种谐振腔及其构成的滤波器
CN108574130B (zh) * 2017-03-13 2019-08-02 电子科技大学 微带滤波电路、微带双工器及相关电子器件
CN111903000A (zh) * 2018-05-04 2020-11-06 瑞典爱立信有限公司 可调波导谐振器
FR3083015B1 (fr) 2018-06-21 2021-12-17 Thales Sa Systeme hyperfrequence accordable
US10957960B2 (en) 2018-12-14 2021-03-23 Gowrish Basavarajappa Tunable filter with minimum variations in absolute bandwidth and insertion loss using a single tuning element
CN111384560A (zh) * 2018-12-31 2020-07-07 深圳市大富科技股份有限公司 介质滤波器、通信设备、制备介质块及介质滤波器的方法

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JPS61136302A (ja) * 1984-12-06 1986-06-24 Murata Mfg Co Ltd 誘電体共振器
US6147577A (en) * 1998-01-15 2000-11-14 K&L Microwave, Inc. Tunable ceramic filters
IT1320543B1 (it) * 2000-07-20 2003-12-10 Cselt Centro Studi Lab Telecom Cavita' caricata dielettricamente per filtri ad alta frequenza.
US20050200437A1 (en) * 2004-03-12 2005-09-15 M/A-Com, Inc. Method and mechanism for tuning dielectric resonator circuits
US7388457B2 (en) * 2005-01-20 2008-06-17 M/A-Com, Inc. Dielectric resonator with variable diameter through hole and filter with such dielectric resonators
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Publication number Publication date
CA2822129A1 (en) 2014-01-27
FR2994028A1 (fr) 2014-01-31
US9343792B2 (en) 2016-05-17
CA2822129C (en) 2020-12-22
FR2994028B1 (fr) 2015-06-19
EP2690703A1 (de) 2014-01-29
US20140028415A1 (en) 2014-01-30

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