EP2484183B1 - Ballast électronique et procédé de fonctionnement d'au moins une lampe à décharge - Google Patents

Ballast électronique et procédé de fonctionnement d'au moins une lampe à décharge Download PDF

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Publication number
EP2484183B1
EP2484183B1 EP10744908.4A EP10744908A EP2484183B1 EP 2484183 B1 EP2484183 B1 EP 2484183B1 EP 10744908 A EP10744908 A EP 10744908A EP 2484183 B1 EP2484183 B1 EP 2484183B1
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EP
European Patent Office
Prior art keywords
electronic switch
electronic
switch
control device
coupled
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Not-in-force
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EP10744908.4A
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German (de)
English (en)
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EP2484183A1 (fr
Inventor
Arwed Storm
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Osram GmbH
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Osram GmbH
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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/282—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices
    • H05B41/2825—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices by means of a bridge converter in the final stage
    • H05B41/2828—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices by means of a bridge converter in the final stage using control circuits for the switching elements

Definitions

  • the present invention relates to an electronic ballast for operating at least one discharge lamp having an input with a first and a second input terminal for coupling with a DC supply voltage, an output having a first and a second output terminal for coupling to the at least one discharge lamp, an inverter having a bridge circuit with at least a first and a second electronic switch and a control device for controlling at least the first and the second electronic switch such that the first and the second electronic switch are alternately turned on at a first frequency, the first and the second switch connected in series between the first and second input terminals are coupled, wherein the first electronic switch is coupled to the first input terminal and the second electronic switch is coupled to the second input terminal, wherein between the first and the second electronic switch, a first bridge center is formed, a current measuring device for measuring the current at least by the second electronic switch, a lamp inductor, which is serially coupled between the first bridge center and the first output terminal, at least one trapezoidal capacitor, which is parallel to a the two electronic switches is coupled and at least one coupling capacitor for coup
  • multi-lamp electronic ballasts electronic ballasts on the market, which are designed to operate different lamps, especially lamps of different power.
  • a problem in this context is to ensure a switch-relieved operation of the bridge circuit of the inverter at different loads.
  • switching during the conducting phase of the free-wheeling diode via the second electronic switch is ensured as follows: Using a half-bridge shunt resistor, the current in the lower bridge branch is measured. Falling below a negative threshold of this current is equated with the time at which the freewheeling diode of the lower switching element becomes conductive. This event triggers the switching on of the lower half-bridge switch and thus determines the dead time of the drive signals for the switches of the half-bridge.
  • the usually existing Resonant circuit can be designed with large resonance capacities.
  • this measure leads to increased reactive currents and thus to undesirably large losses in the inverter.
  • WO 2009/037613 A1 discloses an electronic ballast wherein the operating frequency is controlled.
  • the present invention is therefore based on the object of developing a generic electronic ballast or a generic method such that even with an operation of the electronic ballast in the vicinity of the phase jump at different connected loads a switch-unloaded operation can be provided with minimum losses.
  • the present invention is based on the finding that the above problem can be met if the frequency at which the switches of the half-bridge are operated is increased when a switching operation is detected after reaching the maximum dead time. By increasing this frequency, the operating frequency is shifted from inductive operation to a transient frequency between capacitive and inductive operation. This results in an increase of the negative current amplitude when taking over the current through the freewheeling diode of the lower switch. If the operating frequency of the two switches is increased so far that the specifiable negative threshold value of the current through the lower switch is exceeded again, so the known dead time control works again; a switch-unloaded operation of the switches of the inverter can be ensured.
  • Each of the two electronic switches comprises a control electrode, a working electrode and a reference electrode. It can now be provided that the path working electrode reference electrode is connected in parallel with a discrete diode as a freewheeling diode or that the freewheeling diode is a body diode of the electronic switch. The latter is the case, for example, when mosfet transistors are used as switches.
  • control device of an electronic ballast comprises a memory in which the predefinable period of time is stored. This opens up the possibility, in particular, of modifying these for specific lamps.
  • control device comprises a time-measuring device which is designed to determine the time duration after the blocking-end switching of the first electronic switch until the second electronic switch is turned on.
  • the control device is designed to carry out the following step: c1) If the measured time duration is equal to the predefinable time duration: Increase the first frequency by a predefinable step.
  • the control device is preferably designed to carry out the following step: c2) Repeat step c1) at any rate until the measured time duration is less than the predefinable time duration. This results in the sum that the operating frequency of the switches of the half-bridge is increased in predetermined stages until the dead time no longer corresponds to the maximum dead time. Since too much increase in the operating frequency of the switches of the half-bridge would reduce the power transferable to the lamp, this approach represents an optimal compromise between a switch-unloaded operation of the switches of the half-bridge and a maximum transmitted to the connected lamp power.
  • control device is designed to carry out the following step: d1) If the measured time duration is less than the predefinable time duration: decrease the first frequency by a predefinable step.
  • control device is preferably designed to carry out the following step: d2) Repeat step d1) until a predefinable value for the first frequency has been reached.
  • Fig. 1 shows a schematic representation of an embodiment of an electronic ballast according to the invention.
  • the invention is presented below using the example of an inverter with a half-bridge circuit, it will be obvious to a person skilled in the art that the principles according to the invention can also be applied to an inverter with a full-bridge circuit.
  • This in Fig. 1 illustrated electronic ballast has an input with a first E1 and a second input terminal E2 for coupling with a DC supply voltage.
  • this is the so-called intermediate circuit voltage U Zw , which is usually obtained from an AC line voltage.
  • This intermediate circuit voltage U Zw is applied to an inverter 10, comprising a first S1 and a second electronic switch S2 in a half-bridge arrangement.
  • a control device 12 is provided for controlling the switches S1, S2, a control device 12 is provided.
  • the control device 12 controls the switches S1, S2 in particular such that the first and the second switches S1, S2 are alternately turned on with a first frequency.
  • control device 12 is coupled to a current measuring device, which in the present case comprises a shunt resistor R S , which is arranged in series with the first switch S1.
  • the current flowing through the shunt resistor R S is denoted by I S.
  • the switches S1, S2 are designed as Mosfet, wherein for simplification of the following explanations, the respective body diode D1, D2, which acts here in each case as a freewheeling diode, is located.
  • a first half-bridge center HBM is formed, wherein the voltage dropping at the half-bridge center is designated U HBM .
  • a trapezoidal capacitor C t is coupled.
  • a lamp inductor ELF is coupled between the first half-bridge center HBM and a first output terminal A1 of the electronic ballast.
  • an output voltage U R is provided to a load R L , which in the present case comprises at least one discharge lamp.
  • a coupling capacitor C C is coupled.
  • Parallel to the series connection of the load R L and the coupling capacitor C C is a resonant capacitor C R coupled.
  • Fig. 2 shows a schematic representation of the dependence of the provided between the output terminals A1, A2 voltage U R of the operating frequency f R , with which the control device 12 controls the switches S1, S2, for two different loads R L.
  • Curve 1) represents a low-impedance load 1) (low burning voltage, low output power) with a resonant frequency f R1 , curve 2) a higher-impedance load 2) with a resonant frequency f R2 .
  • the frequency f R2 is greater than the frequency f R1 .
  • the frequency f o of the resonant circuit with the first-mentioned load (curve 1)) would be operated inductively, with the second-mentioned load (curve 2)) capacitive.
  • Fig. 3 shows the time courses of different sizes of the embodiment of Fig. 1 , It shows in particular the time course of the on and off state of the switch S2 (curve a)), the voltage U HBM (curve b)) and the on and off state of the switch S1 (curve c)).
  • phase 1 the switch S2 is on, that is conductive. This is the reason Potential at the half-bridge center on the potential of the intermediate circuit voltage U Zw .
  • the switch S1 is off during this time.
  • the current through the shunt resistor R S is also zero. In phase 1, therefore, the current flows through the switch S2, the inductor L R to the load R L.
  • phase 2 The transition to phase 2 is characterized in that the switch S2 goes into the off state, while the switch S1 is not yet turned on.
  • the current driven by the inductor L R thus flows from the trapezoidal capacitor C t through the inductor L R to the load R L.
  • the potential at the half-bridge center is linearly reduced to zero.
  • the beginning of phase 2 corresponds to the beginning of the dead time t dead .
  • phase 2 to phase 3 The transition from phase 2 to phase 3 is characterized in that the trapezoidal capacitor is discharged.
  • the freewheeling diode D1 becomes conductive and clamps the voltage at the half-bridge center to approximately -0.7 V.
  • the current now flows through the freewheeling diode D1, the inductor L R to the load R L. With reference to curve d), therefore, a negative current I S flows from the time when the freewheeling diode D1 has become conductive. If this reaches a Threshold I Thres , then this is used according to the prior art to trigger the switch-on of the switch S1.
  • the switch-on operation of the switch S1 represents the beginning of the phase 4.
  • the period between the beginning of the phase 2 and the end of the phase 3 represents the dead time t dead .
  • the phase 3 designates the time interval within which the switch S1 can be switched switched-off ,
  • the voltage U HBM dropping across the switch S1 is equal to zero within this period.
  • phase 4 the current now begins to flow through the switch S1, as a result of which the current flow in phase 4, see curve d), runs approximately sinusoidally until the switch S1 is switched off.
  • Fig. 4 shows a schematic representation of a signal flow graph for controlling the dead time t dead .
  • the method starts in step 100.
  • step 120 it is checked whether the dead time t dead measured by the time measuring device is equal to the predefinable time period t timeout .
  • step 140 the frequency f R , with which the switches of the half-bridge are operated, increased. Subsequently, step 120 is repeated. By the action of step 140, see Fig. 2 , the resonant frequency again shifted into the inductive range. This results in a larger negative current amplitude when taken over by the freewheeling diode, whereby the dead time control works again.
  • step 160 it is checked in step 160 whether the current operating frequency f R is greater than a nominal operating frequency f nom .
  • the nominal operating frequency f nom represents a minimum operating frequency of the electronic ballast. If it is determined that the current operating frequency f R is above the nominal operating frequency f nom , the operating frequency f R is reduced in step 180 and then branched back to the start.
  • step 160 if it is determined in step 160 that the nominal operating frequency f nom has been reached, then without a change in the current operating frequency f R, it is branched back to the start.
  • steps 160, 180 is of particular importance when initially a lamp with a higher operating voltage has been operated on the electronic ballast and its burning voltage has subsequently dropped, for example due to thermal effects. Without regulation to the nominal operating frequency f nom , the lamp would in this case be operated permanently at increased frequency and thus at reduced power.
  • the in Fig. 4 illustrated regulatory relationship on the one hand, a functioning of the dead time control, on the other hand, an operation of each connected to the electronic ballast lamp with the optimum operating frequency.
  • the increase of the half-bridge frequency can be digital, for example by digital PWM registers for the switch-on times of the switching elements, or analogously by an offset at the input of a VCO or CCO.
  • the trapezoidal capacitor C t and the coupling capacitor C C may also be located elsewhere.

Claims (11)

  1. Ballast électronique pour faire fonctionner au moins une lampe à décharge (RL), avec
    - une entrée comprenant une première (E1) et une deuxième borne d'entrée (E2) pour le couplage d'une tension continue d'alimentation (UZw) ;
    - une sortie comprenant une première (A1) et une deuxième borne de sortie (A2) pour le couplage de la au moins une lampe à décharge (RL) ;
    - un onduleur (10) comprenant un circuit en pont avec au moins un premier (S1) et un deuxième commutateur électronique (S2) et un dispositif de commande (12) destiné à commander au moins le premier (S1) et le deuxième commutateur électronique (S2) de manière que le premier (S1) et le deuxième commutateur électronique (S2) soient alternativement commutés à l'état passant avec une première fréquence (fR), le premier (S1) et le deuxième commutateur (S2) étant couplés en série entre la première (E1) et la deuxième borne d'entrée (E2), le deuxième commutateur électronique (S2) étant couplé à la première borne d'entrée (E1) et le premier commutateur électronique (S1) à la deuxième borne d'entrée (E2), entre le premier (51) et le deuxième commutateur électronique (52) étant formé un premier point central de pont (HBM);
    - un dispositif de mesure de courant (RS) pour mesurer le courant (IS) qui traverse au moins le premier commutateur électronique (S1) ;
    - une bobine de choc de lampe (LR) couplée en série entre le premier point central de pont (HBM) et la première borne de sortie (A1) ;
    - au moins un condensateur trapézoïdal (Ct) couplé en parallèle à l'un des deux commutateurs électroniques (S1 ; S2) ; et
    - au moins un condensateur de couplage (CC) pour le
    couplage de la charge ;
    le dispositif de commande (12) étant couplé au dispositif de mesure de courant (RS) et étant conçu pour commuter le premier commutateur électronique (S1) à l'état passant
    a) si une valeur seuil négative (IThres) prédéfinissable du courant (IS) traversant le premier commutateur électronique (S1) est dépassée après la commutation du deuxième commutateur électronique (S2) à l'état bloqué ; ou
    b) si la valeur seuil négative (IThres) prédéfinissable du courant (IS) traversant le premier commutateur électronique (S1) n'est pas dépassée après la commutation du deuxième commutateur électronique (S2) à l'état bloqué : après une période de temps prédéfinissable (ttimeout) ;
    caractérisé en ce que
    le dispositif de commande (12) est conçu pour augmenter la première fréquence (fR) dans le cas b).
  2. Ballast électronique selon la revendication 1, caractérisé en ce que
    chacun des deux commutateurs électroniques (S1, S2) comprend une électrode de commande, une électrode de travail et une électrode de référence, une diode de roue libre (D2, D1) étant montée en parallèle à la ligne électrode de travail - électrode de référence.
  3. Ballast électronique selon la revendication 2, caractérisé en ce que
    la diode de roue libre (D2, D1) constitue une diode intrinsèque du commutateur électronique (S2, S1).
  4. Ballast électronique selon la revendication 2,
    caractérisé en ce que
    la diode de roue libre (D2, D1) constitue une diode discrète.
  5. Ballast électronique selon l'une des revendications précédentes,
    caractérisé en ce que
    le dispositif de commande (12) comprend une mémoire dans laquelle la période de temps prédéfinissable (ttimeout) est déposée.
  6. Ballast électronique selon l'une des revendications précédentes,
    caractérisé en ce que
    le dispositif de commande (12) comprend un dispositif de mesure du temps qui est conçu pour déterminer la période de temps après la commutation à l'état bloqué du deuxième commutateur électronique (S2) jusqu'à la commutation à l'état passant du premier commutateur électronique (S1).
  7. Ballast électronique selon la revendication 6,
    caractérisé en ce que
    le dispositif de commande (12) est conçu pour exécuter l'étape suivante :
    c1) si la période de temps mesurée (tdead) est égale à la
    période de temps prédéfinissable (ttimeout) (étape 120) :
    augmentation de la première fréquence (fR) d'un incrément prédéfinissable (étape 140).
  8. Ballast électronique selon la revendication 7,
    caractérisé en ce que
    le dispositif de commande (12) est conçu en outre pour exécuter l'étape suivante :
    c2) répétition de l'étape c1) du moins jusqu'à ce que la
    période de temps mesurée (tdead) soit inférieure à la période de temps prédéfinissable (ttimeout).
  9. Ballast électronique selon l'une des revendications 7 ou 8, caractérisé en ce que
    le dispositif de commande (12) est conçu en outre pour exécuter l'étape suivante :
    d1) si la période de temps mesurée (tdead) est inférieure à
    la période de temps prédéfinissable (ttimeout) (étape 160) :
    diminution de la première fréquence (fR) d'un incrément prédéfinissable (étape 180).
  10. Ballast électronique selon la revendication 9,
    caractérisé en ce que
    le dispositif de commande (12) est conçu en outre pour exécuter l'étape suivante :
    d2) répétition de l'étape d1) jusqu'à ce qu'une valeur
    prédéfinissable pour la première fréquence (fR) soit atteinte.
  11. Procédé pour faire fonctionner une lampe à décharge (RL) sur un ballast électronique avec une entrée comprenant une première (E1) et une deuxième borne d'entrée (E2) pour le couplage d'une tension continue d'alimentation (UZw) ; avec une sortie comprenant une première (A1) et une deuxième borne de sortie (A2) pour le couplage de la au moins une lampe à décharge (RL) ; avec un onduleur (10) comprenant un circuit en pont avec au moins un premier (S1) et un deuxième commutateur électronique (S2) et un dispositif de commande (12) pour commander au moins le premier (S1) et le deuxième commutateur électronique (S2) de manière que le premier (S1) et le deuxième commutateur électronique (S2) soient alternativement commutés à l'état passant avec une première fréquence (fR), le premier (S1) et le deuxième commutateur (S2) étant couplés en série entre la première (E1) et la deuxième borne d'entrée (E2), le deuxième commutateur électronique (S2) étant couplé à la première borne d'entrée (E1) et le premier commutateur électronique (S1) à la deuxième borne d'entrée (E2), entre le premier (S1) et le deuxième commutateur électronique (S2) étant formé un premier point central de pont (HBM) ; avec un dispositif de mesure de courant (RS) pour mesurer le courant (IS) qui traverse au moins le premier commutateur électronique (S1) ; avec une bobine de choc de lampe (LR) couplée en série entre le premier point central de pont (HBM) et la première borne de sortie (A1) ; avec au moins un condensateur trapézoïdal (Ct) couplé en parallèle à l'un des deux commutateurs électroniques (S1 ; S2) ; et avec au moins un condensateur de couplage (CC) pour le couplage de la charge ; le dispositif de commande (12) étant couplé au dispositif de mesure de courant (RS) et étant conçu pour commuter le premier commutateur électronique (S1) à l'état passant,
    a) si une valeur seuil négative (IThres) prédéfinissable du courant (IS) traversant le premier commutateur électronique (S1) est dépassée après la commutation du deuxième commutateur électronique (S2) à l'état bloqué; ou
    b) si la valeur seuil négative (IThres) prédéfinissable du courant (IS) traversant le premier commutateur électronique (S1) n'est pas dépassée après la commutation du deuxième commutateur électronique (S2) à l'état bloqué : après une période de temps prédéfinissable (ttimeout) ;
    caractérisé par l'étape suivante :
    augmentation de la première fréquence (fR) dans le cas b) (étape 140).
EP10744908.4A 2009-09-29 2010-08-12 Ballast électronique et procédé de fonctionnement d'au moins une lampe à décharge Not-in-force EP2484183B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE200910043611 DE102009043611A1 (de) 2009-09-29 2009-09-29 Elektronisches Vorschaltgerät und Verfahren zum Betreiben mindestens einer Entladungslampe
PCT/EP2010/061769 WO2011038974A1 (fr) 2009-09-29 2010-08-12 Ballast électronique et procédé de fonctionnement d'au moins une lampe à décharge

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EP2484183A1 EP2484183A1 (fr) 2012-08-08
EP2484183B1 true EP2484183B1 (fr) 2013-12-25

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US (1) US8994285B2 (fr)
EP (1) EP2484183B1 (fr)
CN (1) CN102577626B (fr)
DE (1) DE102009043611A1 (fr)
WO (1) WO2011038974A1 (fr)

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Publication number Priority date Publication date Assignee Title
US8947893B2 (en) * 2010-11-11 2015-02-03 Fairchild Korea Semiconductor Ltd. Switch controller and converter including the same for prevention of damage
DE102016124116A1 (de) * 2016-12-12 2018-06-14 Sml Verwaltungs Gmbh Vorrichtung zur Ansteuerung einer Strahlungsquelle zum Aushärten von Auskleidungsschläuchen

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US5604411A (en) * 1995-03-31 1997-02-18 Philips Electronics North America Corporation Electronic ballast having a triac dimming filter with preconditioner offset control
CN1179077A (zh) 1996-09-19 1998-04-15 通用电气公司 高压集成电路驱动半桥气体放电灯镇流器
US5925990A (en) * 1997-12-19 1999-07-20 Energy Savings, Inc. Microprocessor controlled electronic ballast
JP2003517257A (ja) * 1999-12-18 2003-05-20 コーニンクレッカ フィリップス エレクトロニクス エヌ ヴィ 共振回路素子を含む変換器
CN1389088A (zh) * 2000-08-28 2003-01-01 皇家菲利浦电子有限公司 电路设备
KR20040029082A (ko) 2001-08-28 2004-04-03 코닌클리즈케 필립스 일렉트로닉스 엔.브이. 하프 브리지 회로 및 이를 포함하는 장치
DE102006022819A1 (de) * 2005-05-23 2007-01-04 Infineon Technologies Ag Schaltungsanordnung zum Versorgen einer Last mit einem Ausgangsstrom
JP2008159382A (ja) * 2006-12-22 2008-07-10 Koito Mfg Co Ltd 放電灯点灯回路
DE102006061357B4 (de) 2006-12-22 2017-09-14 Infineon Technologies Austria Ag Verfahren zur Ansteuerung einer Leuchtstofflampe
CN101803164A (zh) * 2007-09-18 2010-08-11 Nxp股份有限公司 避免电容性模式的半桥谐振转换器的控制

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WO2011038974A1 (fr) 2011-04-07
DE102009043611A1 (de) 2011-04-07
US8994285B2 (en) 2015-03-31
CN102577626A (zh) 2012-07-11
EP2484183A1 (fr) 2012-08-08
US20120181945A1 (en) 2012-07-19
CN102577626B (zh) 2014-12-10

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