EP2270956A2 - Synchronous electric machine comprising a stator and at least one rotor and associated control device. - Google Patents

Abstract

The machine has a stator (10) and a rotor (20) with permanent magnets (21). The stator, rotor and magnets are arranged such that its direct reactance (X d) is greater than quadrature reactance (X q). Polar units of the rotor have a protruding part extending in a direction of the stator having a radial edge staggered angularly with respect to another edge. Independent claims are also included for the following: (a) A set e.g. washing machine, having synchronous electrical machine (b) a control process for synchronous electrical machine.

Description

The present invention relates to the field of rotating electrical machines.

The invention relates more particularly but not exclusively to permanent magnet synchronous machines that can operate at a substantially constant power over a wide range of speeds, for example lifting or electric traction machines.

In the context of lifting, it is useful to adapt the lifting speed to the lifting load in order to reduce the lifting time when this load is low while allowing lifting of the heavier parts.

In the case of electric traction, when starting or when the vehicle approaches a climb, the engine must provide a high torque at low speed. On the other hand, on a horizontal course, the efforts to be provided are smaller, and the vehicle can drive faster without requiring more engine power.

Synchronous machines can operate at constant torque up to a certain speed called base speed. Up to this basic speed, the power increases substantially in proportion to the speed of rotation of the rotor. Beyond the base speed, the torque decreases at substantially constant power.

The phases of the armature can each be modeled by an inductance which groups together the terms of self-induction, phase mutuals and leakage. This inductance depends on the angular position of the rotor relative to the stator, and its components in a reference linked to the electrical pulsation the direct inductance L _d and the quadrature inductance L _q . The direct reactance X _d designates the product of the direct inductance L _d by the electric pulsation ω, and the quadrature reactance X _q designates the product of the inductance Lq in quadrature by the electric pulsation ω. The speed of rotation of the rotor Ω is related to the electric pulsation ω by the relation ω = zΩ, where z denotes the number of pairs of poles.

In the reference linked to the electrical pulsation, the direct inductance L _d of a phase of the armature is the value of the inductance in the direct d axis, that is to say when the axis of the Inductor poles coincide with that of the stator coils of this same phase. The quadrature inductance Lq is the value of the inductance in the quadrature q axis, that is to say when the axis of the inductive poles is perpendicular to the axis of the stator coils for this same phase.

The rotating electric machines with permanent magnets known for lifting and electric traction are mostly so-called smooth-poles machines, for which the direct reactance X _d is substantially equal to the quadrature reactance X _q .

In addition to machines with smooth poles, there are also so-called inverted saliency machines, for which the direct reactance X _d is much smaller than the quadrature reactance X _q . Their main advantage is that the reluctance torque, which is proportional to the difference between the reactances X _q and X _d , is added, in normal operation, to the electromotive force torque generated by the magnets, which makes it possible, at the requested torque identical, reduce the volume of magnets and therefore the price of the machine. For this type of machine, there is an optimal offset in phase advance of the current with respect to the electromotive force for which the torque is maximum. It is this operating point that is held up to the base speed.

Beyond the base speed, the voltage across the phases of the machine becomes all other things equal higher than the available voltage supplied by the network to the machine through the control device, due to the force electromotive which varies in proportion to the speed.

To reduce the voltage across the phases of the machine, it acts on the current in the stator windings and on its phase shift with respect to the inductor flux, that is to say that of the magnets, to create a magnetic flux s' partially opposing the inducing flux. This operation is called "defluxing" and generates electrical losses all the more important as the current required for defluxing is high.

There is a need to improve synchronous machines and enable them to operate with high efficiency at substantially constant power over a wide range of speeds, and especially beyond basic speed.

The invention responds to this need by means of a synchronous electric machine comprising a stator and at least one rotor with permanent magnets, the machine being characterized in that it is arranged so as to have X _d > X _q ,
where X _d is the direct reactance and X _{q is} the quadrature reactance. For example, X _d / X _q > 1.1, better X _d / X _q > 1.5. We can have for example X _d / X _q ≅ 3.

The advantages provided by the invention are as follows.

On the one hand, the power factor cos φ varying in the opposite direction of the quadrature reactance X _q , a low value of X _q makes it possible to obtain a high power factor. For example, according to the desired power factor level, X _q I _o / E between 0.33 and 0.6, where I _o denotes the maximum intensity of the line current imposed by the dimming of the drive and E the phase-induced electromotive force of the machine.

On the other hand, the flux of the magnets being oriented in the direct axis d, field weakening is performed by injecting a current in the armature so as to generate in the direct axis of a flux proportional to the reactance X _of and the component I _d of the intensity in the direct axis. With a direct reactance X _d high, we obtain a large defluxage with less direct current I _d and therefore less corresponding losses, which has the effect of reducing the size of the control device and improve the efficiency.

In addition, with X _d high, the risk of demagnetization is reduced in the event of a short circuit, related to the value of the short-circuit current. This current is proportional to the ratio between the electromotive force and the direct reactance, and is therefore weak when the direct reactance X _d is large. For example, according to the required defluxing range, X _d I _o / E between 0.66 and 1, where I _o denotes the maximum intensity of the line current imposed by the caliber of the variator and E the electromotive force induced. per phase of the machine.

Up to the basic speed, the machine can operate with a current in phase with the electromotive force. The electromotive force torque is maximum and the reluctance torque is zero. The base speed may be greater than 100 or 200 revolutions per minute, for example.

In a particular embodiment, the stator comprises teeth each carrying at least one individual coil and these teeth are devoid of pole spurs. This allows in particular the establishment on the teeth of prefabricated coils, which simplifies the manufacture of the machine.

The rotor is advantageously at flux concentration, the permanent magnets of the rotor then being arranged between polar parts. This reduces the amount of magnets, thus reducing the cost of the machine.

The values of the direct and quadrature reactances can be determined by the shape of the pole pieces of the rotor, and in particular by the shape of the protruding parts of these pole pieces.

The projecting portions of two successive pole pieces can define between them a notch having two opposite edges having radial portions and a bottom partially formed by a face of at least one permanent magnet.

Such a shape of the pole pieces causes asymmetry between the direct and quadrature reactances and a relatively large positive difference between the direct and quadrature reactances.

The pole pieces of the rotor may each have a face facing the stator which has a convex portion. The convex portion of a pole piece may have a radius of curvature of between 20% and 30% of a radius of the stator, in particular of an inner radius of the stator, or even about 25%.

• entre $\frac{80°}{n_{\mathit{dents}}}$
  
  et $\frac{100°}{n_{\mathit{dents}}},$
  
  étant par exemple de $\frac{90°}{n_{\mathit{dents}}}$
  
  environ, pour une machine dont le rapport entre le nombre de dents n_dents du stator et le nombre de pôles n_pôles du rotor est de 3/2 ou qui vérifie la relation $\frac{n_{\mathit{dents}}}{n_{\mathit{pôles}}}=\frac{6n}{6n-2},$
  
  avec n entier supérieur ou égal à 2, et
• entre $\frac{50°}{n_{\mathit{dents}}}$
  
  et $\frac{70°}{n_{\mathit{dents}}},$
  
  étant par exemple de $\frac{60°}{n_{\mathit{dents}}}$
  
  environ, pour une machine qui vérifie la relation $\frac{n_{\mathit{dents}}}{n_{\mathit{pôles}}}=\frac{6n}{6n+2},$
  
  avec n entier supérieur ou égal à 2.

The circumferential ends of this convex portion may be angularly offset from the permanent magnets which are adjacent to this pole piece. The angular offset of the circumferential ends with respect to the adjacent permanent magnets can be understood as:

• enter $\frac{80°}{{\mathrm{not}}_{\mathit{teeth}}}$
  
  and $\frac{100°}{{\mathrm{not}}_{\mathit{teeth}}},$
  
  being for example of $\frac{90°}{{\mathrm{not}}_{\mathit{teeth}}}$
  
  approximately, for a machine whose ratio between the number of teeth n _teeth of the stator and the number of poles n _poles of the rotor is 3/2 or which verifies the relation $\frac{{\mathrm{not}}_{\mathit{teeth}}}{{\mathrm{not}}_{\mathit{poles}}}=\frac{6\mathrm{not}}{6\mathrm{not}-2},$
  
  with n integer greater than or equal to 2, and
• enter $\frac{50°}{{\mathrm{not}}_{\mathit{teeth}}}$
  
  and $\frac{70°}{{\mathrm{not}}_{\mathit{teeth}}},$
  
  being for example of $\frac{60°}{{\mathrm{not}}_{\mathit{teeth}}}$
  
  about, for a machine that checks the relationship $\frac{{\mathrm{not}}_{\mathit{teeth}}}{{\mathrm{not}}_{\mathit{poles}}}=\frac{6\mathrm{not}}{6\mathrm{not}+2},$
  
  with n integer greater than or equal to 2.

Each of the permanent magnets of the rotor may be located radially recessed from the circumferential ends of the convex portions of the two adjacent pole pieces. The shrinkage in the radial direction of the magnets with respect to the circumferential ends of the convex portions may be between 10% and 20%, being for example about 15%, of a radius of the stator, in particular of an inner radius of the stator.

Each of the pole pieces of the rotor may have two shoulders. A permanent magnet can be located between the shoulders of two adjacent pole pieces.

Each of the pole pieces of the rotor may have a protruding portion extending towards the stator, having radial edges which are angularly offset from radially directed edges of the permanent magnets adjacent to this pole piece.

The permanent magnets of the rotor may have, when the machine is observed along the axis of rotation of the rotor, a cross section of elongated shape in a radial direction. In particular, the permanent magnets of the rotor may have, when the machine is observed along the axis of rotation of the rotor, a rectangular cross section of large side oriented parallel to a radius of the machine.

In a particular implementation of the invention, the ratio X _d / X _q is chosen so as to obtain at the maximum speed of rotation of the rotor substantially the same power as that obtained at the base speed, with the same voltage and the same current.

Preferably, among the possible values for the ratio X _d / X _q making it possible to obtain the result mentioned above, the smaller one is chosen to avoid having a high saliency which would result in poles of smaller aperture and a larger equivalent gap, and this would increase the volume of magnets, so the price and weight of the machine. High saliency would also reduce the maximum torque that the machine would be able to provide, which would limit the possibility of overloading.

The stator may comprise 6n teeth and the rotor 6n ± 2 poles, n being greater than or equal to 2. Such a structure may make it possible to reduce both the torque oscillations and the voltage harmonics.

The machine may comprise a single inner rotor or, alternatively, an inner rotor and an outer rotor, arranged radially on either side of the stator and coupled in rotation. Using a dual rotor can reduce iron losses.

The machine can be a generator or a motor.

The power of the machine may be greater than or equal to 0.5 kW, being for example of the order of 1.5 kW, this value being in no way limiting.

• au moins un stator,
• au moins un rotor,

le rotor comportant des pièces polaires et des aimants permanents disposés entre les pièces polaires,
chaque pièce polaire comportant une partie saillante et de part et d'autre de cette partie saillante un épaulement.The invention further relates, independently or in combination with the foregoing, to an electric machine comprising:

• at least one stator,
• at least one rotor,

the rotor comprising polar parts and permanent magnets arranged between the pole pieces,
each pole piece having a protruding portion and on either side of this projecting portion a shoulder.

The shoulders of two adjacent pole pieces may come flush with the permanent magnet disposed between them.

Each projecting portion may be delimited in the circumferential direction by a radially extending edge.

Each pole piece may not cover the adjacent permanent magnets in the circumferential direction.

Each projecting portion may be delimited radially by a continuously rounded edge.

Each pole piece may be symmetrical with respect to a radially oriented median plane.

Each pole piece may comprise a stack of magnetic sheets.

The protruding portion may comprise a radially outer circular edge whose center of curvature is different from the center of rotation, the center of curvature being for example located on a radius between the center of rotation and the maximum half-diameter of the rotor.

The angular spacing between two adjacent projections may be greater than the angular width of the permanent magnet disposed between the corresponding pole pieces.

The permanent magnets may include an outer face facing the stator.

The invention further relates to a control device for controlling a machine as defined above.

$$\mathrm{i}=\sqrt{{\left(\frac{x}{x_q}\right)}^2+{\left(\frac{e-y}{x_d}\right)}^2},$$

le courant unitaire circulant dans une phase de l'induit,
(x, y) étant l'une des racines réelles des équations $${\mathrm{x}}^{\mathrm{2}}\mathrm{+}{\mathrm{y}}^{\mathrm{2}}=\frac{{\mathrm{v}}^{\mathrm{2}}}{{\mathrm{m}}^{\mathrm{2}}}\mathrm{et\; y}=\mathrm{e}\left(1-\frac{x_d}{x_d-x_q}\right)+\frac{p}{m}e\frac{x_d{x}_q}{x_d-x_q}\frac{1}{x},$$

m désigne le rapport entre la vitesse de rotation du rotor et la vitesse de base,
e est le rapport entre, d'une part, la force électromotrice, et d'autre part, le produit de m par la tension maximale par phase V_o imposée par le réseau d'alimentation,
v est le rapport entre la tension aux bornes d'une phase de l'induit et la tension V_o imposée par le réseau d'alimentation,
p est le rapport entre la puissance effective et la puissance constante P_o à laquelle on souhaite que la machine fonctionne, et
α le déphasage entre l'intensité et la force électromotrice.The subject of the invention is, independently or in combination with the foregoing, a control device for a synchronous motor enabling operation of the constant power motor P _o over a range of rotational speed of the rotor, comprising an arranged calculator for determining the values of direct currents I _d and quadrature I _q of the motor supply current, the intensities I _d and I _q being equal, within 20%, better within 10%, better still within 5% , to: I _d ≅ i _d .I _o ≅ -i sin α.I _o and I ≅ _q i _q i .I _o ≅ cos α.I _o, where I _o is the maximum intensity of the line current imposed by the control apparatus of the template, $$\mathrm{\alpha }=\arctan \left(\frac{x_q}{x_d}\frac{\left(e-\mathrm{there}\right)}{x}\right),$$

$$\mathrm{i}=\sqrt{{\left(\frac{\mathrm{<figure-callout\; id="2"\; label="x\; x\; q"\; filenames="imgf0001.png"\; state="\{\{state\}\}">x\; </figure-callout>}}{x_q}\right)}^2+{\left(\frac{e-\mathrm{there}}{{\mathrm{<figure-callout\; id="2"\; label="x\; d"\; filenames="imgf0001.png"\; state="\{\{state\}\}">x\; </figure-callout>}}_d}\right)}^2},$$

the unit current flowing in a phase of the armature,
(x, y) being one of the real roots of the equations $${\mathrm{x}}^{\mathrm{2}}\mathrm{+}{\mathrm{there}}^{\mathrm{2}}=\frac{{\mathrm{v}}^{\mathrm{2}}}{{\mathrm{<figure-callout\; id="2"\; label="m"\; filenames="imgf0001.png"\; state="\{\{state\}\}">m</figure-callout>}}^{\mathrm{2}}}\mathrm{and\; there}=\mathrm{e}\left(1-\frac{x_d}{x_d-x_q}\right)+\frac{p}{m}e\frac{x_d{x}_q}{x_d-x_q}\frac{1}{x},$$

m denotes the ratio between the rotational speed of the rotor and the base speed,
e is the ratio between, on the one hand, the electromotive force, and, on the other hand, the product of m by the maximum voltage per phase V _o imposed by the supply network,
v is the ratio between the voltage at the terminals of a phase of the armature and the voltage V _o imposed by the supply network,
p is the ratio between the effective power and the constant power P _o at which it is desired that the machine operates, and
α the phase difference between the intensity and the electromotive force.

By "direct intensity" and "quadrature intensity" is meant the values of the intensity projected on the direct d and quadrature axes q of the reference linked to the electrical pulsation.

X_d étant la réactance directe.We denote by x _d the quotient $\frac{{\mathrm{X}}_{\mathrm{d}}{\mathrm{I}}_{\mathrm{o}}}{\mathrm{m}{\mathrm{V}}_{\mathrm{o}}},$

X _d being the direct reactance.

où X_q est la réactance en quadrature.In the same way, ${\mathrm{x}}_{\mathrm{q}}\mathrm{=}\frac{{\mathrm{X}}_{\mathrm{q}}{\mathrm{I}}_{\mathrm{o}}}{\mathrm{m}{\mathrm{V}}_{\mathrm{o}}}\mathrm{,}$

where X _q is the quadrature reactance.

Such a control device shifts the current by an angle α relative to the electromotive force, while maintaining the constant voltage, and the component i _d of i in the direct axis d will create a flow that will oppose the main flow. The total magnetomotive force is therefore reduced, thereby causing a drop in the overall induced voltage.

The unit value i of the current can not be increased beyond its nominal value for reasons related to the heating of the machine and the caliber of the control device.

The desired voltage can be obtained with the minimum offset α, ie the lowest direct unit intensity i _d , in order to have more current in quadrature which contributes to the creation of the couple.

The deflux ratio is the maximum value of m which makes it possible to obtain the same power P _o as that obtained at the base speed with the same voltage V _o and the same current I _o defined previously. We can deduce the values of the electromotive force, and that of the direct and quadrature reactances for a given machine. The ratio X _d / X _q thus found for P _o , V _o and I _o given is an increasing function of the desired defluxing ratio, the latter being for example greater than 2, being for example equal to 6.

Among the possible solutions (x, y), the one that minimizes i is preferably chosen.

The control device which has just been described is preferably used in combination with a synchronous motor having X _d > X _q as defined above.

• un onduleur triphasé,
• un contrôleur vectoriel agencé pour transmettre en fonction des intensités i_d et i_q les signaux de commande aux interrupteurs électroniques de l'onduleur.

The control device may further comprise:

• a three-phase inverter,
• a vector controller arranged to transmit as a function of the intensities i _d and i _q the control signals to the electronic switches of the inverter.

The invention further relates, independently or in combination with the foregoing, to a method of controlling an engine in which at least the supply voltage of an inverter connected to the motor and the speed of rotation of the motor are measured. and calculating in real time and / or access to a register the direct i _d and quadrature i _q currents of the supply current for maintaining, for a speed reference Ω * given above the speed of base, constant power.

It is possible to determine a torque setpoint t * as a function of at least the difference between the measured rotational speed and the rotational speed reference of the rotor Ω *. A power setpoint can be determined as a function of at least the torque setpoint and the rotational speed measured. The direct unit intensities i _d and in quadrature i _q can be calculated in real time from the power setpoint, the rotational speed measured and the DC supply voltage of the inverter. The direct and quadrature currents can be determined according to the control laws as a function of the load and the supply voltage of the inverter. These control laws can be integrated into the computer to improve its dynamic performance.

• un stator, et
• au moins un rotor à aimants permanents,

le moteur étant agencé de manière à avoir X_d > X_q,
où X_d est la réactance directe et X_q la réactance en quadrature.The present invention further relates, independently or in combination with the foregoing, to an electric vehicle comprising a motor comprising:

• a stator, and
• at least one rotor with permanent magnets,

the motor being arranged to have X _d > X _q ,
where X _d is the direct reactance and X _{q is} the quadrature reactance.

$$\mathrm{i}=\sqrt{{\left(\frac{x}{x_q}\right)}^2+{\left(\frac{e-y}{x_d}\right)}^2},$$

le courant unitaire circulant dans une phase de l'induit,
(x, y) étant l'une des racines réelles des équations $${\mathrm{x}}^{\mathrm{2}}\mathrm{+}{\mathrm{y}}^{\mathrm{2}}=\frac{{\mathrm{v}}^{\mathrm{2}}}{{\mathrm{m}}^{\mathrm{2}}}\mathrm{et\; y}=\mathrm{e}\left(1-\frac{x_d}{x_d-x_q}\right)+\frac{p}{m}e\frac{x_d{x}_q}{x_d-x_q}\frac{1}{x},$$

m désigne le rapport entre la vitesse de rotation du rotor et la vitesse de base,
e est le rapport entre, d'une part, la force électromotrice, et d'autre part, le produit de m par la tension maximale par phase V_o imposée par le réseau d'alimentation,
v est le rapport entre la tension aux borne d'une phase de l'induit et la tension V_o imposée par le réseau d'alimentation,
p est le rapport entre la puissance effective et la puissance constante à laquelle on souhaite que la machine fonctionne, et
α le déphasage entre l'intensité et la force électromotrice.The vehicle may further comprise a control device of a synchronous motor, allowing operation of the constant power motor over a range of rotation speeds of the rotor, comprising a computer arranged to determine the values of the direct I _d and quadrature I currents _q of the supply current of the engine injected into the engine, the intensities I _d and I _q being equal, within 20%, better to within 10%, better still within 5%, to: I _d ≅ i _d -I _o ≅ sin α.I -i _o and _q I _q ≅ i .I _o ≅ i cos α.I _o where I _o is the maximum current required by the control device of the caliber, $$\mathrm{\alpha }=\arctan \left(\frac{x_q}{x_d}\frac{\left(e-\mathrm{there}\right)}{x}\right),$$

$$\mathrm{i}=\sqrt{{\left(\frac{\mathrm{<figure-callout\; id="2"\; label="x\; x\; q"\; filenames="imgf0001.png"\; state="\{\{state\}\}">x\; </figure-callout>}}{x_q}\right)}^2+{\left(\frac{e-\mathrm{there}}{{\mathrm{<figure-callout\; id="2"\; label="x\; d"\; filenames="imgf0001.png"\; state="\{\{state\}\}">x\; </figure-callout>}}_d}\right)}^2},$$

the unit current flowing in a phase of the armature,
(x, y) being one of the real roots of the equations $${\mathrm{x}}^{\mathrm{2}}\mathrm{+}{\mathrm{there}}^{\mathrm{2}}=\frac{{\mathrm{v}}^{\mathrm{2}}}{{\mathrm{<figure-callout\; id="2"\; label="m"\; filenames="imgf0001.png"\; state="\{\{state\}\}">m</figure-callout>}}^{\mathrm{2}}}\mathrm{and\; there}=\mathrm{e}\left(1-\frac{x_d}{x_d-x_q}\right)+\frac{p}{m}e\frac{x_d{x}_q}{x_d-x_q}\frac{1}{x},$$

m denotes the ratio between the rotational speed of the rotor and the base speed,
e is the ratio between, on the one hand, the electromotive force, and, on the other hand, the product of m by the maximum voltage per phase V _o imposed by the supply network,
v is the ratio between the voltage at the terminals of a phase of the armature and the voltage V _o imposed by the supply network,
p is the ratio between the effective power and the constant power at which it is desired that the machine operate, and
α the phase difference between the intensity and the electromotive force.

• la figure 1 représente de façon schématique et partielle, en coupe transversale, une machine conforme à l'invention,
• la figure 2 est un diagramme de Blondel représentant différentes grandeurs sinusoïdales dans un repère lié à la pulsation électrique,
• la figure 3 est un schéma simplifié en blocs d'un dispositif de commande d'un moteur synchrone conforme à l'invention, et
• la figure 4 représente schématiquement un exemple de réalisation du calculateur principal du dispositif de commande de la figure 3.

The present invention will be better understood on reading the following detailed description of a nonlimiting example of implementation of the invention, and on examining the appended drawing, in which:

• the figure 1 represents schematically and partially, in cross-section, a machine according to the invention,
• the figure 2 is a Blondel diagram representing different sinusoidal quantities in a reference linked to the electric pulsation,
• the figure 3 is a simplified block diagram of a control device of a synchronous motor according to the invention, and
• the figure 4 schematically represents an embodiment of the main computer of the control device of the figure 3 .

Electric machine

We have shown on the figure 1 a synchronous electric machine 1 comprising a stator 10 and a rotor 20 with permanent magnets 21.

The stator 10 comprises teeth 11 each carrying an individual coil 12, the coils 12 being electrically connected to each other so as to be supplied by a three-phase current.

The rotor 20 is at flux concentration, the permanent magnets 21 being disposed between pole pieces 22. The permanent magnets 21 and the pole pieces 22 are suitably fixed to a shaft 23 of the machine.

The pole pieces 22 can be held on the shaft 23 by gluing, or by making complementary shapes on the shaft and the pole pieces, or else be held by bars engaged in the pole pieces 22 and fixed at their ends to flanges of the rotor.

The pole pieces 22 are made by a stack of magnetic sheets each covered with an insulating varnish, in order to limit the losses by induced currents.

The magnets 21 have polarities of the same kind, directed towards the pole piece 22 arranged between them, as can be seen on the figure 1 .

The pole pieces 22 each comprise a projecting portion 27, and their face facing the stator 10 has a convex portion 24. The convex portion 24 of a pole piece 22 may have a radius of curvature of between 20% and 30%. a radius of the stator, in particular the inner radius of the stator, or even about 25%.

• entre $\frac{80°}{n_{\mathit{dents}}}$
  
  et $\frac{100°}{n_{\mathit{dents}}},$
  
  étant par exemple de $\frac{90°}{n_{\mathit{dents}}}$
  
  environ, pour une machine dont le rapport entre le nombre de dents n_dents du stator et le nombre de pôles n_pôles du rotor est de 3/2 ou qui vérifie la relation $\frac{n_{\mathit{dents}}}{n_{\mathit{pôles}}}=\frac{6n}{6n-2},$
  
  avec n entier supérieur ou égal à 2, par exemple égal à 2 ou 3, et
• entre $\frac{50°}{n_{\mathit{dents}}}$
  
  et $\frac{70°}{n_{\mathit{dents}}},$
  
  étant par exemple de $\frac{60°}{n_{\mathit{dents}}}$
  
  environ, pour une machine qui vérifie la relation $\frac{n_{\mathit{dents}}}{n_{\mathit{pôles}}}=\frac{6n}{6n+2},$
  
  avec n entier supérieur ou égal à 2, par exemple égale à 2 ou 3.

Each convex portion 24 has circumferential ends 25 angularly offset from the permanent magnets 21 adjacent. The angular offset β of the circumferential ends 25 with respect to the permanent magnets 21 adjacent can be understood:

• enter $\frac{80°}{{\mathrm{not}}_{\mathit{teeth}}}$
  
  and $\frac{100°}{{\mathrm{not}}_{\mathit{teeth}}},$
  
  being for example of $\frac{90°}{{\mathrm{not}}_{\mathit{teeth}}}$
  
  approximately, for a machine whose ratio between the number of teeth n _teeth of the stator and the number of poles n _poles of the rotor is 3/2 or which verifies the relation $\frac{{\mathrm{not}}_{\mathit{teeth}}}{{\mathrm{not}}_{\mathit{poles}}}=\frac{6\mathrm{not}}{6\mathrm{not}-2},$
  
  with n integer greater than or equal to 2, for example equal to 2 or 3, and
• enter $\frac{50°}{{\mathrm{not}}_{\mathit{teeth}}}$
  
  and $\frac{70°}{{\mathrm{not}}_{\mathit{teeth}}},$
  
  being for example of $\frac{60°}{{\mathrm{not}}_{\mathit{teeth}}}$
  
  about, for a machine that checks the relationship $\frac{{\mathrm{not}}_{\mathit{teeth}}}{{\mathrm{not}}_{\mathit{poles}}}=\frac{6\mathrm{not}}{6\mathrm{not}+2},$
  
  with n integer greater than or equal to 2, for example equal to 2 or 3.

In these relations, n _teeth denotes the number of teeth 11 of the stator and n _poles the number of pole pieces 27.

The permanent magnets 21 are located radially recessed from the circumferential ends 25 of the convex portions 24. The retraction r in the radial direction of the magnets 21 with respect to the circumferential ends 25 of the convex portions 24 can be between 10% and 20%, or even About 15% of the inner radius R of the stator.

Each pole piece 22 further comprises two shoulders 26 located on either side of the projecting portion 27, each permanent magnet 21 being located between two shoulders 26.

The protruding portions 27 of each of the pole pieces 22 of the rotor have radial edges 28 which, like the circumferential ends 25, are angularly offset from the radially directed faces 29 of the adjacent permanent magnets 21.

The permanent magnets 21 have, when the machine is observed along the axis of rotation X, a cross section of elongated shape in a radial direction. This cross section is, in the example described, rectangular, of large side oriented parallel to a radius of the machine. Alternatively, the permanent magnets could each have a wedge shape.

In the example considered, the rotor comprises ten poles and the stator twelve teeth, the stator thus having 6n teeth and the rotor 6n ± 2 poles, n being equal to 2. It is not beyond the scope of the present invention if n is greater than 2.

In the example described, the rotor is internal, but it is not beyond the scope of the present invention if the rotor is external, or if the machine comprises both an inner rotor and an outer rotor, each arranged radially on each side. other of the stator and coupled in rotation. The motor advantageously satisfies, in accordance with the invention, the relation X _d > X _q .

Control device

The machine which has just been described with reference to the figure 1 can be controlled by a control device allowing its operation at constant power over a wide range of rotational speeds of the rotor, as will be described with reference to the figures 2 and 3 . This control device is particularly suitable for a machine for which X _d > X _q .

par rapport à l'axe direct d. Les grandeurs sinusoïdales peuvent y être représentées par des vecteurs fixes.For the sake of clarity, we have shown on the figure 2 a well-known reference linked to the electric pulsation ω, comprising a direct axis d having the same direction and the same direction as the inducing flux φ, or main flux, which passes through a phase of the armature, and a quadrature axis q offset from an angle of $+\frac{\mathrm{<figure-callout\; id="2"\; label="\pi "\; filenames="imgf0001.png"\; state="\{\{state\}\}">\pi </figure-callout>}}{2}$

in relation to the direct axis d. Sinusoidal quantities can be represented by fixed vectors.

In what follows, we use the unit values e, x _d and x _q defined above.

The offset of the unit current i with respect to the unit electromotive force e is chosen to maintain the constant voltage at speeds higher than the base speed since the unit component i _d of i in the direct axis d will create a flow that goes to oppose the main flow, the total magnetomotive force being thus reduced and consequently causing a fall in the induced unit voltage v, without unduly motor torque, the control device being arranged to allow the machine to operate with the greatest possible torque beyond the base speed. In particular, the control device aims to allow operation with a power beyond the base speed substantially equal to the power at the base speed.

The synchronous motor 1 is powered by a three-phase current from an inverter 35 comprising six electronic switches 60, for example one or more IGBTs, each associated with a diode 61, and controlled by six control signals 62 coming from a vector controller 37.

The latter makes it possible to correct the intensity of the current supplied to the motor as a function of direct intensity orders i _d and in quadrature i _q that it receives from a main computer 45, the measured intensities i _a and i _b for two of the three phases, and angular position information θ.

The angular position information θ is transmitted by a position calculator 40 connected to a position sensor 39.

The position sensor 39 is also connected to a speed calculator 41.

The value of the rotation speed Ω calculated by the speed calculator 41 is transmitted to the main computer 45, to a multiplier 46 and to a subtractor 47.

The rotation speed Ω is subtracted from a rotation speed reference of the rotor Ω * in the subtractor 47, then the difference Ω * -Ω is processed by a regulation circuit 48 of the PID type (proportional-integral-derivative) and transmitted to a torque calculator 49 which determines a torque setpoint t * as a function of the difference between the measured rotational speed Ω and the rotational speed reference of the rotor Ω *. The torque setpoint t * is capped at the maximum torque t _max that the machine is able to supply.

The torque setpoint t * is transmitted to the multiplier 46 which, as a function of the measured rotation speed Ω of the rotor, calculates a power setpoint p *.

This power setpoint p * is transmitted to the main computer 45.

Furthermore, the voltage V _DC across the inverter 35 is measured and transmitted to the main computer 45 by a control circuit 50 of the PID type to smooth any variations. This control circuit 50 provides a unit voltage v which can vary, being dependent on the voltage of the network.

The main computer 45 determines from the data it receives direct currents i _d and quadrature i _q corresponding to the power operation p *.

These values i _d and i _q are transmitted to the vector controller 37 and enable it to control, as described previously, the inverter 35.

The main computer 45 can determine the values i _d and i _q by accessing a register 53 containing precalculated values, as illustrated in FIG. figure 4 . This register 53 groups the values of i _d and i _q for a large number of inputs v, p * and Ω. For values v, p * and Ω, the calculator determines the values of v, p * and Ω nearest for which we know, in the register, 53 i _d (v, p *, Ω) and i _q (v , p *, Ω).

$$\mathrm{\alpha }\mathrm{=}\mathrm{arctg}\left(\frac{{\mathrm{x}}_{\mathrm{q}}}{{\mathrm{x}}_{\mathrm{d}}}\frac{\left(\mathrm{e}\mathrm{-}\mathrm{y}\right)}{\mathrm{x}}\right)\mathrm{,}$$

$$\mathrm{i}=\sqrt{{\left(\frac{x}{x_q}\right)}^2+{\left(\frac{e-y}{x_d}\right)}^2},$$

(x, y) étant l'une des racines réelles des équations $${\mathrm{x}}^{\mathrm{2}}\mathrm{+}{\mathrm{y}}^{\mathrm{2}}=\frac{{\mathrm{v}}^{\mathrm{2}}}{{\mathrm{m}}^{\mathrm{2}}}\mathrm{et\; y}=\mathrm{e}\left(1-\frac{x_d}{x_d-x_q}\right)+\frac{p}{m}e\frac{x_d{x}_q}{x_d-x_q}\frac{1}{x}\mathrm{.}$$

The main computer 45 can further determine i _d and i _q analytically, by a real-time calculation, using the following formulas: $${\mathrm{i}}_{\mathrm{d}}\mathrm{=}\mathrm{-}\mathrm{i\; sin\alpha \; and}{\mathrm{i}}_{\mathrm{q}}\mathrm{=}\mathrm{i\; cos\alpha }\mathrm{,}$$

$$\mathrm{\alpha }\mathrm{=}\arctan \left(\frac{{\mathrm{x}}_{\mathrm{q}}}{{\mathrm{x}}_{\mathrm{d}}}\frac{\left(\mathrm{e}\mathrm{-}\mathrm{there}\right)}{\mathrm{x}}\right)\mathrm{,}$$

$$\mathrm{i}=\sqrt{{\left(\frac{\mathrm{<figure-callout\; id="2"\; label="x\; x\; q"\; filenames="imgf0001.png"\; state="\{\{state\}\}">x\; </figure-callout>}}{x_q}\right)}^2+{\left(\frac{e-\mathrm{there}}{{\mathrm{<figure-callout\; id="2"\; label="x\; d"\; filenames="imgf0001.png"\; state="\{\{state\}\}">x\; </figure-callout>}}_d}\right)}^2},$$

(x, y) being one of the real roots of the equations $${\mathrm{x}}^{\mathrm{2}}\mathrm{+}{\mathrm{there}}^{\mathrm{2}}=\frac{{\mathrm{v}}^{\mathrm{2}}}{{\mathrm{<figure-callout\; id="2"\; label="m"\; filenames="imgf0001.png"\; state="\{\{state\}\}">m</figure-callout>}}^{\mathrm{2}}}\mathrm{and\; there}=\mathrm{e}\left(1-\frac{x_d}{x_d-x_q}\right)+\frac{p}{m}e\frac{x_d{x}_q}{x_d-x_q}\frac{1}{x}\mathrm{.}$$

The terms "calculator", "register", "regulating circuit", "subtractor" and "multiplier" must be understood in a broad sense. All these functions can be performed by one or more specific electronic circuits housed on one or more electronic cards. These functions can be realized in hardware and / or software. In particular, the elements 40, 41, 47, 48, 49, 46, 45, 50 and 37 can be integrated in the same electronic card comprising one or more micro-controllers and / or micro-processors.

In the example considered, the defluxing ratio is 6, that is to say that the maximum rotational speed of the rotor is six times the base speed, for example about 1350 revolutions per minute.

It is of course not departing from the scope of the present invention if the defluxing ratio is different from 6, in particular is greater than or equal to 2 for example. The electronic switches 60 of the inverter 35 are then sized accordingly.

Of course, the invention is not limited to the embodiment which has just been described. For example, the electric machine can be made differently while having X _d > X _q .

Throughout the description, the phrase "having one" should be considered synonymous with "having at least one", unless the opposite is specified.

Claims (15)

Set comprising: a synchronous electric machine comprising: a stator (10), and at least one rotor (20) with permanent magnets (21), the machine being arranged to have X _d > X _q , where X _d is the direct reactance and X _q the quadrature reactance, this machine constituting a synchronous motor, and a control device for a synchronous motor enabling operation of the motor at a substantially constant power P _o over a range of rotational speeds of the rotor, comprising a computer (45) arranged to determine the values of direct currents I _d and quadrature I _q of the motor supply current, the intensities I _d and I _q being equal, within 20%, better within 10%, better still within 5%, to: $${\mathrm{I}}_{\mathrm{d}}\mathrm{\cong }{\mathrm{i}}_{\mathrm{d}}\mathrm{.}{\mathrm{I}}_{\mathrm{o}}\mathrm{\cong }\mathrm{-}\mathrm{i\; sin\; \alpha }\mathrm{.}{\mathrm{I}}_{\mathrm{o}}\mathrm{and}{\mathrm{I}}_{\mathrm{q}}\mathrm{\cong }{\mathrm{i}}_{\mathrm{q}}\mathrm{.}{\mathrm{I}}_{\mathrm{o}}\mathrm{\cong }\mathrm{i\; cos\; \alpha }\mathrm{.}{\mathrm{I}}_{\mathrm{o}}\mathrm{,}$$

where I _o is the maximum intensity of the current imposed by the size of the control device, $$\mathrm{\alpha }=\arctan \left(\frac{x_q}{x_d}\frac{\left(e-\mathrm{there}\right)}{x}\right),$$

$$\mathrm{i}=\sqrt{{\left(\frac{x}{x_q}\right)}^2+{\left(\frac{e-\mathrm{there}}{x_d}\right)}^2},$$

the unitary current circulating in a phase of
the armature,
(x, y) being one of the real roots of the equations $${\mathrm{x}}^{\mathrm{2}}\mathrm{+}{\mathrm{there}}^{\mathrm{2}}=\frac{{\mathrm{v}}^{\mathrm{2}}}{{\mathrm{m}}^{\mathrm{2}}}\mathrm{and\; there}=\mathrm{e}\left(1-\frac{x_d}{x_d-x_q}\right)+\frac{p}{m}e\frac{x_d{x}_q}{x_d-x_q}\frac{1}{x},$$

m denotes the ratio between the rotational speed of the rotor and the base speed,
e is the ratio between, on the one hand, the electromotive force, and, on the other hand, the product of m by the voltage V _o imposed by the supply network,
v is the ratio between the voltage at the terminals of a phase of the armature and the maximum voltage per phase V _o imposed by the supply network,
p is the ratio between the effective power and the power P _o ,
α the phase difference between the intensity and the electromotive force,
x _d the quotient $\frac{{\mathrm{X}}_{\mathrm{d}}{\mathrm{I}}_{\mathrm{o}}}{\mathrm{m}{\mathrm{V}}_{\mathrm{o}}},$

X _d being the direct reactance, and
x _q the quotient $\frac{{\mathrm{X}}_{\mathrm{q}}{\mathrm{I}}_{\mathrm{o}}}{\mathrm{m}{\mathrm{V}}_{\mathrm{o}}}\mathrm{,}$

where X _q is the quadrature reactance. Assembly according to the preceding claim, characterized in that the root (x, y) chosen is that which minimizes i. Assembly according to any one of the two preceding claims, characterized in that it comprises: - a three-phase inverter (35), a vector controller (37) arranged to transmit, as a function of the intensities i _d and i _q, control signals to electronic switches (60) of the inverter (35). Assembly according to any one of the preceding claims, characterized in that the rotor (20) is at flux concentration, the permanent magnets (21) of the rotor being arranged between pole pieces (22), the pole pieces (22) each rotor having a face facing the stator (10) which has a convex portion (24), the convex portion (24) of a pole piece (22) having in particular a radius of curvature of between 20% and 30% the inner radius (R) of the stator. Assembly according to the preceding claim, characterized in that the circumferential ends (25) of the convex portion (24) of a pole piece (22) are angularly offset relative to the permanent magnets (21) adjacent to this pole piece (22). ), the angular offset β of the circumferential ends (25) relative to the adjacent permanent magnets (21) being notably comprised: - enter $\frac{80°}{{\mathrm{not}}_{\mathit{teeth}}}$

and $\frac{100°}{{\mathrm{not}}_{\mathit{teeth}}},$

being especially of $\frac{90°}{{\mathrm{not}}_{\mathit{teeth}}}$

approximately, for a machine whose ratio between the number of teeth n _teeth of the stator and the number of poles n _poles of the rotor is 3/2 or which verifies the relation $\frac{{\mathrm{not}}_{\mathit{teeth}}}{{\mathrm{not}}_{\mathit{poles}}}=\frac{6\mathrm{not}}{6\mathrm{not}-2},$

with n integer greater than or equal to 2, and - enter $\frac{50°}{{\mathrm{not}}_{\mathit{teeth}}}$

and $\frac{70°}{{\mathrm{not}}_{\mathit{teeth}}},$

being especially of $\frac{60°}{{\mathrm{not}}_{\mathit{teeth}}}$

about, for a machine that checks the relationship $\frac{{\mathrm{not}}_{\mathit{teeth}}}{{\mathrm{not}}_{\mathit{poles}}}=\frac{6\mathrm{not}}{6\mathrm{not}+2},$

with n integer greater than or equal to 2. Assembly according to any one of claims 4 to 5, characterized in that each of the permanent magnets (21) of the rotor (20) is radially recessed from the circumferential ends of the convex portions (24) of the two adjacent pole pieces (22). ), the withdrawal (r) in the radial direction of the magnets (21) relative to the circumferential ends (25) of the convex portions (24) being in particular between 10% and 20% of the inner radius (R) of the stator (10) . Assembly according to any one of claims 4 to 6, characterized in that each of the pole pieces (22) of the rotor (20) comprises two shoulders (26), at least one permanent magnet (21) lying between the shoulders of two adjacent pole pieces (22). Assembly according to any one of claims 4 to 7, characterized in that each of the pole pieces (22) of the rotor (20) has a projecting portion (27) extending towards the stator (10), having edges radial members (28) which are angularly offset from radially directed edges (29) of permanent magnets (21) adjacent to the pole piece (22). Assembly according to any one of the preceding claims, characterized in that the permanent magnets (21) have, when the machine is observed along the axis (X) of rotation of the rotor, an elongated cross section of longitudinal axis extending in a radial direction. Assembly according to any one of the preceding claims, characterized in that the permanent magnets (21) of the rotor (20) have, when the machine is observed along the axis (X) of rotation of the rotor, a rectangular cross section of large side oriented parallel to a radius of the machine. Assembly according to any one of the preceding claims, characterized in that the stator (10) comprises 6n teeth (11) and the rotor (20) 6n ± 2 poles (22), n being greater than or equal to 2. A method of controlling an engine of an assembly as defined in claim 1, wherein: at least the supply voltage (V _DC ) of an inverter connected to the motor and the speed of rotation (Ω) of the motor are measured, and a calculation is carried out in real time and / or by access to a register on the basis of at least the voltage V _DC and the measured speed of the direct currents i _d and in quadrature i _q of the supply current making it possible to maintain the Constant power for a speed reference (Ω *) given above the base speed. Method according to the preceding claim, characterized in that a torque setpoint t * is determined as a function of at least the difference between the measured rotational speed (Ω) and the rotational speed reference of the rotor (Ω * ). Method according to the preceding claim, characterized in that a power setpoint (p *) is determined as a function of at least the torque setpoint and the measured rotational speed. Method according to the preceding claim, characterized in that the direct intensities i _d and in quadrature i _q are calculated in real time from the power setpoint, the measured rotation speed and the DC supply voltage. of the inverter.

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