EP1851927B1 - Iq-modulator-vorverzerrung - Google Patents

Iq-modulator-vorverzerrung Download PDF

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Publication number
EP1851927B1
EP1851927B1 EP05711126.2A EP05711126A EP1851927B1 EP 1851927 B1 EP1851927 B1 EP 1851927B1 EP 05711126 A EP05711126 A EP 05711126A EP 1851927 B1 EP1851927 B1 EP 1851927B1
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Prior art keywords
modulator
distorter
signal
compensate
filter
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EP05711126.2A
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English (en)
French (fr)
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EP1851927A1 (de
Inventor
Spendim Dalipi
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Telefonaktiebolaget LM Ericsson AB
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Telefonaktiebolaget LM Ericsson AB
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    • HELECTRICITY
    • H03ELECTRONIC CIRCUITRY
    • H03FAMPLIFIERS
    • H03F1/00Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/32Modifications of amplifiers to reduce non-linear distortion
    • H03F1/3241Modifications of amplifiers to reduce non-linear distortion using predistortion circuits
    • H03F1/3294Acting on the real and imaginary components of the input signal
    • HELECTRICITY
    • H03ELECTRONIC CIRCUITRY
    • H03FAMPLIFIERS
    • H03F1/00Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/32Modifications of amplifiers to reduce non-linear distortion
    • H03F1/3241Modifications of amplifiers to reduce non-linear distortion using predistortion circuits
    • H03F1/3247Modifications of amplifiers to reduce non-linear distortion using predistortion circuits using feedback acting on predistortion circuits
    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00Modulated-carrier systems
    • H04L27/32Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/36Modulator circuits; Transmitter circuits
    • H04L27/362Modulation using more than one carrier, e.g. with quadrature carriers, separately amplitude modulated
    • H04L27/364Arrangements for overcoming imperfections in the modulator, e.g. quadrature error or unbalanced I and Q levels
    • HELECTRICITY
    • H03ELECTRONIC CIRCUITRY
    • H03FAMPLIFIERS
    • H03F2200/00Indexing scheme relating to amplifiers
    • H03F2200/57Separate feedback of real and complex signals being present

Definitions

  • a direct- IQ radio architecture comprises base band data modification, digital-to-analog conversion (DAC), and analog IQ -quadrature modulation to finally bring a complex I +j Q signal to radio frequency (RF).
  • the IQ -modulator exhibits a DC-component, an amplitude error and also a phase error. Both of the branches ( I and Q ) of the IQ -modulator suffer from this imbalance.
  • the analog IQ -modulator is foreseen to be driven by a higher input power.
  • the mixer parts of the IQ -modulator tend to become inherently non-linear on top of the linear amplitude and phase imbalance.
  • Document WO 99/66637 discloses a circuit for compensating for imperfections in amplification chains. This documents shows in Fig. 10B how the different imperfections between the two branches are mitigated by multiplying input signals I(t) and Q(t) with corresponding coefficients. Furthermore, the LMS algorithm is mentioned in page 28, line 8 and lines 21-27 and equation 10 as a known way of updating FIR filter coefficients with regard to Fig. 16.
  • An object of the present invention is a base station including an IQ -modulator pre-distorter for compensating for these errors.
  • Fig. 1 is a block diagram of an analog IQ -modulator.
  • the IQ -modulator includes a local oscillator 10, the output signal of which multiplies the I- component of a signal that is to be transformed to RF in a mixer 12.
  • the output signal from local oscillator 10 is also forwarded to a 90° phase shifter 14 and then to a second mixer 16 for transforming the Q -component of the input signal to RF.
  • the transformed signals from mixers 12, 16 are then combined in an adder 18 to form the desired RF-signal.
  • the two local oscillator signals are phase shifted 90°, the two components can be regarded as being "orthogonal". If, however, there is an error in the phases of the mixing signals from the local oscillator and also a gain difference, then the I - and Q -branches are not orthogonal any longer. This will lead to leakage between the branches.
  • each branch has non-linear effects. It is believed that these come from phase-modulation of the mixing signals from the local oscillator.
  • Fig. 2 is a simple example model of an IQ -modulator illustrating various possible error sources.
  • the I -component is amplified by a gain A , combined with a DC offset DCA and multiplied by a mixer signal cos( ⁇ ⁇ t + ⁇ A + k ⁇ I ( t )) to produce the transformed or up-converted RF-signal I RF .
  • the up-conversion of the Q -component is modeled in a similar way.
  • the IQ -modulator is seen as having two input ports that each have their own non-linearity. As there are two separate branches, it is necessary to have two separate non-linear compensators for this.
  • the local oscillator signals each have a phase modulation, which gives frequency inter-modulation on the I- and Q -signals (the phase offsets that include the k and c factors).
  • the IQ -modulator errors can be counteracted by digitally pre-distorting the IQ -signal at base band using iteratively updated filter structures in which the filter taps depend on the values of the I- and Q-components.
  • equation (3) represents filter taps gIQ, gQ q for filtering the I- and Q-components to compensate for amplitude errors generated by the IQ- modulator without regard to the inter-modulation error.
  • the inter-modulation is handled by the filter taps cIQ q , cQI q in equation (4), and offset errors are handled by dcI, dcQ in equation (5).
  • x k and y k represent the IQ -modulator pre-distorter input signal (reference signal) and a down-converted IQ -modulator output signal, respectively. These signals will be further illustrated in Fig. 4 . It is noted that these signals are regarded as complex, i.e. they have a real part and an imaginary part (corresponding to the I - and Q-components).
  • the x k and y k signals are also assumed to be time synchronized and phase-locked.
  • q is an index representing a delay d(q)
  • the various ⁇ :s are loop constants b identifies a filter tap bin
  • i is an iteration index
  • N is the number of input samples of reference signal x in a sample batch that have an amplitude that falls within a window M b around the center amplitude of bin b
  • M K represent the number of filter taps +1.
  • Fig. 3 is a block diagram of a first embodiment of an IQ -modulator pre-distorter in accordance with the present invention based on equations (3)-(5).
  • the I -component is multiplied by filter tap gI 0 , the value of which depends on the value of the I -component itself.
  • the I- component is also forwarded to a delay element D, and the delayed signal is multiplied by filter tap gI 1 , the value of which depends on the value of the delayed I -component itself.
  • the multiplied signals are then added.
  • the I- component is processed in a similar way by filter taps gIQ 0 , gIQ 1 .
  • the resulting signal is not maintained in the I -branch. Instead it is cross-coupled over to the Q -branch, where it is added to the Q -component after the latter has been filtered by filter taps gQ 0 , gQ 1 .
  • a cross-coupled signal from the Q -branch is added to the filtered I -component.
  • the off-sets dcI, dcQ are added to the I - and Q -branch, respectively.
  • Fig. 4 is a block diagram of a first embodiment of a base station including an IQ -modulator pre-distorter in accordance with the present invention.
  • An IQ -modulator pre-distorter 20 is connected to a DAC 22 (Digital-to-Analog Converter).
  • the analog pre-distorted IQ -vector is forwarded to an IQ -modulator 24, and the up-converted RF-signal is amplified by a power amplifier 26 for transmission by an antenna.
  • the output of IQ -modulator 24 is also connected to a mixer 28, which down-converts the RF-signal to IF (Intermediate Frequency).
  • the IF-signal is digitized in an ADC 30 (Analog-to-Digital Converter).
  • the digitized IF-signal is further down-converted and transformed into an IQ -signal by a digital IQ -demodulator 32.
  • IQ -demodulator 32 is connected to a pre-distorter trainer 34 for determining the actual pre-distortion.
  • the complex input signals x k and y k to trainer 34 have been indicated in Fig. 4 .
  • trainer 34 forwards the filter taps to pre-distorter 20.
  • the filter taps may be updated every sample period or at more spaced time intervals. The updating of the filter taps has been indicated by the unconnected arrows on the taps in Fig. 3 .
  • a power amplifier 26 there is a power amplifier 26. Since a power amplifier also is a non-ideal component, it is desirable to compensate for errors generated by the amplifier by including a power amplifier pre-distorter. Any suitable power amplifier pre-distorter may be used for this purpose. However, such a pre-distorter may also be based on iterative methods, such as LMS algorithms.
  • Fig. 5 is a block diagram of an embodiment of a power amplifier pre-distorter suitable for use in a second embodiment of a base station in accordance with the present invention.
  • This power amplifier pre-distorter is based on filter taps determined, for example, in accordance with equation (6).
  • the filter includes 3 filter taps.
  • are delayed and the delayed signal is multiplied by filter tap T 1 , the valued of which is determined by the delayed amplitude. After a further delay another multiplication is performed by T 1 . Thereafter the multiplied signals are added to each other to form a signal z that is pre-distorted to counteract errors generated by a power amplifier.
  • the updating of the filter taps has been indicated by the unconnected arrows on the taps in Fig
  • Fig. 6 is a block diagram of a second embodiment of a base station including an IQ -modulator pre-distorter in accordance with the present invention.
  • This embodiment integrates IQ- modulator pre-distorter 20 with a power amplifier pre-distorter 36 in the same control loop.
  • Power amplifier pre-distorter may, for example, be implemented as in Fig. 5 . It is noted that in this case the RF-signal that is down-converted to trainer 34 is taken from the power amplifier output instead of the IQ -modulator output. Furthermore, trainer 34 now updates both pre-distorters.
  • trainer 34 may update the various filter taps in accordance with equations (3)-(6).
  • one of the gain parameters ( gI or gQ ) and one of cross coupling parameters ( cIQ or cQI ) may be set to constants. This divides the responsibility between the power amplifier pre-distorter and the IQ -modulator pre-distorter.
  • the IQ compensation becomes a slave and is only compensating the error in the difference between I -signal and Q -signal.
  • the power amplifier pre-distorter will have the main responsibility for gain, phase and linearization compensation.
  • Fig. 7 is a block diagram of a second embodiment of an IQ- modulator pre-distorter in accordance with the present invention based on the comments in the previous paragraph. This simplified embodiment can be used in the base station in Fig. 6 instead of the embodiment of Fig. 3 .
  • Fig. 7 For the IQ -modulator pre-distorter in Fig.
  • Fig. 8 is a block diagram of a third embodiment of an IQ -modulator pre-distorter in accordance with the present invention. This embodiment differs from the embodiment in Fig. 7 by having a cross-connected digital filter from the I -branch to the Q -branch instead of from the Q -branch to the I -branch.
  • the IQ -modulator pre-distorter in accordance with the present invention may be implemented as an FPGA (Field Programmable Gate Array) or ASIC (Application Specific Integrated Circuit). Another possibility is to use a micro processor or a micro/signal processor combination and corresponding software.
  • FPGA Field Programmable Gate Array
  • ASIC Application Specific Integrated Circuit
  • the filters can also be made symmetric with both positive and negative delays.

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  • Engineering & Computer Science (AREA)
  • Physics & Mathematics (AREA)
  • Nonlinear Science (AREA)
  • Power Engineering (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
  • Transmitters (AREA)
  • Amplifiers (AREA)

Claims (2)

  1. Basisstation mit einem Vorverzerrer für einen IQ-Modulator, wobei der Vorverzerrer für den IQ-Modulator einschließt:
    einen iterativ aktualisierten digitalen Filter, um einen der Zweige eines IQ-Signals zu filtern, um durch den IQ-Modulator erzeugte Amplitudenfehler zu kompensieren;
    einen iterativ aktualisierten digitalen Filter, der von einem der Zweige zu dem anderen Zweig quer verbunden ist, um eine der Komponenten eines IQ-Signals zu filtern, um die durch den IQ-Modulator erzeugte Intermodulation zwischen den Zweigen zu kompensieren; und
    iterativ aktualisiert Versatzkompensatoren, um durch den IQ-Modulator erzeugte Versatzfehler zu kompensieren, wobei
    die iterativ aktualisierten Filter so konfiguriert sind, dass sie gemäß einem Algorithmus der kleinsten, mittleren Quadrate aktualisiert werden, dadurch gekennzeichnet, dass der Vorverzerrer für den IQ-Modulator in einem Vorverzerrer für einen Leistungsverstärker in einer gleichen Steuerschleife integriert ist, und dass die Basisstation außerdem einen Trainer, der eingerichtet ist, die iterativ aktualisierten Filter zu aktualisieren, und Versatzkompensatoren gemäß dem folgenden Algorithmus der kleinsten, mittleren Quadrate umfasst: { g I q , i + 1 b = g I q , i b + μ g I b 1 N l k - d q M b N Re x k - d q Re x k - Re y k g Q q , i + 1 b = g Q q , i b + μ g Q b 1 N l k - d q M b N Im x k - d q Im x k - Im y k q = 0 , , M
    Figure imgb0015
    { c I Q q , i + 1 b = c I Q q , i b + μ c I Q b 1 N l k - d q M b N Im x k - d q Re x k - Re y k c Q I q , i + 1 b = c Q I q , i b + μ c Q I b 1 N l k - d q M b N Re x k - d q Im x k - Im y k q = 0 , , K
    Figure imgb0016
    { d c I i + 1 = d c I i + μ d c 1 N k = 1 N Re x k - Re y k d c Q i + 1 = d c Q i + μ d c 1 N k = 1 N Im x k - Im y k ,
    Figure imgb0017
    wobei a) die Filterabgriffe gIQ, gQq zum Filtern der I- und Q-Komponenten darstellt, um Amplitudenfehler zu kompensieren, die von dem IQ-Modulator ohne Berücksichtigung eines Intermodulationsfehlers erzeugt wurden;
    wobei die Intermodulation durch Filterabgriffe cIQq, cQIq in b) gehandhabt wird, und wobei Versatzfehler durch dcl, dcQ in c) gehandhabt werden;
    wobei xk und yk ein Eingabesignal des Vorverzerrers für den IQ-Modulator bzw. ein abwärts-konvertiertes Ausgangssignal des IQ-Modulators darstellen, und wobei q ein Index ist, der eine Verzögerung d(q) darstellt, wobei verschiedene µ Schleifenkonstanten sind, b einen Filterabgriffbehälter identifiziert, i ein Iterationsindex ist, N die Anzahl der Eingabestichproben eines Referenzsignals x in einer Stichprobenmenge ist, die eine Amplitude haben, die innerhalb eines Intervalls Mb um eine zentrale Amplitude eines Filterabgriffbehälters b abfällt, und wobei M, K eine Anzahl von Filterabgriffen + 1 darstellen,
    wobei das Ausgabesignal z von einem Leistungsverstärker anstelle eines Eingabesignals x verwendet wird, um zu bestimmen, ob ein Abtastwert in dem Intervall Mb eingeschlossen ist, und wobei das Eingabesignal x immer noch in der aktuellen Summierung verwendet wird.
  2. Basisstation nach Anspruch 1, wobei der Vorverzerrer für den IQ-Modulator zwei iterativ aktualisierte, digitale Filter (gQ0, gQ1, gI0, gI1), um jeden Zweig des IQ-Signals zu filtern, um durch den IQ-Modulator erzeugte Amplitudenfehler in jedem Zweig zu kompensieren, und zwei iterativ aktualisierte, digitale Filter (cQI0, cQI1, cIQ0, gIQ1) einschließt, die von einem entsprechenden Zweig zu dem anderen Zweig quer verbunden sind, um beide IQ-Signalkomponenten zu filtern, um eine durch den IQ-Modulator erzeugte Intermodulation zwischen den Zweigen zu kompensieren.
EP05711126.2A 2005-02-24 2005-02-24 Iq-modulator-vorverzerrung Not-in-force EP1851927B1 (de)

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PCT/SE2005/000266 WO2006091130A1 (en) 2005-02-24 2005-02-24 Iq-modulator pre-distortion

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EP1851927B1 true EP1851927B1 (de) 2015-12-09

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JP2008532381A (ja) 2008-08-14
EP1851927A1 (de) 2007-11-07
CA2593829A1 (en) 2006-08-31
US8068557B2 (en) 2011-11-29
WO2006091130A1 (en) 2006-08-31
CN101129040A (zh) 2008-02-20
JP4653183B2 (ja) 2011-03-16
US20080253477A1 (en) 2008-10-16
CN101129040B (zh) 2013-02-06

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