EP1648197B2 - Procédé et dispositif pour réduire les rétroactions dans un système acoustique - Google Patents

Procédé et dispositif pour réduire les rétroactions dans un système acoustique Download PDF

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Publication number
EP1648197B2
EP1648197B2 EP05109366.4A EP05109366A EP1648197B2 EP 1648197 B2 EP1648197 B2 EP 1648197B2 EP 05109366 A EP05109366 A EP 05109366A EP 1648197 B2 EP1648197 B2 EP 1648197B2
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EP
European Patent Office
Prior art keywords
signal
feedback
feedback signal
detected
output signal
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Not-in-force
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EP05109366.4A
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German (de)
English (en)
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EP1648197A3 (fr
EP1648197B1 (fr
EP1648197A2 (fr
Inventor
Volkmar Hamacher
Ulrich Dr. Kornagel
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Sivantos GmbH
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Siemens Audioligische Technik GmbH
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04R—LOUDSPEAKERS, MICROPHONES, GRAMOPHONE PICK-UPS OR LIKE ACOUSTIC ELECTROMECHANICAL TRANSDUCERS; DEAF-AID SETS; PUBLIC ADDRESS SYSTEMS
    • H04R25/00—Deaf-aid sets, i.e. electro-acoustic or electro-mechanical hearing aids; Electric tinnitus maskers providing an auditory perception
    • H04R25/45—Prevention of acoustic reaction, i.e. acoustic oscillatory feedback
    • H04R25/453—Prevention of acoustic reaction, i.e. acoustic oscillatory feedback electronically
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04R—LOUDSPEAKERS, MICROPHONES, GRAMOPHONE PICK-UPS OR LIKE ACOUSTIC ELECTROMECHANICAL TRANSDUCERS; DEAF-AID SETS; PUBLIC ADDRESS SYSTEMS
    • H04R3/00—Circuits for transducers, loudspeakers or microphones
    • H04R3/02—Circuits for transducers, loudspeakers or microphones for preventing acoustic reaction, i.e. acoustic oscillatory feedback
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04R—LOUDSPEAKERS, MICROPHONES, GRAMOPHONE PICK-UPS OR LIKE ACOUSTIC ELECTROMECHANICAL TRANSDUCERS; DEAF-AID SETS; PUBLIC ADDRESS SYSTEMS
    • H04R2430/00—Signal processing covered by H04R, not provided for in its groups
    • H04R2430/03—Synergistic effects of band splitting and sub-band processing

Definitions

  • the present invention relates to a method of reducing feedback in an acoustic system by detecting a feedback signal in an input signal and processing the input signal in response to the detected feedback signal to produce an output signal. Moreover, the present invention relates to a corresponding signal processing device for an acoustic system.
  • the acoustic system is, for example, a mobile radio device, a headset, a public address system and in particular a hearing aid or middle ear implant.
  • Feedback Acoustic feedback, hereafter referred to as feedback, is common in hearing aids, especially when it comes to high gain devices. These feedbacks are expressed in strong oscillations of a certain frequency and can be heard as whistling. This "whistling" is usually very uncomfortable for the hearing aid wearer himself as well as for people in his immediate vicinity. Feedback can be z. B. occur when sound that was recorded on the hearing aid microphone, amplified by a signal amplifier and output via the handset, gets back to the microphone and is reinforced again.
  • the simplest approach to reducing feedback is to permanently reduce hearing instrument gain so that the loop gain remains below the critical limit even in adverse situations.
  • the decisive disadvantage is that this limitation can no longer achieve the reinforcements required for severe deafness.
  • Other approaches see a measurement of loop gain during the hearing aid fitting and reduce with the help of so-called notch filters (narrow-band notch filters) the gain targeted in the critical area.
  • notch filters narrow-band notch filters
  • the second class contains the algorithms that only become active when feedback whistles are present. They generally include a feedback whistle detection mechanism that continuously monitors the microphone signal for feedback oscillation. If feedback-type oscillations are detected, the hearing aid gain at the corresponding point is reduced to such an extent that the loop gain drops below the critical limit.
  • the gain reduction can, for. B. by lowering a frequency channel or by activating a suitable narrow-band notch filter (Notchfilter) done.
  • the disadvantage is that the oscillation detectors in principle do not distinguish between tonal input signals and feedback whistles can. The result is that tonal input signals are held for feedback oscillations and then inadvertently lowered in level by the reduction mechanism (eg, notch filter).
  • Another countermeasure is to slow down the adaptation of the filter so that all relevant environmental tonal signals are not attacked.
  • this also has the consequence that the compensation filter can no longer follow rapid changes in the feedback path quickly, so that feedback whistles develop for a certain time, which only disappears again when the feedback path has stabilized and the filter has again been adapted with sufficient accuracy ,
  • the feedback detector operates on the principle of bandwidth detection. If a narrow bandwidth of the input signal of the hearing device is detected by the bandwidth detector in the frequency band prone to feedback whistles, it is assumed that feedback whistling is present. A distinction of natural, narrow-band signals with spectral components in this frequency band, such. As music, but is not possible. In addition, the feedback whistle must represent a dominant signal component in order to be recognized.
  • Another method for reducing feedback in acoustic systems is from the document US 6,347,148 B1 known.
  • the spectrum of an input signal is estimated and a control signal is generated on the basis of a psychoacoustic model.
  • the control signal is used to drive a noise source, with which a non-audible noise signal in response to the noise signal can be generated.
  • the possibility is described there to impose short noise signals of predetermined duration on the output signal.
  • the noise signals in the input signal reduce feedback signals.
  • the object of the present invention is thus to further improve the reduction of feedback of a hearing aid.
  • this object is achieved by a method according to claim 1 and a signal processing device according to claim 7.
  • the underlying idea is to impose imperceptible features on the output signal of the acoustic system and in particular the hearing aid for the hearing aid wearer. This allows, by appropriate analysis of the input signal too determine whether the input signal is feedback or a "normal" external input signal (useful signal). The determination of the characteristic of the feature in the input signal also allows conclusions to be drawn about the corresponding proportions of feedback and useful signal. This can then be used directly to control feedback reduction algorithms.
  • the processing of the input signal preferably takes place with an adaptable filter whose adaptation speed and / or strength depends on the quantity of the detected feedback signal.
  • adaptation speed increases in proportion to the quantity of the detected feedback signal. If, for example, the feature analysis of the input signal is negative, d. H. it contains no feedback signal, so the adaptation speed of the compensation filter mentioned above can be slowed down so that the filter is not adjusted by tonal input signals and they are not attacked. If, on the other hand, the feature is detected in the input signal, the effectiveness and / or speed of the feedback compensator is set to the value at which feedback is optimally suppressed.
  • At least one notch filter may be activated for processing the input signal.
  • phase modulation shows no particular susceptibility to misdetection in narrowband signals.
  • a feedback situation can already be detected before there is a dominant expression of the feedback whistle in the signal mixture.
  • the detection of feedback can be performed separately in several subbands. As a result, the gain, but also the reduction of feedback in the individual subbands can be adjusted individually.
  • a closed loop in the signal processing device can be used for a signal modification.
  • the modulated signal passes through the loop several times, so that the corresponding signal modification is caused.
  • FIG. 1 the prior art explained in more detail.
  • FIG. 1 shows a hearing aid HG, whose input forms a microphone M.
  • the recorded signal is applied as an input signal ES a processing unit V forwarded. There it is processed and possibly reinforced.
  • the resulting output signal AS is delivered to a handset H. Via a feedback path RP, the output signal of the handset H is fed back to the microphone M.
  • a feedback path RP With open supply, there is primarily an acoustic feedback path. In general, however, electromagnetic, electrical, magnetic and other feedback are also conceivable.
  • the feedback signal RS resulting from the feedback path is added to a useful signal NS, and the sum signal is picked up by the microphone M.
  • the signal path from the microphone M via the hearing aid processing V, the handset H, the feedback path RP back to the microphone M represents a loop.
  • H. the gain experienced by a signal passing through this loop is at least 1.0 at least at one frequency, and when the phase condition is met, feedback whistling occurs. Even if the loop gain is just below this limit, audible feedback effects, e.g. B. sound changes on.
  • One successful method for suppressing the feedback effects is the digital replica of the feedback path RP. This is simulated by an adaptive filter AF, which is fed by the output signal of the processing unit V. A corresponding compensation signal KS, which originates from the compensating, adaptive filter AF, is subtracted from the input signal ES of the microphone M and the resulting difference signal is fed to the processing unit V.
  • step size control An important component in the adaptive algorithm for determining the feedback path is its step size control. It indicates the speed with which the adaptive compensation filter adapts to the outer feedback path RP. Since there is no meaningful compromise for a fixed step size, it must be adapted to the current situation in which the system is located.
  • a large step size for a fast adaptation of the adaptive compensation filter AF to the outer feedback path RP is to be aimed for.
  • a disadvantage of a large step size is the generation of perceptible signal artifacts.
  • the step size should be vanishingly small.
  • the situation in which the loop gain is just below 1 or greater than / equal to 1 and the phase condition is fulfilled at least at one frequency is referred to as the feedback situation.
  • the step size should or will be large. This ensures that the algorithm adapts the adaptive compensation filter AF only if it differs significantly in its characteristic from the characteristic of the feedback path RP, ie. H. if there is a need for post-adaptation.
  • a feedback detector is provided.
  • FIG. 2 between the processing unit V and the handset H is connected. It modulates the output signal AS to a modulated output signal AS '.
  • the modulation of the output signal AS is not perceptible. In the event of a feedback situation, a significant proportion of the sound signal emitted by the receiver H returns to the microphone M and is recorded in the device together with the ambient signal.
  • the feedback path RP can basically be designed arbitrarily. Ie. it does not have an acoustic feedback signal RS, as in FIG. 1 is indicated, present, which is added with an acoustic useful signal NS before the microphone M. Rather, the feedback in the microphone M can also be done for example via structure-borne noise or electromagnetic coupling.
  • the input signal ES of the microphone M is analyzed by a feedback detector RD.
  • the feedback signal RS can be detected due to its modulation.
  • a downstream controller S drives the adaptive compensation filter AF according to the detection result of the feedback detector RD. As a result, for example, the adaptation speed of the adaptive filter AF is changed.
  • FIG. 3 corresponds essentially to that of FIG. 2 ,
  • the feedback path as in the example of FIG. 1 purely acoustic nature, so that the feedback signal is added to the useful signal in front of the microphone M.
  • Another difference to the circuit of FIG. 2 is that the signal for the feedback detector RD is not picked up immediately after the microphone M, but after the subtraction of the compensation signal of the adaptive filter AF at the point A.
  • the strength of the modulation of the signal at the point A is an image of the difference between the effect of the feedback path RP and the effect of the adaptive compensation filter AF.
  • FIG. 3 indicated that in the feedback detector RD a step size control can be integrated, so that can be dispensed with a separate control module.
  • the remaining components of the embodiment of FIG. 3 correspond to those of the embodiment of FIG. 2 , In this respect, therefore, the description to FIG. 2 directed.
  • the phase of the output signal AS is modulated since the human ear is largely insensitive to phase changes.
  • the phase of the output signal AS with a specific frequency referred to here as the modulation frequency f_mod
  • the modulation frequency f_mod is linearly rotated back and forth between two phase values.
  • the phase values are ⁇ and ⁇ + ⁇ / 2, where ⁇ is any solid phase.
  • a detectable tremolo component with a frequency of f_mod is formed in the signal loop.
  • the tremolo component can be detected by means of a frequency demodulator in the feedback detector RD. It is advantageous to construct the feedback detector RD with a filter bank, as in FIG. 4 is shown, the z. B. the input signal ES with multiple bandpasses BP1, BP2, ..., BPn divided into subbands. After each bandpass an analysis unit AE and a threshold value SW is arranged in each case. The output signals of the signal paths for each subband are optionally supplied to an OR gate OR.
  • the respective analysis units AE and threshold SW can be identical to each other. Thus, the analysis in this example is done in each subband path in the same way. If the analysis result in a band exceeds a certain threshold, the associated threshold switch SW responds, ie a feedback situation is detected for this band.
  • the step size control of the adaptive filter AF in addition to the simple threshold decision according to FIG. 4 According to which only the presence or absence of feedback is detected, also differentiated occur.
  • the step size can be determined by proportional conversion of the estimated strength of the signal modulation at point A. This can also be done again via a subband approach. The greater the detected signal modification, the higher would be the need for a post-adaptation, ie the higher the necessary step size would have to be selected.
  • the step size can thus be continuously adapted to the signal modulation. In a pure threshold decision, however, the step size is set high for a certain fixed time or for the time frame in which feedback is detected. Otherwise, it takes on a small value.

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  • Health & Medical Sciences (AREA)
  • General Health & Medical Sciences (AREA)
  • Otolaryngology (AREA)
  • Physics & Mathematics (AREA)
  • Engineering & Computer Science (AREA)
  • Acoustics & Sound (AREA)
  • Signal Processing (AREA)
  • Neurosurgery (AREA)
  • Circuit For Audible Band Transducer (AREA)
  • Amplifiers (AREA)
  • Soundproofing, Sound Blocking, And Sound Damping (AREA)

Claims (12)

  1. Procédé de réduction de réactions dans un système ( HG ) acoustique par
    - détection d'un signal ( RS ) de réaction dans un signal ( ES ) d'entrée,
    - traitement du signal ( ES ) d'entrée en produisant en fonction du signal ( RS ) de réaction détecté un signal ( AS ) de sortie et
    - modulation ( MO ) du signal ( AS ) de sortie par application d'une caractéristique au signal ( AS ) de sortie, de manière à moduler de façon correspondante également le signal ( RS ) de réaction, dans lequel
    - la détection du signal ( RS ) de réaction s'effectue sur la base de la présence de la caractéristique appliquée,
    caractérisé en ce que
    la phase est à cet effet avancée et ramenée d'une fréquence donnée à l'avance entre deux valeurs de phase.
  2. Procédé suivant la revendication 1, dans lequel le traitement du signal ( ES ) d'entrée s'effectue par un filtre ( AF ) adaptable dont la vitesse d'adaptation et/ou l'intensité d'action dépend de la quantité du signal ( RS ) de réaction détecté.
  3. Procédé suivant la revendication 2, dans lequel la vitesse d'adaptation et/ou l'intensité d'action augmente proportionnellement avec la quantité du signal ( RS ) de réaction détecté.
  4. Procédé suivant l'une des revendications précédentes, dans lequel, dans le cas de la détection d'un signal de réaction, au moins un filtre coupe-bande est activé pour le traitement du signal ( ES ) d'entrée.
  5. Procédé suivant l'une des revendications précédentes, dans lequel la détection est effectuée séparément dans plusieurs bandes partielles.
  6. Procédé suivant la revendication 5, dans lequel le filtre ( AF ) adaptatif est adapté individuellement dans les bandes partielles.
  7. Dispositif de traitement du signal pour un système ( HG ) acoustique comprenant
    - un dispositif ( V, AF ) de traitement pour la production d'un signal ( AS ) de sortie à partir d'un signal ( ES ) d'entrée en tenant compte d'un signal ( RS ) de réaction,
    - un dispositif de modulation pour la modulation ( MO ) du signal ( AS ) de sortie par application d'une caractéristique au signal ( AS ) de sortie, de manière à obtenir, lors d'une réaction, un signal ( RS ) de réaction modulé d'une manière correspondante, et
    - un dispositif ( RD ) de détection pour la détection du signal ( RS ) de réaction modulé, dans lequel le signal de réaction peut être détecté par le dispositif ( RD ) de détection sur la base de la présence de la caractéristique appliquée,
    caractérisé en ce que
    - le signal ( AS ) de sortie peut être modulé par le dispositif ( MO ) de modulation par modulation de phase et
    - la phase est à cet effet avancée et ramenée d'une fréquence donnée à l'avance entre deux valeurs de phase.
  8. Dispositif de traitement du signal suivant la revendication 7, dans lequel le dispositif ( V, AF ) de traitement comporte un filtre ( AF ) adaptable, dont la vitesse d'adaptation et/ou l'intensité d'action dépend de la quantité du signal ( RS ) de réaction.
  9. Dispositif de traitement du signal suivant la revendication 8, dans lequel la vitesse d'adaptation et/ou l'intensité d'action augmente proportionnellement avec la quantité du signal ( RS ) de réaction.
  10. dispositif de traitement du signal suivant l'une des revendications 7 à 9, dans lequel au moins un filtre coupe-bande peut être activé par le dispositif de traitement dans le cas de la détection d'un signal de réaction.
  11. Dispositif de traitement du signal suivant l'une des revendications 7 à 10, qui comporte pour plusieurs bandes partielles respectivement un dispositif ( RD ) de détection.
  12. dispositif de traitement du signal suivant l'une des revendications 7 à 11, qui utilise une boucle fermée pour l'application d'une modification de signal.
EP05109366.4A 2004-10-14 2005-10-07 Procédé et dispositif pour réduire les rétroactions dans un système acoustique Not-in-force EP1648197B2 (fr)

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
DE102004050304A DE102004050304B3 (de) 2004-10-14 2004-10-14 Verfahren zur Reduktion von Rückkopplungen bei einem Akustiksystem und Signalverarbeitungsvorrichtung

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EP1648197A2 EP1648197A2 (fr) 2006-04-19
EP1648197A3 EP1648197A3 (fr) 2008-01-23
EP1648197B1 EP1648197B1 (fr) 2011-09-14
EP1648197B2 true EP1648197B2 (fr) 2015-01-07

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EP (1) EP1648197B2 (fr)
JP (1) JP4309390B2 (fr)
CN (1) CN1774144B (fr)
AT (1) ATE524937T1 (fr)
AU (1) AU2005220246B2 (fr)
DE (1) DE102004050304B3 (fr)
DK (1) DK1648197T4 (fr)

Families Citing this family (10)

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Publication number Priority date Publication date Assignee Title
DE102006023723A1 (de) * 2006-05-19 2007-11-22 Siemens Audiologische Technik Gmbh Hörvorrichtung mit Rückkopplungsdetektion und entsprechendes Verfahren
US8280088B2 (en) 2006-05-19 2012-10-02 Siemens Audiologische Technik Gmbh Hearing apparatus with feedback detection and corresponding method
DE102006029194B4 (de) * 2006-06-26 2010-04-15 Siemens Audiologische Technik Gmbh Vorrichtung und Verfahren zur Schrittweitensteuerung eines adaptiven Filters
EP2148527B1 (fr) * 2008-07-24 2014-04-16 Oticon A/S Système de réduction de réponse acoustique pour les appareils d'aide auditive utilisant une transmission de signal inter-auriculaire, procédé et utilisation
DE102008036803B3 (de) 2008-08-07 2009-12-17 Siemens Medical Instruments Pte. Ltd. Anordnung und Verfahren zur Regelung einer Rückkopplungsunterdrückung bei Hörvorrichtungen
DE102009016845B3 (de) 2009-04-08 2010-08-05 Siemens Medical Instruments Pte. Ltd. Anordnung und Verfahren zur Erkennung von Rückkopplungen bei Hörvorrichtungen
CN102740189B (zh) * 2011-04-01 2014-10-08 中国科学院声学研究所 一种基于时间反转的声反馈抑制方法
CN104320750B (zh) * 2014-11-25 2018-08-17 厦门莱亚特医疗器械有限公司 一种测量助听器反馈路径的方法
CN104575520A (zh) * 2014-12-16 2015-04-29 中国农业大学 一种结合心理声学评价的声波监测装置及方法
WO2023277022A1 (fr) * 2021-06-28 2023-01-05 ヤマハ株式会社 Dispositif de traitement du son, procédé de traitement du son et programme

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WO2000044113A1 (fr) † 1999-01-21 2000-07-27 Acoustic Technologies, Inc. Reduction de la retroaction acoustique par modulation numerique
EP1191814A1 (fr) † 2000-09-25 2002-03-27 TOPHOLM & WESTERMANN APS Prothèse auditive avec un filtre adaptatif pour la suppression de la réaction acoustique
US7092532B2 (en) † 2003-03-31 2006-08-15 Unitron Hearing Ltd. Adaptive feedback canceller

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US5748751A (en) † 1994-04-12 1998-05-05 U.S. Philips Corporation Signal amplifier system with improved echo cancellation
WO2000044113A1 (fr) † 1999-01-21 2000-07-27 Acoustic Technologies, Inc. Reduction de la retroaction acoustique par modulation numerique
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Publication number Publication date
EP1648197A3 (fr) 2008-01-23
AU2005220246B2 (en) 2007-09-27
DE102004050304B3 (de) 2006-06-14
AU2005220246A1 (en) 2006-05-04
EP1648197B1 (fr) 2011-09-14
CN1774144A (zh) 2006-05-17
DK1648197T3 (da) 2011-12-19
DK1648197T4 (en) 2015-04-13
ATE524937T1 (de) 2011-09-15
JP4309390B2 (ja) 2009-08-05
EP1648197A2 (fr) 2006-04-19
JP2006115509A (ja) 2006-04-27
CN1774144B (zh) 2013-12-18

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