EP1406380A1 - Circuit melangeur - Google Patents

Circuit melangeur Download PDF

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Publication number
EP1406380A1
EP1406380A1 EP01949963A EP01949963A EP1406380A1 EP 1406380 A1 EP1406380 A1 EP 1406380A1 EP 01949963 A EP01949963 A EP 01949963A EP 01949963 A EP01949963 A EP 01949963A EP 1406380 A1 EP1406380 A1 EP 1406380A1
Authority
EP
European Patent Office
Prior art keywords
transistor
signal
transistors
mixer circuit
constant current
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP01949963A
Other languages
German (de)
English (en)
Other versions
EP1406380A8 (fr
Inventor
Yoshinori c/o MITSUBISHI DENKI K. K. TAKAHASHI
Hiroyuki c/o MITSUBISHI DENKI K. K.IS JOBA
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Mitsubishi Electric Corp
Original Assignee
Mitsubishi Electric Corp
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Mitsubishi Electric Corp filed Critical Mitsubishi Electric Corp
Publication of EP1406380A1 publication Critical patent/EP1406380A1/fr
Publication of EP1406380A8 publication Critical patent/EP1406380A8/fr
Withdrawn legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/14—Balanced arrangements
    • H03D7/1425—Balanced arrangements with transistors
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/14—Balanced arrangements
    • H03D7/1425—Balanced arrangements with transistors
    • H03D7/1433—Balanced arrangements with transistors using bipolar transistors
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/14—Balanced arrangements
    • H03D7/1425—Balanced arrangements with transistors
    • H03D7/1441—Balanced arrangements with transistors using field-effect transistors
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/14—Balanced arrangements
    • H03D7/1425—Balanced arrangements with transistors
    • H03D7/1458—Double balanced arrangements, i.e. where both input signals are differential
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D2200/00—Indexing scheme relating to details of demodulation or transference of modulation from one carrier to another covered by H03D
    • H03D2200/0001—Circuit elements of demodulators
    • H03D2200/0025—Gain control circuits

Definitions

  • the present invention relates generally to mixer circuits and particularly to a direct conversion mixer for use in mobile communications.
  • a direct conversion system which converts a signal modulated into a radio frequency directly to a baseband signal and modulates a baseband directly to a radio frequency.
  • this system does not provide an intermediate frequency. As such, it can dispense with image suppression, reduce spurious source, an d simplify a system advantageously.
  • the system provides 2nd order intermodulation distortion, local oscillation wave noise, and other similar disadvantages.
  • One approach to alleviate these disadvantages is an even harmonics mixer such as an anti-parallel diode.
  • Fig. 5 is a circuit diagram showing one example of a conventional even harmonics mixer using transistors.
  • transistors 1 and 2 have their respective collectors connected together and their respective emitters connected together to configure a local frequency multiplication unit.
  • a resistor R1 is connected between the collectors and a power supply and a resistor R2 is connected between the emitters and ground.
  • Transistors 1 and 2 receive a modulated wave signal BB at their respective emitters and receive signals LO and ⁇ LO (" ⁇ " indicates an inverted signal) each having a component of a frequency of a local oscillation wave inverted in phase at their respective bases.
  • the local frequency multiplication unit generates a local oscillation wave frequency component multiplied by two and can extract a desired frequency component by multiplying an input signal frequency and the local oscillation wave frequency component.
  • the mixer of Fig. 5 is associated with a small power gain and requires a high local oscillation wave input to operate the local frequency multiplication unit.
  • a main object of the present invention is therefore to provide in the field of high-frequency radio communications a mixer circuit suitable for applications for which there is a demand for low frequency currents, high IC yields and simplified system configurations.
  • a mixer circuit includes: a local frequency multiplication unit configured of a first transistor having an input electrode receiving a frequency component of a local oscillation wave signal and a second transistor receiving a signal opposite in phase to the local oscillation wave, the first and second transistors having their respective first electrodes connected together and their respective second electrodes connected together, the local frequency multiplication unit outputting a modulation signal at the first electrode of each transistor; a third transistor connected in a pair with each of the first and second transistors of the local frequency multiplication unit, having an input electrode receiving a reference signal, and a first electrode differentially outputting the modulation signal; a voltage source providing the first, second and third transistors at their respective first electrodes with a predetermined voltage; a signal input unit connected to the first, second and third transistors at their respective second electrodes and receiving a modulated signal; and a constant current source connected to the signal input unit.
  • the signal input unit is a fourth transistor having an input electrode receiving the modulated signal, a first electrode connected to the second electrode of each of the first, second and third transistors, and a second electrode connected to the constant current source.
  • the voltage source is connected to the two local frequency multiplication units commonly, and the constant current source supplies a constant current to the two fourth transistors commonly.
  • the constant current source is a variable constant current source.
  • the mixer circuit further includes a variable current source varying a bias current provided to the input electrode of the third transistor.
  • Fig. 1 is a circuit diagram of a mixer circuit of one embodiment of the present invention.
  • transistors 1 and 2 similarly as shown in the conventional example of Fig. 5, transistors 1 and 2 have their respective collectors connected together and their respective emitters connected together, each collector receiving a power supply via a resister R3, and their respective bases receiving frequency components signals LO and ⁇ LO of a local oscillation wave to configure a local frequency multiplication unit 10.
  • Local frequency multiplication unit 10 generates in a manner similar to that of an even harmonics mixer a frequency corresponding to the local oscillation wave frequency multiplied by two.
  • a reference transistor 3 has its emitter connected to the emitters of transistors 1 and 2, its collector connected to a power supply via a resistor R4, and its base receiving a bias current Ref.
  • Resistors R3 and R4 configure a load 6 serving as a voltage source. In place of resistors R3, R4 a different type of load may be connected. Transistors 1, 2 and 3 have their emitters connected to the collector of a transistor 4 for receiving a modulated wave. Transistor 4 has its emitter receiving a constant current from a constant current source 5 and its base receiving a modulated wave signal BB.
  • the sum of the current flowing through local frequency multiplication unit 10 configured of transistors 1 and 2 and that flowing through transistor 3 equals that flowing through transistor 4. Furthermore, the current flowing through transistor 4 equals the constant current of constant current source 5. As such by allowing transistor 4 to have a gain a mixer circuit having a gain can be implemented.
  • the frequency multiplied by two and generated by local frequency multiplication unit 10 configured of transistors 1 and 2 varies the current of local frequency multiplication unit 10. Since transistor 4 provides a constant-current operation relative to local frequency multiplication unit 10 and transistor 3, the variation in current results in transistor 3 having a current of opposite phase flowing therethrough. Transistor 4 has a gain for a modulated wave that is received and the amplified signal is converted in frequency by local frequency multiplication unit 10. The signal converted in frequency is output at load 6 as differential output signals RF and ⁇ RF.
  • a mixer circuit configured of local frequency multiplication unit 10 configured of transistors 1 and 2 and an input unit formed of transistor 4 to receive a modulated wave is provided with reference transistor 3 paired with local frequency multiplication unit 10 to provide a differential mixer. Without increasing an input level of a local oscillation wave a large-gain mixer circuit can be implemented.
  • Fig. 2 is a circuit diagram of another embodiment of present invention.
  • local frequency multiplication unit 10 and transistors 3 and 4 are similar in configuration to those shown in Fig. 1.
  • a local frequency multiplication unit 20 and transistors 9, 11 are configured similarly as shown in the mixer circuit of Fig. 1. More specifically, transistors 7 and 8 have their respective collectors connected together, their respective emitters connected together, and their respective bases receiving frequency component signals LO, ⁇ LO of a local oscillation wave, respectively.
  • Transistors 7, 8 have their respective emitters connected to the emitter of a reference transistor 9.
  • Reference transistor 9 has its base receiving a bias current.
  • Each transistor 7, 8, 9 has its emitter connected to the collector of a transistor 11 receiving a modulated wave.
  • Transistor 11 has its base receiving a modulated wave signal ⁇ BB opposite in phase to the modulated wave signal BB input to the base of transistor 4.
  • Local frequency multiplication unit 20 has its collectors connected to collectors of local frequency multiplication unit 10, and each collector receives a power supply commonly via a resistor R3.
  • Transistor 9 has its collector connected to a collector of transistor 3 and these collectors receive a power supply via a resistor R4.
  • Transistor 11 has its emitter connected to an emitter of transistor 4 and these emitters are connected to constant current source 5 commonly.
  • the mixer circuit of Fig. 2 corresponds to the mixer circuit of Fig. 1 if the mixer circuit of Fig. 1 has the Gilbert cell configuration.
  • each mixer circuit having the same configuration as shown in Fig. 1 can have a large gain, as aforementioned, and it can also realize the Gilbert cell configuration to implement a mixer circuit capable of suppressing a frequency component of a local oscillation wave leaking toward an output.
  • Fig. 3 is a circuit diagram showing another embodiment of the present invention.
  • constant current source 5 shown in Fig. 1 is replaced by a variable current source 12.
  • a variable gain control effect can be obtained.
  • Fig. 4 is a circuit diagram showing still another embodiment of the present invention.
  • a variable current source 13 is connected to the base of the reference transistor 3 of Fig. 1 to allow a bias current to be variable. A variable gain control effect can be obtained.
  • the above embodiments have described a mixer circuit mixing a frequency component of a local oscillation wave and the signal of a modulated wave BB together to output a signal of a modulated wave.
  • the mixer circuit may receive a radio frequency signal having been received as a signal of a modulated wave and mix it with a frequency component of a local oscillation wave, and output a baseband signal as a modulation signal.
  • a mixer circuit configured of a local frequency multiplication unit and an input unit receiving a modulated wave is provided with a reference transistor to provide a differential mixer thereby to simplify a system configuration with large gain. Furthermore, constant-current control can reduce dependency on semiconductor process variation and providing a constant current source in a bandgap configuration can reduce power supply voltage variation and temperature variation.
  • a mixer circuit can have both of an advantage of a conventional mixer circuit and that of an even harmonics mixer to allow the even harmonics mixer to be active to implement a large-gain mixer circuit while preventing an influence of a carrier component. It is applicable to mobile communications involving modulation from a baseband signal directly to a radio frequency.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Amplitude Modulation (AREA)
  • Superheterodyne Receivers (AREA)
EP01949963A 2001-07-12 2001-07-12 Circuit melangeur Withdrawn EP1406380A1 (fr)

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
PCT/JP2001/006062 WO2003009465A1 (fr) 2001-07-12 2001-07-12 Circuit melangeur

Publications (2)

Publication Number Publication Date
EP1406380A1 true EP1406380A1 (fr) 2004-04-07
EP1406380A8 EP1406380A8 (fr) 2004-07-21

Family

ID=11737541

Family Applications (1)

Application Number Title Priority Date Filing Date
EP01949963A Withdrawn EP1406380A1 (fr) 2001-07-12 2001-07-12 Circuit melangeur

Country Status (5)

Country Link
US (1) US6759887B2 (fr)
EP (1) EP1406380A1 (fr)
JP (1) JP4040473B2 (fr)
CN (1) CN1481605A (fr)
WO (1) WO2003009465A1 (fr)

Families Citing this family (13)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20030211094A1 (en) 2001-06-26 2003-11-13 Nelsestuen Gary L. High molecular weight derivatives of vitamin k-dependent polypeptides
US20020102958A1 (en) * 2001-01-29 2002-08-01 Buer Kenneth V. Sub-harmonically pumped k-band mixer utilizing a conventional ku-band mixer IC
WO2003079538A1 (fr) * 2002-03-15 2003-09-25 Mitsubishi Denki Kabushiki Kaisha Convertisseur de frequence
US7358121B2 (en) * 2002-08-23 2008-04-15 Intel Corporation Tri-gate devices and methods of fabrication
US20050176398A1 (en) * 2002-08-23 2005-08-11 Kenichi Maeda Mixer circuit
US7965994B2 (en) * 2004-10-29 2011-06-21 Broadcom Corporation Method and system for an analog zero-IF interface for GSM receivers
US20080094107A1 (en) * 2006-10-20 2008-04-24 Cortina Systems, Inc. Signal magnitude comparison apparatus and methods
US20080284489A1 (en) * 2007-05-14 2008-11-20 Mediatek Singapore Pte Ltd Transconductor and mixer with high linearity
KR101466851B1 (ko) * 2008-12-30 2014-11-28 주식회사 동부하이텍 3개 입력들을 비교하는 비교 회로
CN103117709B (zh) * 2013-02-05 2016-05-25 天津大学 一种基于对数放大器的混频器
US10141930B2 (en) 2013-06-04 2018-11-27 Nvidia Corporation Three state latch
JP6238400B2 (ja) * 2013-09-06 2017-11-29 株式会社デンソー 高調波ミキサ
JP6299637B2 (ja) * 2015-03-19 2018-03-28 三菱電機株式会社 高周波ミクサ

Family Cites Families (5)

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Publication number Priority date Publication date Assignee Title
JPH02190011A (ja) 1989-01-18 1990-07-26 Nec Corp ダブルバランスミキサ半導体集積回路
JP3052872B2 (ja) 1997-02-05 2000-06-19 日本電気株式会社 バランス型ミキサのミキシング方法と回路
US5936466A (en) * 1997-08-04 1999-08-10 International Business Machines Corporation Differential operational transconductance amplifier
JP3665714B2 (ja) 1998-06-30 2005-06-29 株式会社東芝 周波数変換器
US6631257B1 (en) * 2000-04-20 2003-10-07 Microtune (Texas), L.P. System and method for a mixer circuit with anti-series transistors

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
See references of WO03009465A1 *

Also Published As

Publication number Publication date
US6759887B2 (en) 2004-07-06
WO2003009465A1 (fr) 2003-01-30
CN1481605A (zh) 2004-03-10
US20040027187A1 (en) 2004-02-12
EP1406380A8 (fr) 2004-07-21
JP4040473B2 (ja) 2008-01-30
JPWO2003009465A1 (ja) 2004-11-11

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