EP1233657B1 - Schutzschaltung für eine Leuchtstofflampe - Google Patents

Schutzschaltung für eine Leuchtstofflampe Download PDF

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Publication number
EP1233657B1
EP1233657B1 EP02001285A EP02001285A EP1233657B1 EP 1233657 B1 EP1233657 B1 EP 1233657B1 EP 02001285 A EP02001285 A EP 02001285A EP 02001285 A EP02001285 A EP 02001285A EP 1233657 B1 EP1233657 B1 EP 1233657B1
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EP
European Patent Office
Prior art keywords
resistor
voltage
point
component
protective circuit
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
EP02001285A
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German (de)
English (en)
French (fr)
Other versions
EP1233657A3 (de
EP1233657A2 (de
Inventor
Harald Schmitt
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Osram GmbH
Original Assignee
Patent Treuhand Gesellschaft fuer Elektrische Gluehlampen mbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
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Publication date
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Publication of EP1233657A2 publication Critical patent/EP1233657A2/de
Publication of EP1233657A3 publication Critical patent/EP1233657A3/de
Application granted granted Critical
Publication of EP1233657B1 publication Critical patent/EP1233657B1/de
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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/295—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
    • H05B41/298—Arrangements for protecting lamps or circuits against abnormal operating conditions
    • H05B41/2981—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
    • H05B41/2985—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions against abnormal lamp operating conditions

Definitions

  • the present invention relates to a protection circuit for a fluorescent lamp having a first and a second lamp filament, comprising a DC voltage source with a positive and a negative pole, a half-bridge arrangement having a first and a second switch, wherein the half-bridge arrangement is powered by the DC voltage source and the first and second the second switch being interconnected to form a first reference point, the first reference point being connected to the negative pole via a first resistor, a coupling capacitor arranged in serial connection between the half-bridge arrangement and the first or second coil, the coil side Terminal of the decoupling capacitor forms a second reference point, which is connected via a second resistor to the negative terminal, a comparator having a first and a second input and an output, wherein the first input to the first Re reference point and the second input is connected to the second reference point, wherein the output is connected via a detection capacitor to the negative terminal, and an evaluation circuit with which the voltage drop across the detection capacitor voltage is evaluated to exceed a predetermined voltage level to cause deactivation of the half-bridge arrangement
  • Such a protection circuit is for example off EP-A-886 460 or WO-A-00/11916 is known and incorporated, for example by the assignee of the present invention in ballasts for fluorescent lamps.
  • the protection circuit is at the end of life of the fluorescent lamp, ie if the lamp is not defective, evaluate a criterion that in good time before overheating in the helix area (risk of melting the socket) leads to a shutdown of the half-bridge arrangement (also known as end-of -Life-shutdown). In this case, use is made of the fact that the filaments of a fluorescent lamp are covered with emitters in order to reduce the work function of the electrons.
  • the two reference points lie on average at a potential which corresponds to half the voltage provided by the DC voltage source.
  • the second of the two reference points is at a different potential and thus the reference points at different potential.
  • the potential difference is used to charge a detection capacitor, wherein the evaluation circuit is advantageously realized so that a voltage level is adjustable, beyond which a deactivation of the half-bridge arrangement is effected.
  • the term "relamping" is known. This is understood in a lighting system comprising several lamps to allow the insertion of a new lamp, without that the supply voltage and thus the other lamps must be turned off. Rather, it should be ensured that the voltage applied across the entire process of replacement mains voltage causes the newly inserted lamp immediately burns again. Also for this circuit structures are for example off US-A-5770925 known.
  • the disadvantage of the prior art approach is that the additional implementation of the relamping function of such ballasts, which is a mass product, significantly more expensive and therefore often be omitted.
  • ballasts in which an end-of-life detection and relamping are realized
  • ballasts in which only the end-of-life detection is realized.
  • all lamps must be turned off to effect a reset of the end-of-life detection. Only after switching off all lamps a new lamp can be used instead of the decrepit lamp. Afterwards all lamps can be switched on again. Especially in large factory buildings such interruptions are undesirable.
  • the object of the present invention is therefore to make available a cost-effective realization of the end-of-life detection and the relamping function.
  • the generic protection circuit further comprises a third resistor which bridges the decoupling capacitor and a fourth resistor which connects the first reference point to the positive pole of the DC voltage source, wherein the first, the second, the third and the fourth resistor are selected so that the first and the second reference point without inserted fluorescent lamp are at the same potential.
  • the invention is based on the idea of designing the end-of-life detection circuit or realizing the relamping function in such a way that as many components as possible are shared.
  • a cost-effective realization of the additional relamping function can thus be realized almost without additional expenditure, which results in a very desirable price reduction.
  • the idea consists in supplying the comparator, which detects an asymmetry, with identical fluorescent potential at its two inputs identical potentials, which cause a resetting of the shutdown of the half-bridge arrangement.
  • the two reference points are on average at half the potential of the DC voltage provided by the DC voltage source. This is usually the so-called intermediate circuit voltage and is usually provided on a DC link capacitor.
  • the ratio of the first resistance to the fourth resistance is the same big as the ratio of second resistance to third resistance.
  • the two reference points are even with the fluorescent lamp removed at a potential corresponding to half of the DC voltage source provided DC voltage.
  • the first resistor comprises a first and a second series resistor connected in series and the second resistor comprises a third and a fourth series resistor connected in series, wherein the first reference point with the connection point of the first partial resistor and the fourth resistor and the second reference point with the Connection point of the third resistor and the third partial resistance is connected and the first input of the comparator is connected to the connection point between the first and second partial resistance and the second input of the comparator is connected to the connection point between the third and the fourth partial resistance.
  • resistors of the voltage dividers need to be designed as high-voltage resistors.
  • the comparator and evaluation must be low voltage suitable. Rather, it is sufficient if a high-voltage resistor is provided per voltage divider, which results in a further cost reduction.
  • the ratio of the sum of the first and second partial resistances to the fourth resistance becomes equal to the ratio of the sum of the third and fourth partial resistance to the third resistor.
  • the two reference points are again at a fluorescent lamp removed at a potential which corresponds to half of the DC voltage source provided DC voltage.
  • the comparator comprises a first and a second switching element, each comprising a working, a control and a reference electrode
  • the fourth partial resistor comprises a fifth and a sixth series resistor connected in series
  • the connection point between the first and the second partial resistance is connected to the reference electrode of the first and to the control electrode of the second switching element
  • the connection point between the third partial resistance and the fifth partial resistance is connected to the control electrode of the first switching element
  • the connection point between the fifth and the sixth resistor is connected to the reference electrode of the second switching element
  • the working electrode of the first switching element and the working electrode of the second switching element to each other and via a series circuit of a fifth resistor and the Detek tion capacitor are connected to ground.
  • the ratio of the partial resistances three, five and six, the potential difference leading to the onset of charging of the detection capacitor can be adjusted.
  • the comparator is realized in a very simple and inexpensive form.
  • the ratio of the fourth resistance to the sum of the first and the second partial resistance is equal to the ratio of the third resistance to the sum of the third, fifth and sixth partial resistance.
  • the reference points are in turn drawn at fluorescent lamp at a potential corresponding to half of the DC voltage source provided DC voltage.
  • the evaluation circuit may comprise a holding member with a triggering potential and be designed so that as soon as the triggering potential assumes a predetermined potential, in particular already by a single pulse, the holding member is activated to deactivate the half-bridge circuit until a reset operation by removing the fluorescent lamp is triggered. This measure ensures a safe deactivation of the half-bridge arrangement and thus for a particularly high reliability of the protection circuit according to the invention.
  • a first threshold component in particular a Zener diode, can be arranged, with which the threshold can be set, above which a deactivation of the half-bridge circuit is triggered. This measure enables the activation of the holding member at a predeterminable voltage on the detection capacitor.
  • the Zündnapssbegrenzungsscrien can in this case have a measuring element for measuring a proportional to the ignition current size, so that the value of this size is suitable for activating the holding member.
  • This embodiment makes use of the fact that the ignition current is approximately proportional to the ignition voltage and therefore can be used as a measure of the ignition voltage. Since the ignition current is easier to measure than the ignition voltage, this results in a simple construction of the circuit arrangement.
  • a second threshold device in particular a Zener diode arranged with the threshold is adjustable, beyond which a deactivation of the half-bridge circuit is triggered.
  • This variant allows a particularly simple adaptation of the potentials of the ignition voltage limiting circuit to the potentials of the holding member.
  • the measuring element may in particular be a resistor which is arranged serially to one of the half-bridge switches.
  • This embodiment is the Recognizing that the ignition current is also provided by the half-bridge arrangement and therefore the current flowing through the half-bridge arrangement is proportional to the ignition current.
  • a resistor is arranged serially to one of the half-bridge switch as the measuring element, it is particularly easy to determine a variable proportional to the ignition current.
  • Common practice is the switching of a storage capacitor between plus and minus pole.
  • operating circuits for fluorescent lamps in which the voltage at said storage capacitor increases with increasing amplitude of the ignition voltage.
  • One type of operating circuit that has this characteristic are so-called pump circuits.
  • pump circuits it is possible to monitor the ignition voltage by monitoring the voltage across said storage capacitor.
  • the tripping potential point of the holding member is connected via a Zündnapssbegrenzungsscrien with the voltage of the storage capacitor.
  • the ignition voltage limiting circuit consists of a resistor which adapts the voltage on the storage capacitor to the tripping potential required for tripping.
  • the embodiments according to the invention preferably also include suitable screening circuits in order to provide direct voltages for evaluation at the reference and potential points.
  • the half-bridge arrangement converts the DC voltage provided by the DC voltage source into an AC voltage which is reflected in the subsequent protection circuit.
  • To evaluate the signals at the reference points are essentially DC voltages interesting, so that by suitable Siebscrienen For example, using capacitors, ensures that they are provided for further processing.
  • a capacitor C1 provides a voltage Uz, which serves to supply the subsequent circuit arrangement.
  • a half-bridge arrangement comprises a first switch S1 and a second switch S2. The controls of the switches S1 and S2 are well known to those skilled in the art and therefore not shown in FIG. 1 for reasons of clarity.
  • the half-bridge arrangement feeds via a decoupling capacitor C2 a fluorescent lamp L A with a first filament W1 and a second filament W2.
  • the fluorescent lamp L A is connected to an ignition circuit Zs, which is designed to cause an ignition of the lamp L A
  • the center of the half-bridge arrangement forms a first reference point A, which is connected via a lamp inductor L D with the lamp L A.
  • the winding-side terminal of the decoupling capacitor C2 forms a second reference point B.
  • the potentials of both reference points A, B are fed to a comparator V G whose output is connected to a detection capacitor C3.
  • the across the capacitor C3 C3 voltage U is fed to an evaluation circuit AS, which causes a deactivation of the half-bridge arrangement upon exceeding a predetermined voltage level.
  • the potentials of the reference points A and B due to the absence of emitter on one of the two helical electrodes W1, W2 and the thus increasing increase the work function of one of the two helical electrodes W1, W2, even if the increase in work function only is minimal.
  • the potential difference between the two reference points leads to the charging of the capacitor C3 and thus to the build-up of the voltage U C3 . If this exceeds a certain value, the half-bridge arrangement is switched off by the evaluation circuit As and thus an overheating in the coil area prevented.
  • the reference points A and B are on average at half the voltage U Z.
  • the decoupling capacitor C2 could also be arranged elsewhere, for example between the lamp inductor L D and the filament electrode W2.
  • consumption of the emitter on the helical electrode W1 prior to consumption of the emitter on the helical electrode W2 would increase the voltage at the helix electrode W1, resulting in a rise in the voltage across the capacitor C2.
  • the potential B would increase in relation to the potential A.
  • the potential at the reference point A would drop from the potential at the reference point B.
  • a relamping function is realized by resetting the voltage across the capacitor C3 by applying identical potential to the two inputs of the comparator.
  • the first reference point A via a resistor R1
  • the second reference point B via a resistor R2 to the negative pole of the voltage U Z is connected.
  • the positive pole of the voltage U Z is on the one hand via a resistor R3, which bridges the capacitor C2, connected to the reference point B, on the other hand via a resistor R4 to the reference point A.
  • suitable dimensioning of the two voltage divider R4, R1 and R3, R2 can be achieved be that the potentials at the reference points A, B are identical when removed lamp L A and thus lead to a reset of the end-of-life detection.
  • a dimensioning of the ratio of the resistance R1 to the resistance R4 and from the resistance R2 to the resistance R3 equal to 1, that half the voltage of U Z at the two reference points A, B is established.
  • the resistors R1 and R2 are divided into two partial resistors R11, R12 and R21, R22.
  • By suitable dimensioning of the partial resistors it can be ensured that the majority of the voltages applied to the reference points A, B drop off at the partial resistors R11 and R21. Accordingly, the comparator V G is subjected only to low voltages and can therefore be realized with less voltage-resistant components.
  • FIGS. 3a / b an overall circuit for operating a fluorescent lamp is shown, which can be connected to a power supply via the terminals K1 and K2.
  • a fuse SI is arranged, followed by a filter circuit comprising a capacitor C4 and an inductor L3 before the mains signal is rectified in a power rectifier N GR .
  • the rectified output signal of the mains rectifier N GR is buffered in the capacitor C1 and serves to supply the subsequent circuit arrangement.
  • Resistor R22 of FIG. 2 is divided into two partial resistors R221 and R222.
  • the capacitor C3 is a resistor R5 connected in parallel, which allows a discharge of the capacitor C3.
  • the resistor R12 is connected in parallel with a capacitor C5, while the series connection of the resistors R221 and R222 is connected in parallel with a capacitor C6. These measures ensure that DC signals are present at the bases of two switching elements T1, T2 contained in the comparator.
  • the control electrode of the switching element T1 is connected to the connection point D between the resistor R21 and the resistor R221. Connected to the junction point C of the resistors R11 and R12 is the reference electrode of the switching element T1 and the control electrode of the switching element T2.
  • the reference electrode of the switching element T2 is connected to the connection point E between the resistors R221 and R222.
  • both switching elements T1, T2 are connected via a resistor R6 to the connection point F, to which the capacitor C3 is connected. Since the voltage is constant at the reference point A, a voltage of 15 V can be set by suitable selection of the resistors R11 and R12, for example at the connection point C. By suitable dimensioning of the resistors R21, R221 and R222 can be set in normal operation, ie the potential at point A is equal to the potential at point B, a voltage which is at point D 18 V and at point E 12 V. In this state, the two switching elements T1, T2 are disabled.
  • the switching element T1 begins to conduct when the voltage at point D becomes smaller than the voltage at point C. As long as the voltage at point E is less than the voltage at point C remains the switching element T2 locked. By conducting the switching element T1, the capacitor C3 is again charged via the resistor R6. With the height of the voltage difference between the potential points C and D or C and E, the switching threshold and thus the degree of asymmetry at which the shutdown occurs, can be additionally set.
  • the voltage at the point F which corresponds to the state of charge of the capacitor C3, is transmitted via a diode D1 and a Zener diode Z1 to a tripping potential point G in a holding member HG.
  • the holding member HG is supplied via the charge stored in a capacitor C7 of a starting circuit ST.
  • the switching element T4 turns on.
  • the switching element T3 turns on and thus supplies the holding current for a retaining element that is self-holding in this way.
  • the resistor R8 in combination with the capacitor C8 and the resistor R9 in combination with the capacitor C9 provide for the elimination of interference, thereby preventing accidental activation of the holding member. Characterized in that the switching element T4 conducts, the potential at point I drops to 0 V.
  • the two switches S1 and S2 of the half-bridge circuit have respective drive circuits A S1 , A S2 .
  • Each drive circuit A S1 , A S2 comprises an inductance L1, L2, which is coupled to the lamp inductor L D. As soon as the potential at point I falls to 0 V, the diode D2 begins to conduct, thus grounding the signal fed via the inductance L2 into the drive circuit A S2 , so that the switch S2 is no longer activated. This also leads to a shutdown of the switch S1.
  • a ZündHarndsbegrenzungsscrien Z SB With the point G of the holding member H G is further connected a Zünddozenssbegrenzungsscrien Z SB . It comprises a measuring resistor R10, which is arranged in series with the switch S2. The potential at the point J, that is, the voltage dropping across the resistor R10 is proportional to the ignition current and thus proportional to the ignition voltage.
  • the Zündtemposbegrenzungsweakened Z SB has the task, for example, to prevent destruction of the ignition circuit Z S in air pullers ..
  • the ignition circuit Z S comprises two capacitors C10 and C11 and PTC1 PTC.
  • the resistor R14 serves to cause a time delay of the response of the Zünddozenssbegrenzungscnies. Via the diodes D3 and Z2, the level can be set at which a Zünddozenssbegrenzung by acting on the point G of the holding member H G and thus a shutdown of the half-bridge arrangement is performed.
  • the voltage across resistor R10 is filtered by resistor R9 and capacitor C9.
  • the level of the critical ignition voltage can also be influenced by the value of the resistor R10.
  • the diode D3 protects the holding member H G also against negative voltage spikes.

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  • Circuit Arrangements For Discharge Lamps (AREA)
  • Circuit Arrangement For Electric Light Sources In General (AREA)
EP02001285A 2001-02-20 2002-01-17 Schutzschaltung für eine Leuchtstofflampe Expired - Lifetime EP1233657B1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE10108138 2001-02-20
DE10108138A DE10108138A1 (de) 2001-02-20 2001-02-20 Schutzschaltung für eine Leuchstofflampe

Publications (3)

Publication Number Publication Date
EP1233657A2 EP1233657A2 (de) 2002-08-21
EP1233657A3 EP1233657A3 (de) 2006-05-24
EP1233657B1 true EP1233657B1 (de) 2007-07-25

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EP02001285A Expired - Lifetime EP1233657B1 (de) 2001-02-20 2002-01-17 Schutzschaltung für eine Leuchtstofflampe

Country Status (7)

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US (1) US6650514B2 (zh)
EP (1) EP1233657B1 (zh)
CN (1) CN100477880C (zh)
AT (1) ATE368367T1 (zh)
CA (1) CA2373571A1 (zh)
DE (2) DE10108138A1 (zh)
TW (1) TW540255B (zh)

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US8319446B2 (en) 2007-04-19 2012-11-27 Osram Ag Circuit for controlling a fluorescent lamp, method for operating the circuit, and system comprising the circuit

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US7598677B2 (en) * 2003-08-26 2009-10-06 Q Technology, Inc. Multiple failure detection shutdown protection circuit for an electronic ballast
US7405522B2 (en) * 2003-08-26 2008-07-29 Q Technology, Inc. Multiple failure detection shutdown protection circuit for an electronic ballast
US7187139B2 (en) 2003-09-09 2007-03-06 Microsemi Corporation Split phase inverters for CCFL backlight system
US7468722B2 (en) 2004-02-09 2008-12-23 Microsemi Corporation Method and apparatus to control display brightness with ambient light correction
WO2005099316A2 (en) 2004-04-01 2005-10-20 Microsemi Corporation Full-bridge and half-bridge compatible driver timing schedule for direct drive backlight system
US7755595B2 (en) 2004-06-07 2010-07-13 Microsemi Corporation Dual-slope brightness control for transflective displays
DE102005013898A1 (de) * 2005-03-24 2006-09-28 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Schaltungsanordnung zum Betrieb mindestens einer ersten und einer zweiten darin einsetzbaren Lampe
DE102005028419A1 (de) * 2005-06-20 2006-12-28 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Abschaltschaltung
US7414371B1 (en) * 2005-11-21 2008-08-19 Microsemi Corporation Voltage regulation loop with variable gain control for inverter circuit
US7569998B2 (en) 2006-07-06 2009-08-04 Microsemi Corporation Striking and open lamp regulation for CCFL controller
DE102006036293A1 (de) * 2006-08-03 2008-02-14 Cooper Crouse-Hinds Gmbh Überwachungsvorrichtung
DE502007006528D1 (de) * 2007-03-29 2011-03-31 Osram Gmbh Schaltungsanordnung zur ansteuerung mindestens einer leuchtstofflampe
US8093839B2 (en) 2008-11-20 2012-01-10 Microsemi Corporation Method and apparatus for driving CCFL at low burst duty cycle rates
US8487541B2 (en) * 2010-10-11 2013-07-16 General Electric Company Method to ensure ballast starting regardless of half cycle input
US8810146B1 (en) 2011-11-04 2014-08-19 Universal Lighting Technologies, Inc. Lighting device with circuit and method for detecting power converter activity
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CN103369770B (zh) * 2012-03-31 2016-09-07 海洋王照明科技股份有限公司 灯具过温保护电路及装置

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Publication number Priority date Publication date Assignee Title
US8319446B2 (en) 2007-04-19 2012-11-27 Osram Ag Circuit for controlling a fluorescent lamp, method for operating the circuit, and system comprising the circuit

Also Published As

Publication number Publication date
CA2373571A1 (en) 2002-08-20
TW540255B (en) 2003-07-01
DE10108138A1 (de) 2002-08-29
CN100477880C (zh) 2009-04-08
ATE368367T1 (de) 2007-08-15
CN1374824A (zh) 2002-10-16
DE50210534D1 (de) 2007-09-06
EP1233657A3 (de) 2006-05-24
EP1233657A2 (de) 2002-08-21
US20020114114A1 (en) 2002-08-22
US6650514B2 (en) 2003-11-18

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