EP0978183A2 - Procede et appareil de traitement d'un signal dans un appareil de telecommunication - Google Patents

Procede et appareil de traitement d'un signal dans un appareil de telecommunication

Info

Publication number
EP0978183A2
EP0978183A2 EP98917151A EP98917151A EP0978183A2 EP 0978183 A2 EP0978183 A2 EP 0978183A2 EP 98917151 A EP98917151 A EP 98917151A EP 98917151 A EP98917151 A EP 98917151A EP 0978183 A2 EP0978183 A2 EP 0978183A2
Authority
EP
European Patent Office
Prior art keywords
transmitter
feedback
equalizer
receiver
filter
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP98917151A
Other languages
German (de)
English (en)
Other versions
EP0978183B1 (fr
Inventor
Heikki Laamanen
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Infinera Oy
Original Assignee
Tellabs Oy
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Tellabs Oy filed Critical Tellabs Oy
Publication of EP0978183A2 publication Critical patent/EP0978183A2/fr
Application granted granted Critical
Publication of EP0978183B1 publication Critical patent/EP0978183B1/fr
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/38—Synchronous or start-stop systems, e.g. for Baudot code
    • H04L25/40—Transmitting circuits; Receiving circuits
    • H04L25/49—Transmitting circuits; Receiving circuits using code conversion at the transmitter; using predistortion; using insertion of idle bits for obtaining a desired frequency spectrum; using three or more amplitude levels ; Baseband coding techniques specific to data transmission systems
    • H04L25/497—Transmitting circuits; Receiving circuits using code conversion at the transmitter; using predistortion; using insertion of idle bits for obtaining a desired frequency spectrum; using three or more amplitude levels ; Baseband coding techniques specific to data transmission systems by correlative coding, e.g. partial response coding or echo modulation coding transmitters and receivers for partial response systems
    • H04L25/4975—Correlative coding using Tomlinson precoding, Harashima precoding, Trellis precoding or GPRS
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L25/03012—Arrangements for removing intersymbol interference operating in the time domain
    • H04L25/03019—Arrangements for removing intersymbol interference operating in the time domain adaptive, i.e. capable of adjustment during data reception
    • H04L25/03057—Arrangements for removing intersymbol interference operating in the time domain adaptive, i.e. capable of adjustment during data reception with a recursive structure
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L25/03343—Arrangements at the transmitter end
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/38—Synchronous or start-stop systems, e.g. for Baudot code
    • H04L25/40—Transmitting circuits; Receiving circuits
    • H04L25/49—Transmitting circuits; Receiving circuits using code conversion at the transmitter; using predistortion; using insertion of idle bits for obtaining a desired frequency spectrum; using three or more amplitude levels ; Baseband coding techniques specific to data transmission systems
    • H04L25/497—Transmitting circuits; Receiving circuits using code conversion at the transmitter; using predistortion; using insertion of idle bits for obtaining a desired frequency spectrum; using three or more amplitude levels ; Baseband coding techniques specific to data transmission systems by correlative coding, e.g. partial response coding or echo modulation coding transmitters and receivers for partial response systems

Definitions

  • the invention relates to a method according to the preamble of claim 1 for processing a signal in a telecommunication apparatus.
  • the invention also relates to an apparatus for processing a signal in a telecommunication apparatus.
  • VDSL modem Very high speed Digital Subscriber Line
  • the bandwidth of the modulated signal may even be in the range of 10 MHz.
  • the modem receiver may be interfered with by AM radio stations and radio amateur stations whose transmitted radio waves may be connected to the aerial cable, partly becoming so called transversal interference in a twisted pair and being conveyed to the modem receiver, interfering with it.
  • a modem may, on the other hand, interfere with listening in on AM radio channels or with a radio amateur's reception because a modulated signal travelling in a twisted pair contains power at said radio frequencies and this power is partly emitted into the environment.
  • Radio interference caused by a transmitter may be eliminated by removing by filtering from the spectrum of a modulated signal the frequencies which are within the bands causing problems.
  • signal processing is mainly digital wherefore a received signal is converted into numeric form by means of an analog-to-digital converter (A/D converter).
  • A/D converter analog-to-digital converter
  • the level of the radio interference may be high compared to the received effective signal, it would be of advantage for the dynamics of the A D converter if at least a part of the radio interference filtering took place before the A/D conversion by means of a band stop filter implemented using analog techniques.
  • the operation of the adaptive line equalizer is made difficult if a modem signal is filtered in the transmitter, the receiver or both, because the filters change the transfer function and the impulse response or the so called system response of the entire signal path. Filters give rise to additional distortion which even contains transmission zeros in the problematic radio frequency bands. Band stop filters of narrow bandwidth are particularly problematic from the point of view of receiver equalizers because equalizing them requires time-wise very long adaptive equalizers.
  • Reference III (p. 574 to 577) describes a mechanism in the transmitter of a modem by means of which it is possible to provide transmission zeros in the transmission spectrum at desired frequencies without hampering the operation of the receiver.
  • band stop filters filtering radio interference can be made "invisible" for the adaptive line equalizer whereby the adaptive equalizers do not need to take part in equalizing the distortion of the system response caused by these band stop filters.
  • the method is suited for modems making use of generally known linear modulation methods: PAM modulation (Pulse Amplitude Modulation), QAM modulation (Quadrature Amplitude Modulation) or CAP modulation (Carrierless Amplitude/Phase coding).
  • the method is based on the use of the so called Tomlinson-Harashima precoding (in the following termed Tomlinson coding).
  • Tomlinson coding In the original Tomlinson coding method distortion caused by the channel or part of the distortion is corrected by means of a filter in the transmitter. QAM and CAP modulation produce signals which are of the bandpass type.
  • the examination can, however, always be carried out by using the commonly known, so called baseband equivalent channel model where the transfer function of the transmission channel is transferred to the baseband and the channel is modelled using a complex baseband transfer function and a complex impulse response. Thus the whole examination can be performed by studying the baseband system.
  • the aim of the present invention is to remove the disadvantages hampering the above- described techniques and to provide an entirely novel type of method and apparatus for processing a signal in a telecommunication apparatus.
  • the invention is based on the equalizer correcting the fixed part H(z) being transferred to the transmitting end of the apparatus.
  • the invention provides considerable benefits.
  • Radio-frequency interference is effectively filtered without hampering reception.
  • Fig. 1 illustrates a prior-art adaptive equalizer.
  • Fig. 2 illustrates another prior-art equalizer.
  • Fig. 3 illustrates a third prior-art equalizer.
  • Fig. 4 shows an apparatus according to the invention.
  • Fig. 5 shows another alternative apparatus according to the invention.
  • Fig. 6 depicts a third alternative apparatus in accordance with the invention.
  • Fig. 7 illustrates an alternative solution according to the invention to the solution of Fig. 5.
  • Fig. 8 illustrates an alternative solution according to the invention to the solution of Fig. 6.
  • Z transformation is used to describe transfer functions at the frequency domain.
  • the following reference numerals are used in the following description to refer to components of the invention or other relevant components.
  • Receiver band stop filter 15 Linear adaptive equalizer 16
  • Fig. 1 shows a commonly known adaptive DFE equalizer (cf, e.g., Ill, p. 474) where the adaptive equalizer comprises a linear section 16 (1/G,(z)) and a feedback section 30 (1 - G 2 (z)) which together equalize the transfer function G,(z)G 2 (z) of channel 10.
  • the transfer function G,(z)G 2 (z) also contains the fixed filters of the transmitter 50 and the receiver 60.
  • the bit stream 45 entering the transmitter is grouped into groups having a length of N bits and these groups of bits are described as one- or two-dimensional symbols. Hereby one symbol conveys N bits of information.
  • the transmitter 50 and the receiver 60 are not separately described but it will be obvious to a person skilled in the art that they are located on both sides of the channel 10, in this presentation such that the transmitter 50 is mainly described on the left-hand side of the figures, the arrows which represent the flow of information progressing from the transmitter 50 towards the receiver 60.
  • Fig. 2 shows a commonly known construction making use of Tomlinson precoding.
  • the feedback coupled transfer function 30 (1-G 2 (z)) contained in the coder 1 of the transmitter corrects the section G 2 (z) in the transfer function of the channel 10.
  • the feedback loop contains a modulo-operation 25 by means of which the transmission power of the transmitter can be kept constant in spite of the feedback.
  • Using a modulo- operation 25 requires the use of a so called expanded sheer 26 in the receiver.
  • Tomlinson coding and the use of an expanded sheer is a commonly known method which is described, among other sources, in reference III (p. 460 to 464).
  • band stop filters 14 and 15 are added to the transmitter and the receiver, said filters filtering the signal power of both a transmitted and a received signal at frequencies where the modem may interfere with external radio receivers or where the modem receiver may be interfered with when a signal transmitted by external radio transmitters is connected to a line coupled to the receiver.
  • the transfer function of the channel is indicated by G(z).
  • the band stop filter 15 of the receiver may contain the transfer function H 2 (z) of an analogue filter and the transfer function H 3 (z) of a digital filter.
  • the analog section H 2 (z) is a baseband equivalent of the transfer function of the actual analog filter, because this transfer function is reflected via a frequency modulation in the QAM demodulation or CAP filtering of the receiver. In baseband modems the transfer function H 2 (z) directly corresponds to the transfer function of the analog filter.
  • Hj(z) is the transfer function of the band stop filter at the transmission end.
  • Fig. 3 The construction of Fig. 3 is a functional system as such.
  • the adaptive equalizers 16 (F j (z)) and 30 (1-F 2 (z)) now have to equalize not only the distortion caused by the channel but also the transfer function H,(z)H 2 (z)H 3 (z) caused by the band stop filters 14 and 15. Below, this transfer function is labelled H(z).
  • H(z) As H(z) is in practice of narrow bandwidth, the equalizers F,(z) and 1-F 2 (z) (in practice adaptive FIR filters) must be made of very long duration, whereby their implementation becomes difficult to calculate.
  • a filter which compensates band stop filters could be implemented by means of a fixed filter which would be connected in cascade with the adaptive feedback equalizer.
  • the shared transfer function of the feedback equalizer would then be l-F 2 (z)H(z) where F 2 is the adaptively controlled section and H the fixed section. It is known, however, that controlling the adaptive section would be very problematic with such a cascade connection. In addition, it is known that using trellis coding would be very difficult if the receiver equalizer were to contain a feedback section.
  • the above-described system can be improved by transferring the fixed equalizer which equalizes the H(z) section to the transmission end in accordance with Fig. 4.
  • a modulo-operation 25 has been added to the mechanism 2 in the manner of a Tomlinson coder.
  • I I p. 574 to 576
  • an outgoing signal is filtered using a band stop filter and the effect of said filter is corrected using Tomlinson coding such that the operation of the receiver is not hampered.
  • the method is expanded such that even the band stop filters in the receiver are "corrected" by means of the Tomlinson coding 2 at the transmitting end, whereby the band stop filters 14 and 15 do not hamper the operation of the line equalizer of the receiver.
  • the feedback section 30 (1-F 2 (z)) of the equalizer of the receiver in Fig. 4 can be transferred to the transmitter to form part of the feedback filter chain of the Tomlinson coder.
  • Fig. 5 illustrates this method where the filter F 2 (z) is transferred to form part of the feedback filter chain of the transmitter, the transfer function of the feedback filter 3 hereby being l-H 1 (z)H 2 (z)H 3 (z)F 2 (z).
  • the receiver then only contains the linear equalizer 16 in front of the sheer 26, this making the use of channel coding possible. That it is very difficult to use channel coding if the receiver equalizer contains a feedback section is generally known (e.g. Ill, p. 464).
  • the implementation of the feedback filter in the transmitter of Fig. 5 is often easier if the filter is divided into smaller blocks in cascade connection in accordance with block 4 in Fig. 6.
  • the transfer functions of the filters of the transmitters in Figs. 5 and 6 are the same if the effect of the modulo-operation is not taken into account.
  • the modulo- operation cannot be carried out in accordance with the original Tomlinson coder; instead, a modified method is shown in Fig. 6.
  • the aim is, as in Tomlinson coding, to keep the signal 5 level within the limits -M and M, where M is associated with the signal geometry used such that the relative values of the coordinates of the points in said geometry are
  • the mechanism depicted in Fig. 6 operates as follows: a) taking the next symbol value from the symbol description block b) calculating a filter chain whereby a value is obtained for the signal 5 c) checking in the level control block 6 whether the signal 5 is between the limits - M and +M, and if not, the adder 7 is used to sum a value kM into the input to the filter, where k is a positive or negative integer, such that the signal 5 after this correction is within the target limits -M and M d) a signal containing the correction term kM calculated above is taken to the feedback connections 8a, 8b, 8c and 5 of the filter; then the correction term is contained in the output signal 5 of the entire filter, keeping it within the desired limits, and in signals fed to the feedback connections of all partial filters. If two-dimensional signal geometry is used, the above-described level control must be performed separately for both coordinates.
  • the above-described mechanism requires that an expanded detector be used in the receiver.
  • This expanded detector is similar to the expanded detector used with the original Tomlinson coder.
  • Figs. 5 and 6 can be simplified in accordance with Figs. 7 and 8 by either modifying the digital band stop filter H,(z) of the transmitter or the digital band stop filter H 3 (z) of the receiver such that it is of greater width than the other filters, such that the transfer function of this wider filter alone (with a certain accuracy) determines the transfer function which is common to all band stop filters. Then, if e.g. the stop band of Hj(z) is modified such that it is wider than the others, the following is true:
  • the feedback filter of the transmitter is simplified because the section incorporating H 2 (z) and H 3 (z) can be omitted whereby the filter merely contains H,(z).
  • the method further provides the benefit that the implementation tolerances of the analog band stop filter do not pose problems, if the above condition (1) is met with sufficient accuracy even within the scope of the variations due to the inaccuracy of the components of the analog filter.
  • Reference III Edward A. Lee, David G. Messerschmitt: Digital Communication, Kluwer Academic Publishers.

Landscapes

  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Physics & Mathematics (AREA)
  • Spectroscopy & Molecular Physics (AREA)
  • Power Engineering (AREA)
  • Cable Transmission Systems, Equalization Of Radio And Reduction Of Echo (AREA)
  • Digital Transmission Methods That Use Modulated Carrier Waves (AREA)

Abstract

L'invention concerne un procédé et un appareil de traitement d'un signal dans un appareil de télécommunication. Dans le procédé selon l'invention, le signal est transmis à un canal de télécommunication (10), le signal étant traité avec un égaliseur de réception adaptatif linéaire (16) et éventuellement un égaliseur adaptatif à décision rétroactive (30). Selon l'invention, l'égalisation (H(z)) des sections des filtres coupe-bande fixes (14, 15) situés dans l'émetteur (50) et le récepteur (60) s'effectue à l'extrémité d'émetteur (50) avant le filtrage par filtre coupe-bande (14) de l'émetteur (50).
EP98917151A 1997-04-24 1998-04-21 Procede et appareil pour le traitement d'un signal dans un appareil de telecommunication Expired - Lifetime EP0978183B1 (fr)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
FI971760A FI104024B (fi) 1997-04-24 1997-04-24 Menetelmä ja laitteisto signaalin käsittelemiseksi tietoliikennelaitteistossa
FI971760 1997-04-24
PCT/FI1998/000353 WO1998048545A2 (fr) 1997-04-24 1998-04-21 Procede et appareil de traitement d'un signal dans un appareil de telecommunication

Publications (2)

Publication Number Publication Date
EP0978183A2 true EP0978183A2 (fr) 2000-02-09
EP0978183B1 EP0978183B1 (fr) 2007-07-18

Family

ID=8548720

Family Applications (1)

Application Number Title Priority Date Filing Date
EP98917151A Expired - Lifetime EP0978183B1 (fr) 1997-04-24 1998-04-21 Procede et appareil pour le traitement d'un signal dans un appareil de telecommunication

Country Status (5)

Country Link
EP (1) EP0978183B1 (fr)
AU (1) AU7046198A (fr)
DE (1) DE69838096T2 (fr)
FI (1) FI104024B (fr)
WO (1) WO1998048545A2 (fr)

Families Citing this family (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
AU2216701A (en) * 1999-12-30 2001-07-16 Tioga Technologies Inc. Data transceiver with filtering and precoding
US6879639B1 (en) 1999-12-30 2005-04-12 Tioga Technologies Inc. Data transceiver with filtering and precoding
FI107307B (fi) 2000-01-18 2001-06-29 Tellabs Oy Menetelmä ja laitteisto kanavakorjauksen tekemiseksi digitaalisella tietoliikenneyhteydellä
US6885699B2 (en) 2000-07-24 2005-04-26 Stmicroelectronics Ltd. Semi-stationary quiescent mode transmission
FI108323B (fi) * 2000-08-14 2001-12-31 Tellabs Oy Menetelmä ja laitteisto itsekompensoivan kaistanestosuodattimen toteuttamiseksi digitaalisella tietoliikenneyhteydellä
US7599431B1 (en) * 2004-11-24 2009-10-06 Xilinx, Inc. Combined decision feedback equalization and linear equalization

Family Cites Families (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CA2153641A1 (fr) * 1995-07-11 1997-01-12 Mark R. Gibbard Systeme et methode de communication numeriques

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
See references of WO9848545A3 *

Also Published As

Publication number Publication date
EP0978183B1 (fr) 2007-07-18
FI104024B1 (fi) 1999-10-29
DE69838096T2 (de) 2007-11-22
WO1998048545A3 (fr) 1999-01-21
AU7046198A (en) 1998-11-13
FI971760A0 (fi) 1997-04-24
DE69838096D1 (de) 2007-08-30
FI104024B (fi) 1999-10-29
WO1998048545A2 (fr) 1998-10-29
FI971760A (fi) 1998-10-25

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