EP0696793B1 - Codeur de parole - Google Patents

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Publication number
EP0696793B1
EP0696793B1 EP95112594A EP95112594A EP0696793B1 EP 0696793 B1 EP0696793 B1 EP 0696793B1 EP 95112594 A EP95112594 A EP 95112594A EP 95112594 A EP95112594 A EP 95112594A EP 0696793 B1 EP0696793 B1 EP 0696793B1
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European Patent Office
Prior art keywords
speech
codevector
signal
excitation
codebook
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EP95112594A
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German (de)
English (en)
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EP0696793A3 (fr
EP0696793A2 (fr
Inventor
Shin-Ichi C/O Nec Corporation Taumi
Masahiro C/O Nec Corporation Serizawa
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NEC Corp
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NEC Corp
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    • G—PHYSICS
    • G10—MUSICAL INSTRUMENTS; ACOUSTICS
    • G10L—SPEECH ANALYSIS OR SYNTHESIS; SPEECH RECOGNITION; SPEECH OR VOICE PROCESSING; SPEECH OR AUDIO CODING OR DECODING
    • G10L19/00—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis
    • G10L19/04—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis using predictive techniques
    • G10L19/06—Determination or coding of the spectral characteristics, e.g. of the short-term prediction coefficients
    • G10L19/07—Line spectrum pair [LSP] vocoders
    • G—PHYSICS
    • G10—MUSICAL INSTRUMENTS; ACOUSTICS
    • G10L—SPEECH ANALYSIS OR SYNTHESIS; SPEECH RECOGNITION; SPEECH OR VOICE PROCESSING; SPEECH OR AUDIO CODING OR DECODING
    • G10L19/00—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis
    • G10L19/04—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis using predictive techniques
    • G10L19/08—Determination or coding of the excitation function; Determination or coding of the long-term prediction parameters
    • G10L19/10—Determination or coding of the excitation function; Determination or coding of the long-term prediction parameters the excitation function being a multipulse excitation
    • G—PHYSICS
    • G10—MUSICAL INSTRUMENTS; ACOUSTICS
    • G10L—SPEECH ANALYSIS OR SYNTHESIS; SPEECH RECOGNITION; SPEECH OR VOICE PROCESSING; SPEECH OR AUDIO CODING OR DECODING
    • G10L19/00—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis
    • G10L2019/0001—Codebooks
    • G10L2019/0003—Backward prediction of gain
    • G—PHYSICS
    • G10—MUSICAL INSTRUMENTS; ACOUSTICS
    • G10L—SPEECH ANALYSIS OR SYNTHESIS; SPEECH RECOGNITION; SPEECH OR VOICE PROCESSING; SPEECH OR AUDIO CODING OR DECODING
    • G10L19/00—Speech or audio signals analysis-synthesis techniques for redundancy reduction, e.g. in vocoders; Coding or decoding of speech or audio signals, using source filter models or psychoacoustic analysis
    • G10L2019/0001—Codebooks
    • G10L2019/0007—Codebook element generation

Definitions

  • the present invention relates to a speech coder for coding a speech signal in high quality at low bit rate, particularly 4.8 kb/s and below.
  • CELP code-excited LPC coding
  • spectrum parameters representing a spectral characteristic of the speech signal are extracted for each frame (of 20 ms, for instance) therefrom through LPC (linear prediction) analysis.
  • the frame is divided into a plurality of sub-frames (of 5 ms, for instance), and adaptive codebook parameters (i.e., a delay parameter corresponding to the pitch cycle and a gain parameter) are extracted for each sub-frame on the basis of past excitation signal.
  • adaptive codebook parameters i.e., a delay parameter corresponding to the pitch cycle and a gain parameter
  • the excitation codevector is selected in such a manner as to minimize an error power between the signal synthesized from the selected noise signal and the above residual signal.
  • the index representing the kind of the selected codevector and the gain are transmitted in combination with the spectrum parameters and adaptive codebook parameters by a multiplexer. The receiving side is not described.
  • a sparse excitation codebook is utilized.
  • the prior art sparse excitation codebook as shown in Fig. 5, features in that in all of its codevectors the number of non-zero elements is fixed (i.e., nine, for instance).
  • the prior art sparse codebook generation is taught in, for instance, Gercho et al, Japanese Patent Laid-Open Publication No. 13199/1989 (hereinafter referred to as Literature 2).
  • FIG. 6 A flow chart of the prior art sparse excitation codebook generation is shown in Fig. 6.
  • a desired initial excitation signal for instance a random number signal
  • the excitation codebook is trained a desired number of times using the well-known LBG process.
  • the finally trained excitation codebook in the LBG process training in the step 3020 is taken out.
  • each codevector in the finally trained excitation codebook taken out in the step 3030 is center clipped using a certain threshold value.
  • LBG process see, for instance, Y. Linde, A. Buzo, R. M. Gray et al, "An Algorithm for Vector Quantizer Design", IEEE Trans. Commun., Vol. COM-28, pp. 84-95, Jan. 1980.
  • split-Band APC System for low bit-rate encoding of Speech discloses a split-band adaptive predictive coding system for digital transmission of speech signals.
  • the prediction residue signal obtained after spectral prediction is filtered into 2 or more frequency bands.
  • Each of the filtered signals is reduced further by pitch prediction and is quantized by a 15-level noise feedback quantizer.
  • the input to the quantizer is severely center-clipped to produce a quantized signal with low entropy.
  • the division of the prediction residue signal into many frequency bands results in more accurate pitch prediction - particularly, at low frequencies.
  • the split-band system uses separate quantizers for each frequency band. The step size of the quantizer and the center-clipping threshold can be adjusted to optimize speech quality in each band.
  • An object of the present invention is to solve the above problems and provide a speech coder capable of generating optimum codevectors and reducing the storage amount and operation amount.
  • a speech coder for coding an excitation signal obtained by removing spectrum information from a speech signal by referring an excitation codebook comprising a plurality of codevectors each having time-positions and amplitudes of non-zero elements, by selecting the most similar codevector to the excitation signal and transmitting an index of the selected codevector, wherein said time-positions of non-zero elements are determined so as to reduce a distance between a speech vector obtained based on the selected codevector and a speech vector having the same length as the codevector obtained by cutting out a previously predetermined training speech signal and then amplitudes of the non-zero elements are determined .
  • a speech coder for coding an excitation signal obtained by removing spectrum information from a speech signal by referring an excitation codebook comprising a plurality of codevectors each having time-positions and amplitudes of non-zero elements, by selecting the most similar codevector to the excitation signal and transmitting an index of the selected codevector, wherein said time-positions of non-zero elements are determined so as to reduce a distance between a speech vector obtained based on the selected codevector and a speech vector having the same length as the codevector obtained by cutting out a previously predetermined training speech signal and then amplitudes of the non-zero elements are determined, and at least two of the codevectors have different numbers of non-zero elements.
  • Fig. 1 shows an embodiment of a speech coder with non-uniform pulse number type sparse excitation codebook according to the present invention
  • Fig. 2 shows a non-uniform pulse type sparse excitation codebook 351 in Fig. 1;
  • Fig. 3 is a flow chart for explaining the production of a non-uniform pulse number type sparse excitation codebook, in which the non-zero elements in the individual codevectors are no greater than P in number;
  • Fig. 4 is a flow chart for explaining a different example of operation
  • Fig. 5 shows the prior art sparse excitation codebook
  • Fig. 6 shows the prior art speech coder using the sparse excitation codebook
  • Fig. 7 shows usual excitation codevector having some elements of very small amplitudes.
  • An input speech signal divider 110 is connected to an acoustical sense weighter 230 through a spectrum parameter calculator 200 and a frame divider 120.
  • the spectrum parameter calculator 200 is connected to a spectrum parameter quantizer 210, the acoustical sense weighter 230, a response signal calculator 240 and a weighting signal calculator 360.
  • An LSP codebook 211 is connected to the spectrum parameter quantizer 210.
  • the spectrum parameter quantizer 210 is connected to the acoustical sense weighter 230, the response signal calculator 240, the weighting signal calculator 360, an impulse response calculator 310, and a multiplexer 400.
  • the impulse response calculator 310 is connected to an adaptive codebook circuit 500, an excitation quantizer 350 and a gain quantizer 365.
  • the acoustical sense weighter 230 and response signal calculator 240 are connected via a subtractor 235 to the adaptive codebook circuit 500.
  • the adaptive codebook 500 is connected to the excitation quantizer 350, the gain quantizer 365 and multiplexer 400.
  • the excitation quantizer 350 is connected to the gain quantizer 365.
  • the gain quantizer 365 is connected to the weighting signal calculator 360 and multiplexer 400.
  • a pattern accumulator 510 is connected to the adaptive codebook circuit 500.
  • a non-uniform sparse type excitation codebook 351 is connected to the excitation quantizer 350.
  • a gain codebook 355 is connected to a gain quantizer 365.
  • speech signals from an input terminal 100 are divided by the input speech signal divider 110 into frames (of 40 ms, for instance).
  • the sub-frame divider 120 divides the frame speech signal into sub-frames (of 8 ms, for instance) shorter than the frame.
  • the spectrum parameter is changed greatly with time particularly in a transition portion between a consonant and a vowel. This means that the analysis is preferably made at as short interval as possible. With reducing interval of analysis, however, the amount of operations necessary for the analysis is increased.
  • the spectrum parameters used are obtained through linear interpolation, on LSP to be described later, between the spectrum parameters of the 1st and 3rd sub-frames and between those of the 3rd and 5th sub-frames.
  • the spectrum parameter may be calculated through well-known LPC analysis, Burg analysis, etc. Here, Burg analysis is employed. The Burg analysis is described in detail in Nakamizo, "Signal Analysis and System Identification", Corona Co., Ltd., 1988, pp. 82-87.
  • the spectrum parameter quantizer 210 efficiently quantizes LSP parameters of predetermined sub-frames. It is hereinafter assumed that the vector quantization is employed and the quantization of the 5th sub-frame LSP parameter is taken as example.
  • the vector quantization of LSP parameters may be made by using well-known processes. Specific examples of process are described in, for instance, the specifications of Japanese Patent Application No. 171500/1992, 363000/1992 and 6199/1993 (hereinafter referred to as Literatures 3) as well as T. Nomura et al, "LSP Coding Using VQ-SVQ with Interpolation in 4.075 kb/s M-LCELP Speech Coder", Proc. Mobile Multimedia Communications, 1993, pp.
  • the spectrum parameter quantizer 210 restores the 1st to 4th sub-frame LSP parameters from the 5th sub-frame quantized LSP parameter.
  • the 1st to 4th sub-frame LSP parameters are restored through linear interpolation of the 5th sub-frame quantized LSP parameter of the prevailing frame and the 5th sub-frame quantized LSP parameter of the immediately preceding frame.
  • LSP interpolation patterns for a predetermined number of bits (for instance, two bits), restore 1st to 4th sub-frame LSP parameters for each of these patterns and select a set of codevector and interpolation pattern for minimizing the accumulated distortion.
  • the transmitted information is increased by an amount corresponding to the interpolation pattern bit number, but it is possible to express the LSP parameter changes in the frame with time.
  • the interpolation pattern may be produced in advance through training based on the LSP data.
  • predetermined patterns may be stored.
  • the predetermined patterns it may be possible to use those described in, for instance, T. Taniguchi et al, "Improved CELP Speech Coding at 4kb/s and Below", Proc. ICSLP, 1992, pp. 41-44.
  • an error signal between true and interpolated LSP values may be obtained for a predetermined sub-frame after the interpolation pattern selection, and the error signal may further be represented with an error codebook.
  • Literatures 3 for instance.
  • the response signal calculator 240 receives for each sub-frame the linear prediction coefficient ⁇ ij from the spectrum parameter calculator 200 and also receives for each sub-frame the linear prediction coefficient ⁇ ' ij restored through the quantization and interpolation from the spectrum parameter quantizer 210.
  • the response signal x z (N) is expressed by Equation (1).
  • ⁇ is a weighting coefficient for controlling the amount of acoustical sense weighting and has the same value as in Equation (3) below
  • the subtractor 235 subtracts the response signal from the acoustical sense weighted signal for one sub-frame as shown in Equation (2), and outputs x w '(n) to the adaptive codebook circuit 500.
  • x w '(n) x w (n) - x z (n)
  • the impulse response calculator 310 calculates, for a predetermined number L of points, the impulse response hw(n) of weighting filter with z conversion thereof given by Equation (3) and supplies hw(n) to the adaptive codebook circuit 500 and excitation quantizer 350.
  • the adaptive codebook circuit 500 derives the pitch parameter.
  • Literature 1 may be referred to.
  • the circuit 500 further makes the pitch prediction with adaptive codebook as shown in Equation (4) to output the adaptive codebook prediction error signal z(n).
  • z(n) x w '(n ) - b(n)
  • b(n) is an adaptive codebook pitch prediction signal given as:
  • b(n) ⁇ v(n - T) h w (n) where ⁇ and T are the gain and delay of the adaptive codebook.
  • the adaptive codebook is represented as v(n).
  • the non-uniform pulse type sparse excitation codebook 351 is as shown in Fig. 2, a sparse codebook having different numbers of non-zero components of the individual vectors.
  • Fig. 3 is a flow chart for explaining the production of a non-uniform pulse number type sparse excitation codebook, in which the non-zero elements in the individual codevectors are no greater than P in number.
  • the codebooks to be produced are expressed as Z(1), Z(2), ..., Z(CS) wherein CS is a codebook size. Distortion distance used for the production is shown in Equation (6).
  • S training data cluster
  • Z is codevector of S
  • w t training data contained in S
  • g t is optimum gain
  • H wt is the impulse response of weighting filter.
  • Equation (7) gives the summation for all the cluster training data and codevectors thereof in Equation (6).
  • Equations (6) and (7) are only an example, and various other Equations are conceivable.
  • a step 1010 the determination of the optimum pulse position of the 1st codevector Z(1) is declared.
  • a step 1020 the optimum pulse position of the Mth codevector Z(M) is declared.
  • pulse number N, dummy codevector V and distortion thereof and the training data are initialized.
  • a step 1040 a dummy codevector V(N) having N optimum pulse positions is produced. Also, distortion D(N) of V(N) and the training data is obtained.
  • a step 1050 a decision is made as to whether the pulse number of V(N) last is to be increased.
  • the condition A in the step 1050 is adapted for the training.
  • a step 1060 the optimum pulse position of Z(M) is determined as that of V(N).
  • a step 1070 the optimum pulse positions of all of Z(1), Z(2), ..., Z (CS) are determined.
  • the pulse amplitudes of all of Z(1), Z(2), ..., Z (CS) are obtained as optimum values of the same order by using Equation (7).
  • Equation (7) the pulse amplitudes of all of Z(1), Z(2), ..., Z (CS) are obtained as optimum values of the same order by using Equation (7).
  • Fig. 4 is a flow chart for explaining a different example of operation.
  • a step 2010 the determination of the optimum pulse position of the 1st codevector Z(1) is declared.
  • a step 2020 the determination of the optimum pulse position of the Mth codevector Z(M) is declared.
  • a step 2030 pulse number N and dummy codevector V are initialized.
  • dummy codevector V(N) having N optimum pulse positions is produced.
  • a decision is made as to whether the pulse number of V(N) is to be increased.
  • the optimum pulse positions of all of Z(1), Z(2), ..., Z (CS) are determined.
  • a step 2080 the pulse amplitudes of all of Z(1), Z(2), ..., Z (CS) are obtained as optimum values of the same order by using Equation (7). Only at the time of the last training, a step 2090 is executed to produce a non-uniform pulse number codebook. In the flow of Fig. 4, it is possible to add the step 2090 in all the studies.
  • Equation (8) When applying Equation (8) only to some codevectors, a plurality of excitation codevectors are preliminarily selected. Equation (8) may be applied to the preliminarily selected excitation codevectors as well.
  • the gain quantizer 365 reads out the gain codevector from the gain codebook 355 and selects a set of the excitation codevector and the gain codevector for minimizing Equation (9) for the selected excitation codevector.
  • D j,k ⁇ n (x w (n)- ⁇ k 'v(n-T)h w (n)- ⁇ k 'c j (n) h w (n)) 2
  • ⁇ ' k and ⁇ ' k represent the kth codevector in a two-dimensional codebook stored in the gain codebook 355.
  • Impulses representing the selected excitation codevector and gain codevector are supplied to the multiplexer 400.
  • the weighting signal calculator 360 receives the output parameters and indexes thereof from the spectrum parameter calculator 200, reads out codevectors in response to the index, and develops a driving excitation signal v(n) based on Equation (10).
  • v(n) ⁇ k 'v(n-T)+ ⁇ k 'cj(n)
  • a weighting signal sw(n) is calculated for each sub-frame based on Equation (11) and is supplied to the response signal calculator 240.
  • the CELP speech coder by varying the number of non-zero elements of each vector for obtaining the same characteristic, it is possible to remove small amplitude elements providing less contribution to restored speech and thus reduce the number of elements. It is thus possible to reduce codebook storage amount and operation amount, which is a very great advantage.
  • the small amplitude elements with less contribution to the reproduced speech can be removed by varying the number of non-zero elements in each vector.
  • the number of elements can be reduced to reduce the codebook storage amount and operation amount.

Claims (3)

  1. Codeur vocal destiné à coder un signal d'excitation obtenu en extrayant des informations de spectre d'un signal vocal en se référant à un livre du code d'excitation comprenant une pluralité de vecteurs codés ayant chacun des positions et des amplitudes de temps et des amplitudes d'éléments différents de zéro, en choisissant le vecteur codé le plus identique au signal d'excitation et en transmettant un index du vecteur codé choisi, dans lequel les positions de temps des éléments différents de zéro sont déterminées de manière à réduire une distance entre un vecteur vocal obtenu en se basant sur le vecteur codé choisi et un vecteur vocal ayant la même longueur que le vecteur obtenu en réduisant un signal vocal de simulation prédéterminé précédemment et les amplitudes des éléments différents de zéro sont par la suite déterminées.
  2. Codeur vocal selon la revendication 1, dans lequel au moins deux des vecteurs codés ont des numéros différents d'éléments différents de zéro.
  3. Codeur vocal selon la revendication 1 ou 2, dans lequel le nombre d'éléments différents de zéro dudit vecteur codé est déterminé en se basant sur une qualité vocale prédéterminée de parole reproduite ou sur une somme de calcul prédéterminé du codage.
EP95112594A 1994-08-11 1995-08-10 Codeur de parole Expired - Lifetime EP0696793B1 (fr)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
JP18961294A JP3179291B2 (ja) 1994-08-11 1994-08-11 音声符号化装置
JP18961294 1994-08-11
JP189612/94 1994-08-11

Publications (3)

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EP0696793A2 EP0696793A2 (fr) 1996-02-14
EP0696793A3 EP0696793A3 (fr) 1997-12-17
EP0696793B1 true EP0696793B1 (fr) 2001-11-21

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EP95112594A Expired - Lifetime EP0696793B1 (fr) 1994-08-11 1995-08-10 Codeur de parole

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US (1) US5774840A (fr)
EP (1) EP0696793B1 (fr)
JP (1) JP3179291B2 (fr)
CA (1) CA2155583C (fr)
DE (1) DE69524002D1 (fr)

Families Citing this family (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6393391B1 (en) * 1998-04-15 2002-05-21 Nec Corporation Speech coder for high quality at low bit rates
EP1553564A3 (fr) * 1996-08-02 2005-10-19 Matsushita Electric Industrial Co., Ltd. Codec vocal, support sur lequel est enregistré un programme codec vocal, et appareil mobile de télécommunications
CA2213909C (fr) * 1996-08-26 2002-01-22 Nec Corporation Codeur de paroles haute qualite utilisant de faibles debits binaires
US6144853A (en) * 1997-04-17 2000-11-07 Lucent Technologies Inc. Method and apparatus for digital cordless telephony
US6546241B2 (en) * 1999-11-02 2003-04-08 Agere Systems Inc. Handset access of message in digital cordless telephone
DE60137359D1 (de) * 2000-11-30 2009-02-26 Nippon Telegraph & Telephone Vektorquantisierungseinrichtung für lpc-parameter
FI119955B (fi) * 2001-06-21 2009-05-15 Nokia Corp Menetelmä, kooderi ja laite puheenkoodaukseen synteesi-analyysi puhekoodereissa
US20080097757A1 (en) * 2006-10-24 2008-04-24 Nokia Corporation Audio coding

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Publication number Priority date Publication date Assignee Title
US4868867A (en) * 1987-04-06 1989-09-19 Voicecraft Inc. Vector excitation speech or audio coder for transmission or storage
JPS63316100A (ja) * 1987-06-18 1988-12-23 松下電器産業株式会社 マルチパルス探索器
JP3114197B2 (ja) * 1990-11-02 2000-12-04 日本電気株式会社 音声パラメータ符号化方法
JP2776050B2 (ja) * 1991-02-26 1998-07-16 日本電気株式会社 音声符号化方式
JP3151874B2 (ja) * 1991-02-26 2001-04-03 日本電気株式会社 音声パラメータ符号化方式および装置
US5396576A (en) * 1991-05-22 1995-03-07 Nippon Telegraph And Telephone Corporation Speech coding and decoding methods using adaptive and random code books
JP3143956B2 (ja) * 1991-06-27 2001-03-07 日本電気株式会社 音声パラメータ符号化方式
JP3338074B2 (ja) * 1991-12-06 2002-10-28 富士通株式会社 音声伝送方式
JPH06209262A (ja) * 1993-01-12 1994-07-26 Hitachi Ltd 駆動音源コードブックの設計法
JP2746039B2 (ja) * 1993-01-22 1998-04-28 日本電気株式会社 音声符号化方式
US5598504A (en) * 1993-03-15 1997-01-28 Nec Corporation Speech coding system to reduce distortion through signal overlap

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Publication number Publication date
EP0696793A3 (fr) 1997-12-17
EP0696793A2 (fr) 1996-02-14
CA2155583A1 (fr) 1996-02-12
US5774840A (en) 1998-06-30
CA2155583C (fr) 2000-03-21
DE69524002D1 (de) 2002-01-03
JPH0854898A (ja) 1996-02-27
JP3179291B2 (ja) 2001-06-25

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