EP0530072B1 - Procédé et dispositif de commande et régulation - Google Patents

Procédé et dispositif de commande et régulation Download PDF

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Publication number
EP0530072B1
EP0530072B1 EP92402262A EP92402262A EP0530072B1 EP 0530072 B1 EP0530072 B1 EP 0530072B1 EP 92402262 A EP92402262 A EP 92402262A EP 92402262 A EP92402262 A EP 92402262A EP 0530072 B1 EP0530072 B1 EP 0530072B1
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EP
European Patent Office
Prior art keywords
value
magnitude
input
output
parameter
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
EP92402262A
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German (de)
English (en)
French (fr)
Other versions
EP0530072A1 (fr
Inventor
Laurent Cariou
Joel Cordier
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Thales SA
Original Assignee
Thomson CSF SA
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Publication of EP0530072A1 publication Critical patent/EP0530072A1/fr
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    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
    • G05F1/00—Automatic systems in which deviations of an electric quantity from one or more predetermined values are detected at the output of the system and fed back to a device within the system to restore the detected quantity to its predetermined value or values, i.e. retroactive systems
    • G05F1/10—Regulating voltage or current
    • G05F1/46—Regulating voltage or current wherein the variable actually regulated by the final control device is dc
    • G05F1/56—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices
    • G05F1/565—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices sensing a condition of the system or its load in addition to means responsive to deviations in the output of the system, e.g. current, voltage, power factor
    • G05F1/567—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices sensing a condition of the system or its load in addition to means responsive to deviations in the output of the system, e.g. current, voltage, power factor for temperature compensation
    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
    • G05F1/00—Automatic systems in which deviations of an electric quantity from one or more predetermined values are detected at the output of the system and fed back to a device within the system to restore the detected quantity to its predetermined value or values, i.e. retroactive systems
    • G05F1/10—Regulating voltage or current
    • G05F1/46—Regulating voltage or current wherein the variable actually regulated by the final control device is dc
    • G05F1/462—Regulating voltage or current wherein the variable actually regulated by the final control device is dc as a function of the requirements of the load, e.g. delay, temperature, specific voltage/current characteristic
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
    • Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10S323/00—Electricity: power supply or regulation systems
    • Y10S323/907—Temperature compensation of semiconductor

Definitions

  • the invention relates to methods and devices intended to control using a first quantity y a second quantity x, this second quantity being itself for each of the values of the quantity x a known function of a parameter h that we don't control.
  • the method and the device according to the invention are applicable whenever a point of abscissa h of the curve representing a second value y 2 (h) can be deduced from the point of the same abscissa h of the curve representing a first value y 1 (h) by adding a value which is a linear function of h.
  • the invention can be extended to an initial control quantity Y one-to-one function of the quantity y, controlling a value X one-to-one function of the variable x.
  • the functions Y (y) , X (x) and Y (X) are not necessarily linear.
  • the invention relates in particular, but not exclusively, to a voltage control intended to bias a diode with an intrinsic zone in current.
  • the first quantity y is a control voltage U
  • the controlled value x is the bias current I of the intrinsic zone diode
  • the parameter h influencing the value of the current is the temperature T of the diode.
  • the embodiments according to the known art do not make it possible to obtain commands for the bias current I of the intrinsically-zone diode that are well regulated in temperature and having switching times between two very short command values.
  • the embodiments according to the prior art either the order is well temperature regulated but then the switching times are long, or the temperature regulation is ineffective.
  • Another object of the invention is to be able to supply this command and this regulation over a wide range of values of the quantity x and over a wide range of variations of the parameter h.
  • Another object of the invention is to allow this command between a minimum value x m and a maximum value x M with a large number of control steps.
  • a zero value will be applied to the other input if the value of the parameter h is effectively equal to h i and which will otherwise be equal to a value which is a function of the difference between the real value of the parameter h r and the reference value h i .
  • the value applied to the other input will be equal to H (hr-hi) , H (hr-hi) being the value of the correction to be applied to U i to obtain the value x i when h is not equal to h i but at h r .
  • H (hr-hi) being the value of the correction to be applied to U i to obtain the value x i when h is not equal to h i but at h r .
  • the method and the device according to the invention are particularly well suited when the change in the control voltage U i results in self-regulation as a function of the parameter h of a part of the means ensuring the correction H (hr-hi) .
  • a particularly simple embodiment of the invention is obtained when the laws of variation of y as a function of the parameter h are linear.
  • the sensor of the quantity h can be a linear sensor, the slope of the output quantity of the sensor as a function of h being of equal value and of sign opposite to one of the slopes of y p as a function of h.
  • the invention is also well suited to the case where the different functions U p (h) are arbitrary but deducible from one another by linear transformation.
  • h i designating a value of the interval h m h M a point of abscissa h of a second curve representative of y p , as a function of h is deduced from the point of the same abscissa h of a first curve representative of y p as a function of h by adding a constant term and a term proportional to the difference (hh i ).
  • the coefficient of proportionality is, when the curves are straight lines, the ratio of the slopes of the second and the first line.
  • the correction voltage can be applied by means of an operational amplifier, the gain of which is made proportional to the slope of the line representing the quantity y p as a function of the parameter h, when the controlled quantity x has the value x p .
  • the gain variation is obtained by changing the value of a resistor placed in an amplifier feedback circuit.
  • the correction voltage is the sum of two voltages, a so-called large step voltage obtained by dividing the total variation y M -y m by the number u of large steps and a so-called fine step voltage obtained by dividing the worth a big step either y M -y m u by the number v of fine steps be y M -y m uv
  • This curve shows that R is a one-to-one function of I so that the control of I leads to the control of R.
  • the control quantity "y" will be represented by the voltage U which should be applied to the input of an operational amplifier to obtain the value x represented here by the bias current of a diode connected to the output of the amplifier.
  • the parameter h is represented by the temperature T of the diode. It is known that when the temperature T of a PIN diode increases the bias voltage to be applied to the diode to obtain a constant output current I decreases.
  • D p represents the value of U as a function of T when the bias current is I p
  • D i represents the value of U when the current polarization is I i (I i > I p ).
  • D 3 be the line passing through the point A of the line D p , with coordinates T i and U i , and parallel to the line D i
  • a point on the line D i is deduced from a point on the line D 3 thus constructed by addition to the value of U represented by the line D 3 for a value of T with a constant value equal to AA i ,
  • a i being the point of the line D i with abscissa T i .
  • the line D 3 thus constructed is deduced from the line D p by addition to the value U T given by the line D p for an abscissa T of a magnitude (U - U T ) proportional to the difference between T and T i , the coefficient of proportionality being in this case the ratio of the slopes of the lines D i and D p .
  • a point of a second straight line representing U as a function of T for a constant value I is deduced well from a point of abscissa T of a first straight line by addition to the ordinate of the point of abscissa T on the first line of a constant term, here AA i and of a term proportional to the value of the abscissa difference (T - T i ), T i designating a value between the minimum temperature T m and the maximum temperature T M.
  • FIG. 4 represents a set of three curves C 1 , C 2 , C 3 , each of the curves representing the value to be given to the quantity y to keep the quantity x constant when the parameter h varied.
  • This figure represents a PIN diode 1 whose resistance R is to be controlled, therefore the current by means of a control voltage U.
  • the command and control device is constituted by means 2. This means applies to the input of an operational amplifier of great internal resistance 10 having two inputs a first 11, a second 12 and an output 13, the control voltage U, in the following manner.
  • the input 11 of this amplifier receives from a control circuit 200 a voltage U i which would be the voltage to be applied to obtain a value I i of the controlled current if the temperature of the diode had the reference value T i .
  • the input 12 of this amplifier is supplied by the output of a temperature sensor 30, this output being corrected by means 40 which receives the value of the command from the control circuit 200.
  • the sensor 30 is preferably located near the diode PIN 1 so that the temperature it senses is as close as possible to that of the diode.
  • the curves representing U as a function of T for constant I are straight lines (see Figure 2).
  • the corrections to be applied are shown in figure 6 in dotted lines.
  • the reference value T i is equal to 20 °, central value of the range -40 ° + 80 °.
  • FIG. 7 This figure is identical to Figure 5 but the device 40 has been detailed. It comprises an operational amplifier 41 comprising an output 12 and two inputs 43, 44. A feedback loop 47 brings the output voltage back to the input 43 by means of a variable resistor 46, the input 43 also receives the output voltage of the sensor 30, the variable resistor 46 is controlled by the command 200. The value of the resistor 46 is such that the gain of the operational amplifier 41 is proportional to the value of the slope of the correction line used for the value ordered.
  • the output 12 of the operational amplifier 41 is the second input of the operational amplifier 10.
  • the command 200 which controls the value of the voltage at the input of the amplifier 10 and the value of the resistor 46 placed in the counter loop reaction 47 has two parts 210 and 220 for performing each of these functions.
  • control part 210 in connection with the input 11 will now be described with reference to FIG. 8.
  • the arrival of the command is made in decibel, that is to say in logarithmic value, a first linearization would therefore be necessary to return to the value of linear attenuation.
  • the desired loss is a linear function of the value of the resistance entered to achieve the loss.
  • the resistance entered is the resistance of the PIN 1 diode, the variation curve of which as a function of I is shown in FIG. 1.
  • the control part 210 200 is produced in the following manner.
  • the input command 201 coded on 6 parallel bits 201a to 201 f is supplied with a clock signal. It therefore makes it possible to obtain 2 6, ie 64 attenuation steps distributed here between 0 and 64 decibels in steps of 1 decibel.
  • These signals are set to TTL 0.5 V standards by a D 202 flip-flop controlled by the clock signal.
  • the binary output word 203 of the flip-flop 202 which represents the input value according to TTL standards addresses two parallel circuits, one of these circuits whose reference numbers are simple represents the control of large pitch, the other whose Reference numbers are the same but with a prime sign represents the end pitch command.
  • the operation of the large pitch control will now be described.
  • the binary word 203 at the output of the flip-flop 202 addresses a programmable memory 204 whose boxes allow the storage of 8 bits.
  • the values stored in the memories make it possible to carry out a transposition achieving the linearization mentioned above. We understand that because of the linearization the width of the steps at the output of the memory is variable and that one may need very fine steps which can only be achieved by coding on a larger number of bits.
  • the output information of the addressed box of the memory 204 are resynchronized by a flip-flop D 205 and sent to a digital analog converter (ADC) 206.
  • ADC digital analog converter
  • the latter behaves like a resistor whose value changes according to the input values received .
  • the fine pitch command comprises the same elements having the same functions, namely a set of memory boxes 204 ′, a flip-flop 205 ′ and a digital analog converter 206 ′.
  • the output 11 of this amplifier is the input of the adder amplifier 10 of FIG. 7.
  • FIG. 9 represents a simplified diagram giving a synoptic view of the control and regulation assembly.
  • This figure shows that the attenuation control word 203 coming from the flip-flop 202 is sent not only to the transformation device represented in FIG. 8 by memories 204, flip-flops 205 (not represented in FIG. 9) and converters 206 but also towards an analog device 220 having an identical function constituted by a group of memories 221, a flip-flop 222 and a digital analog converter 46 which plays the role of variable resistance as explained during the description of FIG. 7.
  • the values displayed in the memories addressed by the control word 203 reproduce the image of a curve recorded during preliminary tests on a PIN 1 diode mounted, under the same conditions. They represent the values of resistors 206 respectively 46 to be displayed to obtain the controlled loss.
  • T T i the decibel attenuations by decibel up to 64 and the corresponding word on each of the coding wheels. This information is then entered on the keyboard of a programmer for each of the memories.
  • the programming of memories can also be computerized.
  • the output voltage of the temperature sensor 30 constitutes the reference voltage supplying the converter 46 and the input 43 of the operational amplifier 41. It is produced from a bare sensor and adapted for example by means of an amplifier operational so that its output voltage is equal to the supply voltage of the input 44 of the operational amplifier 41 when the temperature is equal to the reference temperature T i .
  • the adaptation is particularly simple since the curves U as a function of T are straight lines and there are sensors on the market giving a linear voltage as a function of temperature. This is why it is possible to be satisfied in this case with an adaptation by operational amplifier.
  • the adaptation may include a memory converter association to establish a corrected sensor output having the form of one of the functions y p (h).
  • the input quantity Y which is here a decibel loss
  • a value y which is here the value of the voltage U applied to the input of the operational amplifier 10 which, in turn, -same, conditions the value of a quantity x which is here the value of the output current I of the amplifier 10 which itself conditions a quantity X which is the value of the resistance of the diode PIN 1.
  • the attenuation obtained is almost constant when the temperature T varies from -20 ° to + 80 °.
  • the values obtained for a 16 dB and 37 dB command are shown in Figure 10.
  • the switching times between two commands are of the order of 200 nanoseconds.

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  • Engineering & Computer Science (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • General Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Automation & Control Theory (AREA)
  • Amplifiers (AREA)
  • Feedback Control In General (AREA)
  • Control Of Amplification And Gain Control (AREA)
EP92402262A 1991-08-23 1992-08-11 Procédé et dispositif de commande et régulation Expired - Lifetime EP0530072B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
FR9110569A FR2680587B1 (fr) 1991-08-23 1991-08-23 Procede et dispositif de commande et regulation.
FR9110569 1991-08-23

Publications (2)

Publication Number Publication Date
EP0530072A1 EP0530072A1 (fr) 1993-03-03
EP0530072B1 true EP0530072B1 (fr) 1996-09-18

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EP92402262A Expired - Lifetime EP0530072B1 (fr) 1991-08-23 1992-08-11 Procédé et dispositif de commande et régulation

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US (1) US5341287A (ja)
EP (1) EP0530072B1 (ja)
JP (1) JPH06268459A (ja)
CA (1) CA2076475A1 (ja)
DE (1) DE69213869T2 (ja)
FR (1) FR2680587B1 (ja)

Families Citing this family (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP3329077B2 (ja) * 1993-07-21 2002-09-30 セイコーエプソン株式会社 電源供給装置、液晶表示装置及び電源供給方法
FR2801681B1 (fr) 1999-11-30 2002-02-08 Thomson Csf Procede et dispositif de mesure de la temperature de composants hyperfrequence
ITTO20040411A1 (it) * 2004-06-21 2004-09-21 Olivetti Jet S P A Dispositivo di rilevamento di grandezze fisiche, particolarmente di umidita', e relativo metodo di rilevamento.
CN112764448B (zh) * 2019-11-05 2022-05-24 台达电子工业股份有限公司 过温度补偿控制电路

Family Cites Families (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3701004A (en) * 1971-05-13 1972-10-24 Us Army Circuit for generating a repeatable voltage as a function of temperature
JPS49119080A (ja) * 1973-03-21 1974-11-14
US4002964A (en) * 1975-10-02 1977-01-11 Gordon Engineering Company Temperature compensation technique
US4001554A (en) * 1975-10-29 1977-01-04 The United States Of America As Represented By The Secretary Of The Army Mode control computer interface
NL7907161A (nl) * 1978-09-27 1980-03-31 Analog Devices Inc Geintegreerde temperatuurgecompenseerde spannings- referentie.
DE3171674D1 (en) * 1980-04-28 1985-09-12 Fujitsu Ltd Temperature compensating voltage generator circuit
US4562400A (en) * 1983-08-30 1985-12-31 Analog Devices, Incorporated Temperature-compensated zener voltage reference

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Publication number Publication date
FR2680587B1 (fr) 1993-10-15
DE69213869T2 (de) 1997-01-30
FR2680587A1 (fr) 1993-02-26
JPH06268459A (ja) 1994-09-22
DE69213869D1 (de) 1996-10-24
CA2076475A1 (fr) 1993-02-24
US5341287A (en) 1994-08-23
EP0530072A1 (fr) 1993-03-03

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