EP0165893B1 - Brightness control device for a fluorescent lamp - Google Patents

Brightness control device for a fluorescent lamp Download PDF

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Publication number
EP0165893B1
EP0165893B1 EP85810080A EP85810080A EP0165893B1 EP 0165893 B1 EP0165893 B1 EP 0165893B1 EP 85810080 A EP85810080 A EP 85810080A EP 85810080 A EP85810080 A EP 85810080A EP 0165893 B1 EP0165893 B1 EP 0165893B1
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EP
European Patent Office
Prior art keywords
fluorescent lamp
voltage
capacitor
circuit
current
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EP85810080A
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German (de)
French (fr)
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EP0165893A2 (en
EP0165893B2 (en
EP0165893A3 (en
Inventor
Fredy Kamber
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Starkstrom-Elektronik AG
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Starkstrom-Elektronik AG
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Priority to AT85810080T priority Critical patent/ATE42663T1/en
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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/36—Controlling
    • H05B41/38—Controlling the intensity of light
    • H05B41/39—Controlling the intensity of light continuously
    • H05B41/392—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor
    • H05B41/3921—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor with possibility of light intensity variations
    • H05B41/3924—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor with possibility of light intensity variations by phase control, e.g. using a triac

Definitions

  • the invention relates to a device for controlling the brightness of fluorescent lamps according to the preamble of patent claim 1.
  • control devices of this type are known, but they are disadvantageous because they do not or only with complex auxiliary circuits for controlling the brightness of fluorescent lamps with high ignition voltage and poor control properties, such as the so-called slimline tubes with a diameter of 26 mm can be used, and because they only allow a limited control range with insufficiently low minimum brightness.
  • a control of the brightness is not possible by means of a phase cut of the supplying alternating current if the glow cathodes of the fluorescent lamps are preheated by a heating transformer since the lamps do not ignite.
  • a heating transformer is dispensed with and a conventional glow starter device is provided for it, the lamps can be ignited at full control. With additional circuit measures in the phase gating device, a control range down to about 20% can be achieved.
  • the permissible control range is limited to around 50%.
  • a device has also become known in which, on the one hand, an uncontrolled current is continuously fed to the hot cathodes of the fluorescent lamps for their heating, so that there is no fear of the lamps being destroyed.
  • the supply current of the lamps is controlled by means of phase gating, with a low, higher-frequency energy being continuously supplied in parallel with the lamps for igniting and re-igniting the lamps in the current which is incomplete due to the phase gating control.
  • phase gating As a result of this higher-frequency energy, there is minimal brightness when the phase gating device is fully controlled.
  • the phase gating device is fully controlled, full light is achieved. Since a certain minimum higher-frequency energy must now be supplied to the lamps for a reliable ignition of the lamps on the one hand and a stable burning of the lamps in the controlled state on the other hand, the achievable control range is limited to approximately 4% (1:25).
  • the device according to the invention has the features stated in the characterizing part of patent claim 1.
  • the duration of the feeding of the higher-frequency energy can be shortened considerably. This means that a minimum brightness of well under 1% can be achieved. If the power of the damped ignition pulse oscillation triggered by the trigger circuit is reduced in a suitable manner when the phase gating is controlled back, the control range can be expanded to a minimum brightness of less than 0.01%. Although the ignition of the fluorescent lamp is guaranteed regardless of the time of the phase control, its emissivity remains unchanged in any state of the brightness control, because the hot cathodes of the lamp are continuously fed via an uncontrolled power supply, in particular a heating transformer.
  • Fig. 1 is by dash-dotted lines limits the circuit diagram of an exemplary embodiment of the control device 1 according to the invention.
  • the control device 1 has various connecting terminals, namely a connecting terminal 2 for connecting the phase conductor L1 of an AC network, a connecting terminal 3 for connecting the neutral conductor N of the AC network, a connecting terminal 4 for connecting the earth conductor E of the AC network and a connecting terminal 5 for connecting the controlled output of a phase gating device 6 shown only schematically, which in turn is connected to the phase conductor L1 and the neutral conductor N of the alternating current network and is of a conventional type which is not explained in detail here.
  • the control device 1 has further connection terminals on the load side, namely two connection terminals 7 for connecting a current-limiting ballast 8, usually a choke, and two pairs of connection terminals 9 and 10, which are provided for this purpose, each with a glow cathode filament 11 or 12 of a fluorescent lamp 13 to become.
  • connection terminals 9 and 10 For permanent and uncontrolled heating of the hot cathode filament 11, 12 there is a secondary winding 14 and 15, respectively, of a heating transformer 16 at the paired connection terminals 9 and 10, the primary winding 17 of which, accordingly, with the connection terminals 2 and 3 for the phase conductor L1 and the neutral conductor N of the AC network connected is.
  • the heating transformer 16 could also be arranged outside the control device 1 with dash-dotted lines, as is shown for the phase gating device 6 and the ballast 8.
  • One of each pair of connecting terminals 9, 10 also serves to supply the connected fluorescent lamp 13 with the fuel supply current of the AC network during the phase gating periods. Accordingly, one of the connection terminals 9 is essentially connected to the connection terminal 5 via the connection terminals 7 for the ballast 8, and one of the connection terminals 10 is essentially connected to the connection terminal 3.
  • a first trigger circuit 18 is connected, which consists of the series connection of a resistor 19, a first capacitor 20 and a second capacitor 21 and one at the connection point of the two capacitors 20 , 21 connected trigger diode 22.
  • the control device 1 shown also contains a further capacitor 27, which can be charged with respect to the connected neutral conductor N by a resistor 28 connected to the connected phase conductor L1 of the AC network via the connection terminal 2, and which via a primary winding 29 of a pulse transformer by means of the switching path of a electronic switch 30, preferably a triac, can be discharged.
  • the trigger diode 22 belonging to the trigger circuits 18 and 23 is connected to the control electrode of the triac 30.
  • the capacitor 27 and the primary winding 29 of the pulse transformer form a damped oscillating circuit 31.
  • the damped oscillation which is excited when the triac 30 is closed by the discharge current of the capacitor 27 which flows through the primary winding 29 has here a frequency that is significantly greater than the frequency of the AC network and that is, for example, above 20 kHz.
  • Two separate secondary windings 32 and 33 of the pulse transformer mentioned with the primary winding 29 are connected into the feed lines of the fluorescent lamp 13. They are connected to one another at their ends facing away from the fluorescent lamp 13 by a bypass capacitor 34, so that the fluorescent lamp 13, the two secondary windings 32 and 33 of the pulse transformer and the bypass capacitor 34 form a closed ignition circuit, as will be explained below.
  • the phase gating device 6 supplies a voltage UPA to the connecting terminal 5 of the control device 1, the course of which is shown in FIG. 2a in the period of a half-wave between the specified times t o and t 6 for three different settings of the phase gating device.
  • the phase gating takes place at a time t 3 (relatively large current flow angle).
  • the phase gating takes place at a later point in time t 4 (smaller current flow angle).
  • the phase gating takes place at a time t 5 shortly before the zero crossing of the voltage at time t 6 (very small current flow angle).
  • the voltage still present in the periods t o to t 2 or t o to t comes from the current still flowing when the fluorescent lamp is on and disappears at the zero crossing of the current (time t or t 2 ) with a steep flank this edge with a decreasing current flow angle to the zero crossing t o shifts.
  • the voltage UPA then has a vertical flank 35, 36 or 37 at the times t 3 , t 4 or t 5 set in the phase gating device 6.
  • the occurrence of the edge 35 or 36 for example, generates a control pulse on the control electrode of the triac 30 via the trigger circuit 18. Since at the beginning of the relevant half-wave of the AC line voltage Uu, the capacitor 27 is charged via the resistor connected to the connection terminal 2, the voltage U c of the capacitor 27 is also above the triac 30, so that the latter is turned on by the control pulse of the trigger diode 22 is switched. As a result, the capacitor 27 can discharge via the primary winding 29 of the pulse transformer, which is now connected in parallel with it.
  • the higher-frequency, damped voltage generated by the oscillating circuit 31 into the ignition circuit is closed via the secondary windings 32 and 33, the fluorescent lamp 13 and the capacitor 34.
  • the ignition voltage applied to the fluorescent lamp 13 is thus kept away from the ballast.
  • the frequency of the damped oscillation excited in the oscillating circuit 31 is approximately 30 kHz and the duration of the oscillation is approximately 0.5 ms.
  • the oscillation train of the damped ones produced Vibration very powerful, including the ignition pulse applied to the fluorescent lamp 13 and transformed to a voltage of approximately 1000 V.
  • the latter can also have only a single secondary winding.
  • the division shown in FIG. 1 into two identical secondary windings 32, 33 with an additive winding sense has the advantage that the high transformed ignition voltage of the resonant circuit 31 is halved against the potential of the neutral conductor N or against the earth potential.
  • the voltage stress on the heating transformer 16 is also reduced by half due to the above-mentioned division relative to the earth potential.
  • FIG. 2b shows the time profiles of the two voltages u L1 and u c in a half wave, which corresponds to that of the diagram of FIG. 2a between the times t o and t 6 .
  • 2b shows the values of the voltages u c at the capacitor 27 in the phase gating times t 3 , t 4 and t 5 of FIG.
  • the mains AC voltage present at the connecting terminal 5 is no longer sufficient to maintain a combustion current in the ignited fluorescent lamp 13, the decaying effect causes over the secondary winding 32, 33 of the pulse transformer fed in higher-frequency ignition oscillation a short further burning of the fluorescent lamp 13, so that a low light brightness is maintained. Since, according to the diagram in FIG. 2b, with a further reduction in the phase gating angle , that is to say a further approximation of the phase gating to the zero crossing of the mains voltage UL1 , the voltage at the capacitor 27 decreases and thus the power of the higher-frequency oscillation supplied to the fluorescent lamp decreases, a further reduction in brightness. This makes it possible to continuously achieve a minimum brightness of less than 0.01%.
  • the ignition torque shifts forward.
  • the voltage u c across the capacitor 27 is greater. This has the advantageous consequence that the fluorescent lamp 13 burns stably when the higher light level is set.
  • the second trigger circuit 23 takes advantage of the voltage across the two feed lines of the fluorescent lamp 13 or the voltage across the bypass capacitor 34.
  • the operating voltage of the fluorescent lamp is essentially at the capacitor 34, which is considerably lower than the mains voltage UL1 .
  • the voltage divider with the resistor 24 and the capacitor 25 of the trigger circuit 23 is dimensioned such that in this case the divided operating voltage of the fluorescent lamp 13 applied to the trigger diode 22 via the resistor 26 does not reach the trigger voltage of the diode 22.
  • the voltage across the bypass capacitor 34 is identical to the mains voltage U L1 ' when the phase gating device 6 is fully activated. Since this voltage is significantly higher than the burning voltage of the fluorescent lamp, it is sufficient voltage on capacitor 25 to trigger periodic switch-on of triac 30 via trigger diode 22 until fluorescent lamp 13 has ignited due to the damped vibrations generated thereby. As soon as the fluorescent lamp burns, the second trigger circuit 23 becomes inactive due to a lack of sufficient trigger voltage. It should also be noted here that when the triac 30 is switched on, which, according to the diagram in FIG. 2b, is slightly earlier than the time t 3 or should be by appropriate selection of the values of the components of the trigger circuit 23, the voltage Uc at the capacitor 27 is sufficiently large in spite of lag to generate a powerful ignition pulse.
  • the voltage divider composed of the capacitors 20 and 21 essentially determines the minimum voltage reaching the trigger diode 22 for its control. At times when the voltage UPA applied to the trigger circuit 18 is so high that the trigger diode 22 could be damaged, the resistor 19 limits the current flowing through the capacitors 20 and 21, so that the control voltage at the trigger diode 22 is safe Value is limited.
  • FIG. 3 schematically shows the part of the control device 1 of FIG. 1 that has been changed for this case.
  • the part shown again shows the fluorescent lamp 13 with hot cathode filaments 11 and 12, which are fed with heating current via connecting terminals 9 and 10, respectively, from the secondary windings 14 and 15 of the heating transformer 16 of FIG. 1. Furthermore, the ballast 8 connected via the connection terminals 7 to the phase-controlled mains supply line is shown in accordance with FIG. 1.
  • the primary transformer 29, which belongs to the resonant circuit 31 of FIG. 1, has a single secondary winding 38, which is connected on the one hand to the neutral line connected to the connecting terminal 3 for the neutral conductor N (FIG. 1) and on the other hand via a capacitor 39 to the neutral line this neutral line lying hot cathode coil 11 or is connected to one of the terminals 9.
  • the Ueber shown in Fig. 1 bridge capacitor 34 is of course omitted.
  • the remaining circuit parts of FIG. 1 are essentially unchanged (not shown in FIG. 3).

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Circuit Arrangements For Discharge Lamps (AREA)

Abstract

1. Device for controlling the brightness of fluorescent lamps by means of an adjustable phase control of each voltage half wave of a feeding alternating-current system, the current switched from the time of the phase control to the next zero transition of the voltage halfwave being supplied via a current-limiting ballast to the fluorescent lamp, the cathodes of the fluorescent lamp furthermore being continuously and uncontrolledly heated by the alternating current system, and means being provided to supply higher-frequency energy to the fluorescent lamp for its ignition, characterized by a trigger circuit (18) which can be fed by the voltage of the phasecontrolled halfwave of the system alternating voltage and a damped resonant circuit (31) which can be charged, which is connected to the trigger circuit and to which the fluorescent lamps can be connected with respect to alternating current, the damped oscillation of the resonant circuit (31) triggered by the trigger circuit having a higher frequency than the frequency of the system alternating voltage and exhibiting at the beginning an electric power which is sufficient for igniting the fluorescent lamp.

Description

Die Erfindung bezieht sich auf eine Einrichtung zur Steuerung der Helligkeit von Leuchtstofflampen gemäss dem Oberbegriff des Patentanspruchs 1.The invention relates to a device for controlling the brightness of fluorescent lamps according to the preamble of patent claim 1.

Es sind zahlreiche Steuerungseinrichtungen dieser Art bekannt, die jedoch deshalb nachteilig sind, weil sie sich zur Steuerung der Helligkeit von Leuchtstofflampen mit hoher Zündspannung und schlechten Steuereigenschaften, wie beispielsweise den sogenannten Slimline-Röhren mit einem Durchmesser von 26 mm, nicht oder nur mit aufwendigen Hilfsschaltungen verwenden lassen, und weil sie nur einen beschränkten Steuerbereich mit nicht ausreichend tiefer Minimalhelligkeit zulassen.Numerous control devices of this type are known, but they are disadvantageous because they do not or only with complex auxiliary circuits for controlling the brightness of fluorescent lamps with high ignition voltage and poor control properties, such as the so-called slimline tubes with a diameter of 26 mm can be used, and because they only allow a limited control range with insufficiently low minimum brightness.

Mittels Phasenanschnitts des speisenden Netzwechselstroms ist eine Steuerung der Helligkeit nicht möglich, wenn die Glühkathoden der Leuchtstofflampen durch einen Heiztransformator vorgeheizt werden, da die Lampen nicht zünden. Wenn jedoch auf einen Heiztransformator verzichtet wird und dafür ein konventionelles Glimmstartergerät vorgesehen wird, ist eine Zündung der Lampen bei Vollaussteuerung möglich. Mit zusätzlichen Schaltungsmassnahmen im Phasenanschnittgerät ist ein Steuerbereich bis auf etwa 20% hinunter realisierbar. Da bei Unterschreiten eines bestimmten Lampenstromes die Glühkathoden der Lampen jedoch zu wenig geheizt werden, so dass ihre Emissionsfähigkeit stark sinkt, und damit die Lampen bereits nach wenigen Betriebsstunden zufolge Zerstörung unbrauchbar werden, ist der zulässige Steuerbereich auf etwa 50 % beschränkt.A control of the brightness is not possible by means of a phase cut of the supplying alternating current if the glow cathodes of the fluorescent lamps are preheated by a heating transformer since the lamps do not ignite. However, if a heating transformer is dispensed with and a conventional glow starter device is provided for it, the lamps can be ignited at full control. With additional circuit measures in the phase gating device, a control range down to about 20% can be achieved. However, since the glow cathodes of the lamps are not heated enough when the lamp current falls below a certain value, so that their emissivity drops sharply and the lamps become unusable after only a few hours of operation following destruction, the permissible control range is limited to around 50%.

Es ist auch bekannt, Leuchtstofflampen mit einem Wechselstrom höherer Frequenz zu speisen, das heisst mit einer oberhalb 20 kHz liegenden Frequenz. Mittels eines elektronischen Vorschaltgeräts wird hierbei die höherfrequente Speisespannung bzw. der höherfrequente Speisestrom zur Steuerung der Helligkeit verändert. Eine ungesteuerte Stromversorgung zur Heizung der Glühkathoden ist hierbei nicht erforderlich. Da durch die vorgeschaltete, mittels Phasenanschnitts oder eines Regeltransformators vorgenommene Spannungs- bzw. Stromsteuerung die abgegebene Leistung des elektronischen Vorschaltgeräts stark reduziert wird und dadurch die aus der gleichen Quelle gespiesene Glühkathodenheizung ungenügend wird, ist der erzielbare Steuerbereich auf etwa 10 % begrenzt.It is also known to feed fluorescent lamps with an alternating current of higher frequency, that is to say with a frequency above 20 kHz. By means of an electronic ballast, the higher-frequency supply voltage or the higher-frequency supply current is changed to control the brightness. An uncontrolled power supply for heating the hot cathode is not necessary. Since the output power of the electronic ballast is greatly reduced by the upstream voltage or current control carried out by means of phase angle control or a regulating transformer and the hot cathode heating supplied from the same source is thereby insufficient, the achievable control range is limited to approximately 10%.

Es ist ferner eine Einrichtung bekannt geworden, bei welcher einerseits den Glühkathoden der Leuchtstofflampen zu ihrer Heizung dauernd ein ungesteuerter Strom zugeführt wird, so dass eine Zerstörung der Lampen nicht zu befürchten ist. Andererseits wird der Speisestrom der Lampen mittels Phasenanschnitts gesteuert, wobei zum Zünden und zum Wiederzünden der Lampen bei dem zufolge der Phasenanschnittsteuerung lückenhaften Strom parallel zu den Lampen eine geringe höherfrequence Energie dauernd zugeführt wird. Zufolge dieser höherfrequenten Energie ergibt sich eine minimale Helligkeit, wenn das Phasenanschnittgerät vollständig zurückgesteuert ist. Bei Vollaussteuerung des Phasenanschnittgeräts wird volles Licht erreicht. Da nun für ein sicheres Zünden der Lampen einerseits und ein stabiles Brennen der Lampen im gesteuerten Zustand andererseits eine bestimmte minimale höherfrequente Energie den Lampen zugeführt werden muss, ist der erzielbare Steuerbereich auf etwa 4 % (1 : 25) beschränkt.A device has also become known in which, on the one hand, an uncontrolled current is continuously fed to the hot cathodes of the fluorescent lamps for their heating, so that there is no fear of the lamps being destroyed. On the other hand, the supply current of the lamps is controlled by means of phase gating, with a low, higher-frequency energy being continuously supplied in parallel with the lamps for igniting and re-igniting the lamps in the current which is incomplete due to the phase gating control. As a result of this higher-frequency energy, there is minimal brightness when the phase gating device is fully controlled. When the phase gating device is fully controlled, full light is achieved. Since a certain minimum higher-frequency energy must now be supplied to the lamps for a reliable ignition of the lamps on the one hand and a stable burning of the lamps in the controlled state on the other hand, the achievable control range is limited to approximately 4% (1:25).

Es hat sich jedoch gezeigt, dass es in zahlreichen Fällen erwünscht ist, eine wesentlich kleinere steuerbare Minimalhelligkeit zu erreichen, was mit den bekannten Einrichtungen nicht möglich ist.However, it has been shown that it is desirable in numerous cases to achieve a significantly smaller controllable minimum brightness, which is not possible with the known devices.

Aufgabe der vorliegenden Erfindung ist deshalb, eine Vorrichtung der eingangs genannten Art zu schaffen, mit welcher die Helligkeit der Leuchtstofflampen ohne Beeinträchtigung der Emissionsfähigkeit ihrer Glühkathoden in einem Bereich von vollem Licht bis zu einer wesentlich unterhalb von 4% liegenden Minimalhelligkeit kontinuierlich steuerbar ist.It is therefore an object of the present invention to provide a device of the type mentioned at the outset with which the brightness of the fluorescent lamps can be continuously controlled in a range from full light to a minimum brightness which is substantially below 4% without impairing the emissivity of their hot cathodes.

Zur Lösung dieser Aufgabe weist die Einrichtung gemäss der Erfindung die im kennzeichnenden Teil des Patentanspruchs 1 angeführten Merkmale auf.To achieve this object, the device according to the invention has the features stated in the characterizing part of patent claim 1.

Dadurch, dass bei der erfindungsgemässen Einrichtung der Leuchtstofflampe eine höherfrequente Zündenergie hoher Leistung, jedoch nur im Anschnittzeitpunkt jeder Halbwelle der Netzwechselspannung zugeführt wird, kann die Zeifdauer der Einspeisung der höherfrequenten Energie erheblich verkürzt werden. Dadurch kann eine Minimalhelligkeit von weit unter 1 % erzielt werden. Wenn beim Zurucksteuern des Phasenanschnitts gleichzeitig die Leistung der durch die Triggerschaltung ausgelösten, gedämpften Zündimpulsschwingung in geeigneter Weise reduziert wird, kann der Steuerbereich bis zu einer Minimalhelligkeit von unter 0,01 % erweitert werden. Obwohl die Zündung der Leuchtstofflampe unabhängig vom Zeitpunk des Phasenanschnitts gewährleistet ist, bleibt ihre Emissionsfähigkeit in jedem Zustand der Helligkeitssteuerung unverändert, weil die Glühkathoden der Lampe über eine ungesteuerte Stromversorgung, insbesondere einen Heiztransformator, dauernd gespeist werden.The fact that in the inventive device of the fluorescent lamp a higher-frequency ignition energy of high power, but only at the cut-in time of each half-wave of the AC mains voltage, the duration of the feeding of the higher-frequency energy can be shortened considerably. This means that a minimum brightness of well under 1% can be achieved. If the power of the damped ignition pulse oscillation triggered by the trigger circuit is reduced in a suitable manner when the phase gating is controlled back, the control range can be expanded to a minimum brightness of less than 0.01%. Although the ignition of the fluorescent lamp is guaranteed regardless of the time of the phase control, its emissivity remains unchanged in any state of the brightness control, because the hot cathodes of the lamp are continuously fed via an uncontrolled power supply, in particular a heating transformer.

Ausführungsbeispiele des Erfindungsgegenstandes werden nachstehend anhand der Zeichnung erläutert. Es zeigen :

  • Fig. 1 ein Schaltungsschema einer erfindungsgemässen Einrichtung zusammen mit einem Phasenanschnittgerät, einem Vorschaltgerät und einer Leuchtstofflampe,
  • Fig. 2a und 2b Diagramme des zeitlichen Verlaufs verschiedener Spannungen im Schaltungsschema der Fig. 1, und
  • Fig. 3 ein Teil des Schaltungsschemas der Fig. 1 in einer Ausführungsvariante.
Embodiments of the subject matter of the invention are explained below with reference to the drawing. Show it :
  • 1 shows a circuit diagram of a device according to the invention together with a phase gating device, a ballast and a fluorescent lamp,
  • 2a and 2b diagrams of the time course of different voltages in the circuit diagram of Fig. 1, and
  • Fig. 3 shows a part of the circuit diagram of Fig. 1 in an embodiment.

In Fig. 1 ist durch strichpunktierte Linien begrenzt das Schaltungsschema eines Ausführungsbeispiels der erfindungsgemässen Steuereinrichtung 1 dargestellt. Die Steuereinrichtung 1 hat verschiedene Anschlussklemmen, nämlich speiseseitig eine Anschlussklemme 2 zum Anschliessen des Phasenleiters L1 eines Wechselstromnetzes, eine Anschlussklemme 3 zum Anschliessen des Nullleiters N des Wechselstromnetzes, eine Anschlussklemme 4 zum Anschliessen des Erdleiters E des Wechselstromnetzes sowie eine Anschlussklemme 5 zum Anschliessen des gesteuerten Ausgangs eines nur schematisch dargestellten Phasenanschnittgeräts 6, das seinerseits an den Phasenleiter L1 und den Nulleiter N des Wechselstromnetzes angeschlossen ist und von üblicher, hier nicht näher erläuterter Bauart ist. Die Steuereinrichtung 1 hat lastseitig weitere Anschlussklemmen, nämlich zwei Anschlussklemmen 7 zum reihenmässigen Anschliessen eines strombegrenzenden Vorschaltgeräts 8, üblicherweise einer Drossel, und zwei Paare von Anschlussklemmen 9 und 10, die dafür vorgesehen sind, mit je einem Glühkathodenwendel 11 bzw. 12 einer Leuchtstofflampe 13 verbunden zu werden.In Fig. 1 is by dash-dotted lines limits the circuit diagram of an exemplary embodiment of the control device 1 according to the invention. The control device 1 has various connecting terminals, namely a connecting terminal 2 for connecting the phase conductor L1 of an AC network, a connecting terminal 3 for connecting the neutral conductor N of the AC network, a connecting terminal 4 for connecting the earth conductor E of the AC network and a connecting terminal 5 for connecting the controlled output of a phase gating device 6 shown only schematically, which in turn is connected to the phase conductor L1 and the neutral conductor N of the alternating current network and is of a conventional type which is not explained in detail here. The control device 1 has further connection terminals on the load side, namely two connection terminals 7 for connecting a current-limiting ballast 8, usually a choke, and two pairs of connection terminals 9 and 10, which are provided for this purpose, each with a glow cathode filament 11 or 12 of a fluorescent lamp 13 to become.

Zur dauernden und ungesteuerten Heizung der Glühkathodenwendel 11, 12 liegt an den paarweisen Anschlussklemmen 9 und 10 je eine Sekundärwicklung 14 bzw. 15 eines Heiztransformators 16, dessen Primärwicklung 17 demnach mit den Anschlussklemmen 2 und 3 für den Phasenleiter L1 bzw. den Nulleiter N des Wechselstromnetzes verbunden ist. Es ist ersichtlich, dass der Heiztransformator 16 auch ausserhalb der strichpunktiert umrandeten Steuereinrichtung 1 angeordnet werden könnte, wie dies für das Phasenanschnittgerät 6 und das Vorschaltgerät 8 dargestellt ist. Je eine der Paarweisen Anschlussklemmen 9, 10 dient ferner dazu, die angeschlossene Leuchtstofflampe 13 während den Phasenanschnittperioden mit dem Brennspeisestrom des Wechselstromnetzes zu versorgen. Demnach ist eine der Anschlussklemmen 9 über die Anschlussklemmen 7 für das Vorschaltgerät 8 im wesentlichen mit der Anschlussklemme 5, und eine der Anschlussklemmen 10 im wesentlichen mit der Anschlussklemme 3 verbunden.For permanent and uncontrolled heating of the hot cathode filament 11, 12 there is a secondary winding 14 and 15, respectively, of a heating transformer 16 at the paired connection terminals 9 and 10, the primary winding 17 of which, accordingly, with the connection terminals 2 and 3 for the phase conductor L1 and the neutral conductor N of the AC network connected is. It can be seen that the heating transformer 16 could also be arranged outside the control device 1 with dash-dotted lines, as is shown for the phase gating device 6 and the ballast 8. One of each pair of connecting terminals 9, 10 also serves to supply the connected fluorescent lamp 13 with the fuel supply current of the AC network during the phase gating periods. Accordingly, one of the connection terminals 9 is essentially connected to the connection terminal 5 via the connection terminals 7 for the ballast 8, and one of the connection terminals 10 is essentially connected to the connection terminal 3.

Zwischen den gesteuerten Ausgang des angeschlossenen Phasenanschnittgeräts 6 und den angeschlossenen Nulleiter N des Wechselstromnetzes, ist eine erste Triggerschaltung 18 geschaltet, welche aus der Reihenschaltung eines Widerstands 19, eines ersten Kondensators 20 und eines zweiten Kondensators 21 sowie aus einer an den Verbindungspunkt der beiden Kondensatoren 20, 21 angeschlossenen Triggerdiode 22 besteht. Eine zweite Triggerschaltung 23, welche zwischen den Ausgang des angeschlossenen Vorschaltgeräts 8 und den angeschlossenen Nulleiter N des Wechselstromnetzes geschaltet ist, weist die Reihenschaltung eines Widerstands 24 und eines Kondensators 25 sowie einen Widerstand 26 auf, der den Verbindungspunkt des Widerstands 24 und des Kondensators 25 mit der bereits erwähnten Triggerdiode 22 verbindet.Between the controlled output of the connected phase gating device 6 and the connected neutral conductor N of the AC network, a first trigger circuit 18 is connected, which consists of the series connection of a resistor 19, a first capacitor 20 and a second capacitor 21 and one at the connection point of the two capacitors 20 , 21 connected trigger diode 22. A second trigger circuit 23, which is connected between the output of the connected ballast 8 and the connected neutral conductor N of the AC network, has the series connection of a resistor 24 and a capacitor 25 and a resistor 26, which also connects the connection point of the resistor 24 and the capacitor 25 the already mentioned trigger diode 22 connects.

Die dargestellte Steuereinrichtung 1 enthält zudem einen weiteren Kondensator 27, welcher durch einen mit dem angeschlossenen Phasenleiter L1 des Wechselstromnetzes über die Anschlussklemme 2 in Verbindung stehenden Widerstand 28 gegenüber dem angeschlossenen Nullleiter N aufladbar ist, und welcher über eine Primärwicklung 29 eines Impulstransformators mittels der Schaltstrecke eines elektronischen Schalters 30, vorzugsweise eines Triac, entladbar ist. An die Steuerelektrode des Triac 30 ist die zu den Triggerschaltungen 18 und 23 gehörige Triggerdiode 22 angeschlossen. Wenn sich der Triac 30 im leitenden Zustand befindet, bilden der Kondensator 27 und die Primärwicklung 29 des Impulstransformators einen gedämpften Schwingkreis 31. Die beim Schliessen des Triac 30 durch den Entladungsstrom des Kondensators 27, welcher durch die Primärwicklung 29 fliesst, angeregte gedämpfte Schwingung hat hierbei eine Frequenz, die wesentlich grösser ist als die Frequenz des Wechselstromnetzes und die beispielsweise oberhalb von 20 kHz liegt.The control device 1 shown also contains a further capacitor 27, which can be charged with respect to the connected neutral conductor N by a resistor 28 connected to the connected phase conductor L1 of the AC network via the connection terminal 2, and which via a primary winding 29 of a pulse transformer by means of the switching path of a electronic switch 30, preferably a triac, can be discharged. The trigger diode 22 belonging to the trigger circuits 18 and 23 is connected to the control electrode of the triac 30. When the triac 30 is in the conductive state, the capacitor 27 and the primary winding 29 of the pulse transformer form a damped oscillating circuit 31. The damped oscillation which is excited when the triac 30 is closed by the discharge current of the capacitor 27 which flows through the primary winding 29 has here a frequency that is significantly greater than the frequency of the AC network and that is, for example, above 20 kHz.

Zwei getrennte Sekundärwicklungen 32 und 33 des genannten Impulstransformators mit der Primärwicklung 29 sind in die Speisezuleitungen der Leuchtstofflampe 13 geschaltet. Sie sind an ihren von der Leuchtstofflampe 13 abgewandten Enden durch einen Ueberbrückungskondensator 34 miteinander verbunden, so dass die Leuchtstofflampe 13, die beiden Sekundärwicklungen 32 und 33 des Impulstransformators und der Ueberbrückungskondensator 34 einen geschlossenen Zündstromkreis bilden, wie dies nachstehend noch erläutert wird.Two separate secondary windings 32 and 33 of the pulse transformer mentioned with the primary winding 29 are connected into the feed lines of the fluorescent lamp 13. They are connected to one another at their ends facing away from the fluorescent lamp 13 by a bypass capacitor 34, so that the fluorescent lamp 13, the two secondary windings 32 and 33 of the pulse transformer and the bypass capacitor 34 form a closed ignition circuit, as will be explained below.

Die Arbeitsweise der in Fig. 1 dargestellten Einrichtung 1 im Zusammenhang mit den ebenfalls dargestellten äusseren Bauteilen 6, 8 und 13 sowie dem Wechselstromnetz ist die folgende.The operation of the device 1 shown in Fig. 1 in connection with the outer components 6, 8 and 13 also shown and the AC network is the following.

Das Phasenanschnittgerät 6 gibt an die Anschlussklemme 5 der Steuereinrichtung 1 in an sich bekannter Weise eine Spannung UPA, deren zeitlicher Verlauf in Fig. 2a im Zeitraum einer Halbwelle zwischen den angegebenen Zeitpunkten to und t6 für drei verschiedene Einstellungen des Phasenanschnittgeräts dargestellt ist. Im einen Fall, der mit einer ausgezogenen Linie des Spannungsverlaufs dargestellt ist, erfolgt der Phasenanschnitt in einem Zeitpunkt t3 (relativ grosser Stromflusswinkel). In einem weiteren Fall, der mit einer strichpunktierten Linie des Spannungsverlaufs dargestellt ist, erfolgt der Phasenanschnitt in einem späteren Zeitpunkt t4 (kleinerer Stromflusswinkel). In einem letzten Fall, der mit einer gestrichelten Linie des Spannungsverlaufs dargestellt ist, erfolgt der Phasenanschnitt in einem Zeitpunkt t5 kurz vor dem Nulldurchgang der Spannung im Zeitpunkt t6 (sehr kleiner Stromflusswinkel). Die in den Zeitabschnitten to bis t2 bzw. to bis t, noch anstehende Spannung rührt von dem bei brennender Leuchtstofflampe noch fliessenden Strom her und verschwindet im Nulldurchgang des Stroms (Zeitpunkt t, bzw. t2) mit steiler Flanke, wobei sich diese Flanke mit kleiner werdendem Stromflusswinkel zum Nulldurchgang to verschiebt.The phase gating device 6 supplies a voltage UPA to the connecting terminal 5 of the control device 1, the course of which is shown in FIG. 2a in the period of a half-wave between the specified times t o and t 6 for three different settings of the phase gating device. In one case, which is shown with a solid line of the voltage profile, the phase gating takes place at a time t 3 (relatively large current flow angle). In a further case, which is shown with a dash-dotted line of the voltage curve, the phase gating takes place at a later point in time t 4 (smaller current flow angle). In a last case, which is shown with a dashed line of the voltage curve, the phase gating takes place at a time t 5 shortly before the zero crossing of the voltage at time t 6 (very small current flow angle). The voltage still present in the periods t o to t 2 or t o to t comes from the current still flowing when the fluorescent lamp is on and disappears at the zero crossing of the current (time t or t 2 ) with a steep flank this edge with a decreasing current flow angle to the zero crossing t o shifts.

Die Spannung UPA weist danach in den im Phasenanschnittgerät 6 eingestellten Zeitpunkten t3, t4 oder t5 eine senkrechte Flanke 35, 36 bzw.37 auf. In der Steuereinrichtung 1 (Fig. 1) erzeugt das Auftreten beispielsweise der Flanke 35 oder 36 über die Triggerschaltung 18 an der Steuerelektrode des Triac 30 einen Steuerimpuls. Da mit Beginn der betreffenden Halbwelle der Netzwechselspannung Uu der Kondensator 27 über den mit der Anschlussklemme 2 verbundenen Widerstand aufgeladen wird, liegt die Spannung Uc des Kondensators 27 auch über dem Triac 30, so dass dieser durch den Steuerimpuls der Triggerdiode 22 in den leitenden Zustand geschaltet wird. Dadurch kann sich der Kondensator 27 über die nunmehr zu ihm parallel geschaltete Primärwicklung 29 des Impulstransformators entladen. In dem durch die Induktivität der Primärwicklung 29 und die Kapazität des Kondensators 27 gebildeten Parallelschwingkreis wird eine gedämpfte Schwingung erzeugt, deren erste Spannungs- und Stromamplituden relativ hoch sind. Entsprechend leistungsstarke, zeitlich abgeschwächte Schwingungen treten mit additiver Polarität an den Sekundärwicklungen 32 und 33 des Impulstransformators auf, so dass der über das Vorschaltgerät 8 an der Leuchtstofflampe 13 liegenden Speisespannung die transformierte Spannung des Schwingkreises 31 überlagert wird und die Leuchtstofflampe 13 sicher zündet. Nach erfolgter Zündung beginnt, immer innerhalb derselben Halbwelle der Netzwechselspannung und gespiesen aus dem Phasenanschnittgerät 6 sowie begrenzt durch das Vorschaltgerät 8, der reguläre Lampenstrom zu fliessen, bis der natürliche nächste Nulldurchgang des Netzwechselstroms erreicht wird. Nach einer durch die Einstellung des Phasenanschnittgeräts 6 bestimmten Pause (Fig. 2a) läuft in der nächsten Halbwelle der Netzwechselspannung der nämliche Vorgang mit umgekehrter Polarität ab.The voltage UPA then has a vertical flank 35, 36 or 37 at the times t 3 , t 4 or t 5 set in the phase gating device 6. In the control device 1 (FIG. 1), the occurrence of the edge 35 or 36, for example, generates a control pulse on the control electrode of the triac 30 via the trigger circuit 18. Since at the beginning of the relevant half-wave of the AC line voltage Uu, the capacitor 27 is charged via the resistor connected to the connection terminal 2, the voltage U c of the capacitor 27 is also above the triac 30, so that the latter is turned on by the control pulse of the trigger diode 22 is switched. As a result, the capacitor 27 can discharge via the primary winding 29 of the pulse transformer, which is now connected in parallel with it. In the parallel resonant circuit formed by the inductance of the primary winding 29 and the capacitance of the capacitor 27, a damped oscillation is generated, the first voltage and current amplitudes of which are relatively high. Correspondingly powerful, temporally weakened vibrations occur with additive polarity on the secondary windings 32 and 33 of the pulse transformer, so that the supply voltage applied to the fluorescent lamp 13 via the ballast 8 is superimposed on the transformed voltage of the resonant circuit 31 and the fluorescent lamp 13 is reliably ignited. After the ignition has taken place, the regular lamp current begins to flow, always within the same half-wave of the AC mains voltage and fed from the phase gating device 6 and limited by the ballast 8, until the natural next zero crossing of the AC mains current is reached. After a pause determined by the setting of the phase gating device 6 (FIG. 2a), the same process takes place with the opposite polarity in the next half-wave of the AC mains voltage.

Wie bereits erwähnt, ist mit der in Fig. 1 dargestellten Reiheneinspeisung der vom Schwingkreis 31 erzeugten höherfrequenten, gedämpften Spannung in den Zündstromkreis dieser über die Sekundärwicklungen 32 und 33, die Leuchtstofflampe 13 und den Kondensator 34 geschlossen. Somit wird die an die Leuchtstofflampe 13 angelegte Zündspannung vom Vorschaltgerät ferngehalten. In einem typischen Beispiel beträgt die Frequenz der im Schwingkreis 31 angeregten gedämpften Schwingung etwa 30 kHz und die Dauer der Schwingung etwa 0,5 ms. Da im Zeitpunkt der Triggerung des Triac 30 die Spannung uc am Kondensator 27 des Schwingkreises 31 etwa 150 V beträgt und durch die Zuschaltung der Primärwicklung 29 parallel zum Kondensator 27 ein Strom von höher als 0,5 A fliesst, ist der Schwingungszug der erzeugten gedämpften Schwingung sehr leistungsstark, also auch der an die Leuchtstofflampe 13 angelegte, auf eine Spannung von etwa 1000 V transformierte Zündimpuls.As already mentioned, with the series feed shown in FIG. 1, the higher-frequency, damped voltage generated by the oscillating circuit 31 into the ignition circuit is closed via the secondary windings 32 and 33, the fluorescent lamp 13 and the capacitor 34. The ignition voltage applied to the fluorescent lamp 13 is thus kept away from the ballast. In a typical example, the frequency of the damped oscillation excited in the oscillating circuit 31 is approximately 30 kHz and the duration of the oscillation is approximately 0.5 ms. Since the voltage u c across the capacitor 27 of the resonant circuit 31 is approximately 150 V at the time the triac 30 is triggered and a current of greater than 0.5 A flows through the connection of the primary winding 29 in parallel with the capacitor 27, the oscillation train of the damped ones produced Vibration very powerful, including the ignition pulse applied to the fluorescent lamp 13 and transformed to a voltage of approximately 1000 V.

Statt zweier getrennter Sekundärwicklungen 32, 33 des Impulstransformators kann dieser auch nur eine einzige Sekundärwicklung aufweisen. Durch die in Fig. 1 dargestellte Aufteilung in zwei gleiche Sekundärwicklungen 32, 33 mit additivem Wicklungssinn wird aber der Vorteil erzielt, dass die hohe transformierte Zündspannung des Schwingkreises 31 gegen das Potential des Nulleiters N bzw. gegen das Erdpotential halbiert wird. Auch die Spannungsbeanspruchung am Heiztransformator 16 wird durch die genannte Aufteilung gegenüber dem Erdpotential auf die Hälfte reduziert.Instead of two separate secondary windings 32, 33 of the pulse transformer, the latter can also have only a single secondary winding. The division shown in FIG. 1 into two identical secondary windings 32, 33 with an additive winding sense has the advantage that the high transformed ignition voltage of the resonant circuit 31 is halved against the potential of the neutral conductor N or against the earth potential. The voltage stress on the heating transformer 16 is also reduced by half due to the above-mentioned division relative to the earth potential.

Neben dem vorgängig beschriebenen Betriebszustand, in welchem gemäss dem Diagramm der Fig. 2a die Flanke 35 oder 36 der angeschnittenen Halbwelle entsprechend der jeweiligen Einstellung des Phasenanschnittgeräts 6 (Fig. 1) an irgend einer mittleren Stelle t3 bzw. t4 zwischen den bciden aufeinanderfolgenden Nulldurchgängen der Netzspannung UL1 liegt, jedoch nicht in unmittelbarer Nähe eines dieser Nulldurchgänge, sind noch die Betriebszustände in Betracht zu ziehen, die vorliegen, wenn der Stromflusswinkel sehr klein ist (Zurücksteuern des Phasenanschnittgeräts 3 auf den Zeitpunkt t5 in Fig: 2a) oder maximal ist (Vollsteuerung des Phasenanschnittgeräts).In addition to the previously described operating state, in which, according to the diagram in FIG. 2a, the flank 35 or 36 of the cut half-wave corresponding to the respective setting of the phase gating device 6 (FIG. 1) at any middle point t 3 or t 4 between the two successive ones Zero crossings of the mains voltage UL1 , but not in the immediate vicinity of one of these zero crossings, still have to be taken into account the operating states that exist when the current flow angle is very small (control of the phase gating device 3 back to the time t 5 in FIG. 2a) or maximum is (full control of the phase control device).

Inbezug auf den erstgenannten Fall eines sehr kleinen eingestellten Stromflusswinkels ist zu berücksichtigen, dass die am Kondensator 27 liegende, über den Widerstand 28 zugeführte Spannung uc gegenüber der vom Phasenleiter L1 des Wechselstromnetzes geführten Netzspannung UL1' aus welcher die Kondensatorspannung uc abgeleitet ist, nacheilend phasenverschoben ist. Im Diagramm der Fig. 2b sind die zeitlichen Verläufe der beiden Spannungen uL1 und uc in einer Halbwelle dargestellt, welche derjenigen des Diagramms der Fig. 2a zwischen den Zeitpunkten to und t6 entspricht. In der Fig. 2b sind die Werte der in den Phasenanschnitt-Zeitpunkten t3, t4 und t5 der Fig. 2a am Kondensator 27 liegenden Spannungen uc vor der Triggerung bzw. Entladung des Kondensators 27 durch die Primärwicklung 29 angedeutet. Daraus ist ersichtlich dass die Spannung uc im Zeitpunkt t5 kurz vor dem Nulldurchgang der Netzspannung UL1 im Zeitpunkt t5 noch verhältnismässig gross ist, so dass auch dann, wenn das Phasenanschnittgerät 6 praktisch vollständig zurückgesteuert wird (Zeitpunkt t5 mit Flanke 37 in Fig. 2a), eine für die Zündung der Leuchtstofflampe 13 ausreichende Zündimpulsleistung erzeugt wird. Mit anderen Worten kann mit der vorliegenden Steuereinrichtung 1 auch dann eine sichere Zündung der Leuchtstofflampe 13 erzielt werden, wenn mit dem Phasenanschnittgerät 6 ein sehr kleiner Stromflusswinkel, d. h. eine sehr geringe Helligkeit von wesentlich unter 1 %, eingestellt wird.With regard to the first-mentioned case of a very small set current flow angle, it must be taken into account that the voltage u c applied to the capacitor 27 and supplied via the resistor 28 compared to the line voltage U L1 'carried by the phase conductor L1 of the AC network, from which the capacitor voltage u c is derived, lagging out of phase. The diagram of FIG. 2b shows the time profiles of the two voltages u L1 and u c in a half wave, which corresponds to that of the diagram of FIG. 2a between the times t o and t 6 . 2b shows the values of the voltages u c at the capacitor 27 in the phase gating times t 3 , t 4 and t 5 of FIG. 2a before the triggering or discharge of the capacitor 27 by the primary winding 29. It can be seen from this that the voltage u c at the time t 5 shortly before the zero crossing of the mains voltage U L1 at the time t 5 is still comparatively large, so that even if the phase gating device 6 is almost completely controlled back (time t 5 with edge 37 in Fig. 2a), a sufficient ignition pulse power is generated for the ignition of the fluorescent lamp 13. In other words, a reliable ignition of the fluorescent lamp 13 can also be achieved with the present control device 1 if a very small current flow angle, ie a very low brightness of significantly less than 1%, is set with the phase gating device 6.

Wenn bei solchen Verhältnissen eines sehr kleinen eingestellten Stromflusswinkels die an der Anschlussklemme 5 anstehende Netzwechselspannung nicht mehr ausreicht, um in der gezündeten Leuchtstofflampe 13 einen Brennstrom aufrecht zu erhalten, bewirkt die abklingende, über die Sekundärwicklung 32, 33 des Impulstransformators eingespeiste höherfrequente Zündschwingung ein kurzes Weiterbrennen der Leuchtstofflampe 13, so dass eine geringe Lichthelligkeit aufrechterhalten bleibt. Da gemäss dem Diagramm der Fig. 2b mit einer weiteren Verkleinerung des Phasenanschnittwinkels, das heisst einer weiteren Annäherung des Phasenanschnitts an den Nulldurchgang der Netzspannung UL1, die am Kondensator 27 liegende Spannung abnimmtt und somit die Leistung der der Leuchtstofflampe zugeführten höherfrequenten Schwingung abnimmt, erfolgt eine weitere Reduktion der Helligkeit. Dadurch wird es möglich, kontinuierlich eine Minimalhelligkeit von weniger als 0,01 % zu erreichen.If, under such conditions of a very small set current flow angle, the mains AC voltage present at the connecting terminal 5 is no longer sufficient to maintain a combustion current in the ignited fluorescent lamp 13, the decaying effect causes over the secondary winding 32, 33 of the pulse transformer fed in higher-frequency ignition oscillation a short further burning of the fluorescent lamp 13, so that a low light brightness is maintained. Since, according to the diagram in FIG. 2b, with a further reduction in the phase gating angle , that is to say a further approximation of the phase gating to the zero crossing of the mains voltage UL1 , the voltage at the capacitor 27 decreases and thus the power of the higher-frequency oscillation supplied to the fluorescent lamp decreases, a further reduction in brightness. This makes it possible to continuously achieve a minimum brightness of less than 0.01%.

Wenn die Leuchtstofflampe aus dem Zustand geringer Helligkeit in einen Zustand grösserer Helligkeit gesteuert wird, indem mit dem Phasenanschnittgerät 6 ein grösserer Stromflusswinkel gemäss einer Verschiebung vom Zeitpunkt ts zwm Zeitpunkt t4 eingestellt wird, verschiebt sich der Zündmoment nach vorne. Damit wird aber gemäss dem Diagramm der Fig. 2b die am Kondensator 27 liegende Spannung uc grösser. Dies hat die vorteilhafte Folge, dass die Leuchtstofflampe 13 bei eingestelltem höheren Lichtniveau stabil brennt. Durch eine geeignete Wahl der Werte des Widerstands 28 und des Kondensators 27 kann somit eine optimale Phasenverschiebung der am Kondensator 27 liegenden Spannung uc gegenüber der Netzwechselspannung UL1 erhalten werden, wodurch ein stabiles Brennen der Leuchtstofflampe und ein grosser Steuerbereich für deren Helligkeit erzielt wird.If the fluorescent lamp is controlled from the low brightness state to a higher brightness state by setting a larger current flow angle according to a shift from the time t s to the time t 4 with the phase gating device 6, the ignition torque shifts forward. However, according to the diagram in FIG. 2b, the voltage u c across the capacitor 27 is greater. This has the advantageous consequence that the fluorescent lamp 13 burns stably when the higher light level is set. By a suitable choice of the values of the resistor 28 and the capacitor 27, an optimal phase shift of the voltage u c at the capacitor 27 with respect to the mains alternating voltage UL1 can be obtained, whereby a stable burning of the fluorescent lamp and a large control range for its brightness is achieved.

Inbezug auf den zweiten Fall eines maximalen eingestellten Stromflusswinkels, der auch vorliegt, wenn das Phasenanschnittgerät 6 überbrückt wird, liegt an der Anschlussklemme 5 der Steuereinrichtung 1 eine reine Sinusspannung an, da sich die Zeitpunkte t2 und t3 im Diagramm der Fig. 2a einander bis zur Deckung der beiden Flanken annähern. In diesem Fall ist die steile Anschnitttlanke 35 für die Triggerung der Zündschwingung durch die Triggerschaltung 18 und den Triac 30 nicht mehr vorhanden, so dass die Leuchtstofflampe 13 an sich nicht gezündet wird.With regard to the second case of a maximum set current flow angle, which is also present when the phase gating device 6 is bridged, a pure sinusoidal voltage is present at the connection terminal 5 of the control device 1, since the times t 2 and t 3 in the diagram in FIG approximate to cover the two flanks. In this case, the steep gating flank 35 for triggering the ignition oscillation by the trigger circuit 18 and the triac 30 is no longer present, so that the fluorescent lamp 13 itself is not ignited.

Um auch bei einer solchen am Phasenanschnittgerät 6 eingestellten Vollaussteuerung ein sicheres Zünden der Leuchtstofflampe 13 zu erzielen, ist die zweite Triggerschaltung 23 vorgesehen, welche sich die über den beiden Speiseleitungen der Leuchtstofflampe 13 bzw. die am Ueberbrückungskondensator 34 liegende Spannung zunutze macht. Im Normalbetrieb liegt am Kondensator 34 im wesentlichen die Brennspannung der Leuchtstofflampe, welche erheblich kleiner als die Netzspannung UL1 ist. Der Spannungsteiler mit dem Widerstand 24 und dem Kondensator 25 der Triggerschaltung 23 ist so dimensioniert, dass in diesem Fall die über den Widerstand 26 an der Triggerdiode 22 anliegende, geteilte Brennspannung der Leuchtstofflampe 13 die Triggerspannung der Diode 22 nicht erreicht.In order to achieve a reliable ignition of the fluorescent lamp 13 even with such a full modulation set on the phase gating device 6, the second trigger circuit 23 is provided, which takes advantage of the voltage across the two feed lines of the fluorescent lamp 13 or the voltage across the bypass capacitor 34. In normal operation, the operating voltage of the fluorescent lamp is essentially at the capacitor 34, which is considerably lower than the mains voltage UL1 . The voltage divider with the resistor 24 and the capacitor 25 of the trigger circuit 23 is dimensioned such that in this case the divided operating voltage of the fluorescent lamp 13 applied to the trigger diode 22 via the resistor 26 does not reach the trigger voltage of the diode 22.

Wenn aber die Leuchtstofflampe 13 nicht brennt, das heisst durch das Vorschaltgerät 8 kein Strom fliesst, ist die am Ueberbrückungskondensator 34 liegende Spannung bei voll ausgesteuertem Phasenanschnittgerät 6 identisch der Netzspannung UL1' Da diese Spannung wesentlich höher als die Brennspannung der Leuchtstofflampe ist, reicht die am Kondensator 25 liegende Spannung aus, um über die Triggerdiode 22 periodische Einschaltungen des Triac 30 auszulösen, bis aufgrund der dadurch erzeugten gedämpften Schwingungen die Leuchtstofflampe 13 gezündet hat. Sobald die Leuchtstofflampe brennt, wird die zweite Triggerschaltung 23 mangels ausreichender Triggerspannung inaktiv. Hierbei ist noch zu bemerken, dass im Zeitpunkt der Einschaltung des Triac 30, der gemäss dem Diagramm der Fig. 2b etwas vor dem Zeitpunkt t3 liegt bzw. durch entsprechende Wahl der Werte der Bauelemente der Triggerschaltung 23 liegen soll, die Spannung Uc am Kondensator 27 trotz Nacheilung ausreichend gross ist, um einen leistungsstarken Zündimpuls zu erzeugen.If, however, the fluorescent lamp 13 does not burn, i.e. no current flows through the ballast 8, the voltage across the bypass capacitor 34 is identical to the mains voltage U L1 ' when the phase gating device 6 is fully activated. Since this voltage is significantly higher than the burning voltage of the fluorescent lamp, it is sufficient voltage on capacitor 25 to trigger periodic switch-on of triac 30 via trigger diode 22 until fluorescent lamp 13 has ignited due to the damped vibrations generated thereby. As soon as the fluorescent lamp burns, the second trigger circuit 23 becomes inactive due to a lack of sufficient trigger voltage. It should also be noted here that when the triac 30 is switched on, which, according to the diagram in FIG. 2b, is slightly earlier than the time t 3 or should be by appropriate selection of the values of the components of the trigger circuit 23, the voltage Uc at the capacitor 27 is sufficiently large in spite of lag to generate a powerful ignition pulse.

In der Triggerschaltung 18 bestimmt der sich aus den Kondensatoren 20 und 21 zusammensetzende Spannungsteiler im wesentlichen die an die Triggerdiode 22 gelangende Minimalspannung zu deren Steuerung. In Zeitpunkten, in welchen die an der Triggerschaltung 18 anliegende Spannung UPA so hoch ist, dass die Triggerdiode 22 Schaden nehmen könnte, begrenzt der Widerstand 19 den durch die Kondensatoren 20 und 21 fliessenden Strom, so dass die Steuerspannung an der Triggerdiode 22 auf einen sicheren Wert begrenzt wird.In the trigger circuit 18, the voltage divider composed of the capacitors 20 and 21 essentially determines the minimum voltage reaching the trigger diode 22 for its control. At times when the voltage UPA applied to the trigger circuit 18 is so high that the trigger diode 22 could be damaged, the resistor 19 limits the current flowing through the capacitors 20 and 21, so that the control voltage at the trigger diode 22 is safe Value is limited.

Die in Fig. 1 dargestellte Einspeisung der höherfrequenten Zündenergie über die Sekundärwicklungen 32 und 33 in Reihe zum die Leuchtstofflampe 13 speisenden Wechselstromnetz hat an sich den Nachteil, dass die Sekundärwicklungen 32, 33 für den vollen Lampenstrom dimensioniert werden müssen. Statt dieser Reiheneinspeisung ist auch eine Parallelankopplung des Ausgangs des Schwingkreises 31 an den Stromkreis der Leuchtstofflampe 13 möglich. In Fig. 3 ist der für diesen Fall geänderte Teil der Steuereinrichtung 1 der Fig. 1 schematisch dargestellt.The feeding of the higher-frequency ignition energy shown in FIG. 1 via the secondary windings 32 and 33 in series with the AC network feeding the fluorescent lamp 13 has the disadvantage that the secondary windings 32, 33 have to be dimensioned for the full lamp current. Instead of this series feed, a parallel coupling of the output of the resonant circuit 31 to the circuit of the fluorescent lamp 13 is also possible. FIG. 3 schematically shows the part of the control device 1 of FIG. 1 that has been changed for this case.

Der dargestellte Teil zeigt wiederum die Leuchtstofflampe 13 mit Glühkathodenwendeln 11 und 12, welche über Anschlussklemmen 9 bzw 10 von den Sekundärwicklungen 14 und 15 des Heiztransformators 16 der Fig. 1 mit Heizstrom gespeist sind. Ferner ist das über die Anschlussklemmen 7 in die phasenanschnittgesteuerte Netzspeiseleitung geschaltete Vorschaltgerät 8 in Uebereinstimmung mit Fig. 1 dargestellt.The part shown again shows the fluorescent lamp 13 with hot cathode filaments 11 and 12, which are fed with heating current via connecting terminals 9 and 10, respectively, from the secondary windings 14 and 15 of the heating transformer 16 of FIG. 1. Furthermore, the ballast 8 connected via the connection terminals 7 to the phase-controlled mains supply line is shown in accordance with FIG. 1.

Der die zum Schwingkreis 31 der Fig. 1 gehörende Primärwicklung 29 aufweisende Impulstransformator hat eine einzige Sekundärwicklung 38, welche einerseits an die mit der Anschlussklemme 3 für den Nulleiter N (Fig. 1) verbundene Nulleitung angeschlossen und andererseits über einen Kondensator 39 mit der nicht an dieser Nulleitung liegenden Glühkathodenwendel 11 bzw. mit einer der Anschlussklemmen 9 verbunden ist. Der in Fig. 1 dargestellte Ueberbrückungskondensator 34 entfällt selbstverständlich. Die übrigen Schaltungsteile der Fig. 1 sind im wesentlichen unverändert vorhanden (in Fig. 3 nicht dargestellt).The primary transformer 29, which belongs to the resonant circuit 31 of FIG. 1, has a single secondary winding 38, which is connected on the one hand to the neutral line connected to the connecting terminal 3 for the neutral conductor N (FIG. 1) and on the other hand via a capacitor 39 to the neutral line this neutral line lying hot cathode coil 11 or is connected to one of the terminals 9. The Ueber shown in Fig. 1 bridge capacitor 34 is of course omitted. The remaining circuit parts of FIG. 1 are essentially unchanged (not shown in FIG. 3).

Es ist ersichtlich, dass in der Einrichtung nach Fig. 3 die an der Sekundärwicklung 38 auftretende Zündschwingung parallel in den Netzspeisekreis der Leuchtstofflampe 13 eingespeist wird. Zufolge des Sperrkondensators 39, der einen verhältnismässig kleinen Kapazitätswert hat, da er für die Durchleitung der wesentlich höherfrequenten Zündschwingung dimensioniert ist, fliesst der Strom der Leuchtstofflampe 13 nicht über die Sekundärwicklung 38. Dagegen bestehen die Nachteile, dass im Verhältnis zur Kapazität des Kopplungskondensators 39 nicht vernachlässigbare parasitäre Wicklungskapazitäten der Heizsekundärwicklungen 14,15 und des Vorschaltgeräts 8 gegen das Erd- bzw. Nulleiterpotential die verfügbare, effektiv an der Leuchtstofflampe 13 wirksame Spannung der Zündschwingungen herabsetzen, so dass sich weniger gute Zündeigenschaften ergeben. Zudem liegt die Spannnug der Zündschwingungen am Vorschaltgerät 8 an, so dass dessen Wicklung für eine beträchtlich höhere als die eigentliche Betriebsspannung dimensioniert werden muss. Jedoch sind auch mit der Schaltung nach Fig. 3 wesentlich bessere Steuereigenschaften für die Leuchtstofflampe 13, insbesondere bezüglich minimaler Helligkeit, erzielbar, als mit den eingangs erwähnten, bekannten Steuereinrichtungen.It can be seen that in the device according to FIG. 3 the ignition oscillation occurring at the secondary winding 38 is fed in parallel into the mains feed circuit of the fluorescent lamp 13. As a result of the blocking capacitor 39, which has a relatively small capacitance value, since it is dimensioned for the passage of the significantly higher-frequency ignition oscillation, the current of the fluorescent lamp 13 does not flow via the secondary winding 38. On the other hand, there are the disadvantages that, in relation to the capacitance of the coupling capacitor 39, it does not negligible parasitic winding capacitances of the heating secondary windings 14, 15 and of the ballast 8 against the earth or neutral potential reduce the voltage of the ignition oscillations which is effective at the fluorescent lamp 13, so that the ignition properties are less good. In addition, the tension of the ignition vibrations is applied to the ballast 8, so that its winding must be dimensioned for a considerably higher than the actual operating voltage. However, much better control properties for the fluorescent lamp 13, in particular with regard to minimum brightness, can also be achieved with the circuit according to FIG. 3 than with the known control devices mentioned at the outset.

Claims (10)

1. Device for controlling the brightness of fluorescent lamps by means of an adjustable phase control of each voltage halfwave of a feeding alternating-current system, the current switched from the time of the phase control to the next zero transition of the voltage halfwave being supplied via a current-limiting ballast to the fluorescent lamp, the cathodes of the fluorescent lamp furthermore being continuously and uncon- trolledly heated by the alternating current system, and means being provided to supply higher-frequency energy to the fluorescent lamp for its ignition, characterized by a trigger circuit (18) which can be fed by the voltage of the phasecon- trolled halfwave of the system alternating voltage and a damped resonant circuit (31) which can be charged, which is connected to the trigger circuit and to which the fluorescent lamp can be connected with respect to alternating current, the damped oscillation of the resonant circuit (31) triggered by the trigger circuit having a higher frequency than the frequency of the system alternating voltage and exhibiting at the beginning an electric power which is sufficient for igniting the fluorescent lamp.
2. Device according to Claim 1, characterized in that the resonant circuit contains a capacitor and an inductance which can be connected to the capacitor via an electronic switch, the electronic switch being connected to the trigger circuit so that it can be controlled, and in that the capacitor can be connected to the system alternating voltage via a charging resistor before being periodically charged.
3. Device according to Claim 2, characterized in that the inductance is the primary winding of a pulse transformer the at least one secondary winding of which is connected to a feed circuit for the fluorescent lamp.
4. Device according to Claim 3, characterized in that the secondary winding of the pulse transformer is series-connected into the feed circuit for the fluorescent lamp.
5. Device according to Claim 4, characterized in that the pulse transformer has two separate secondary windings which are each connected on one side of connections for the fluorescent lamp into the feed circuit for the fluorescent lamp.
6. Device according to Claim 3, characterized in that the secondary winding of the pulse transformer is connected metallically isolated, for example via a capacitor, in parallel to the feed circuit for the fluorescent lamp.
7. Device according to one of Claims 2 to 6, characterized in that the capacitor of the resonant circuit and its charging resistor are dimensioned in such a manner that the charging voltage present across the capacitor is phase-shifted with lag compared with the system alternating voltage.
8. Device according to one of Claims 1 to 7, characterized in that the trigger circuit, which can be fed by the voltage of the phase-controlled halfwave of the system alternating voltage, contains a voltagedividing resistor-capacitor section and a switching diode.
9. Device according to one of Claims 1 to 8, characterized in that a further trigger circuit for triggering the damped oscillation of the resonant circuit exists which, for its feed, is connected in parallel to the feed circuit for the fluorescent lamp in order to trigger the damped oscillation for igniting the fluorescent lamp when the voltage halfwave of the alternating current system does not have a phase-controlled edge.
10. Device according to Claim 2, characterized in that the further trigger circuit contains a voltagedividing resistor-capacitor section and a switching diode.
EP85810080A 1984-06-21 1985-02-28 Brightness control device for a fluorescent lamp Expired - Lifetime EP0165893B2 (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
AT85810080T ATE42663T1 (en) 1984-06-21 1985-02-28 DEVICE FOR CONTROLLING THE BRIGHTNESS OF FLUORESCENT LAMPS.

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CH301784 1984-06-21
CH3017/84 1984-06-21

Publications (4)

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EP0165893A2 EP0165893A2 (en) 1985-12-27
EP0165893A3 EP0165893A3 (en) 1986-04-09
EP0165893B1 true EP0165893B1 (en) 1989-04-26
EP0165893B2 EP0165893B2 (en) 1993-06-09

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EP85810080A Expired - Lifetime EP0165893B2 (en) 1984-06-21 1985-02-28 Brightness control device for a fluorescent lamp

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EP (1) EP0165893B2 (en)
AT (1) ATE42663T1 (en)
DE (1) DE3569864D1 (en)

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE3826234A1 (en) * 1988-08-02 1990-02-08 Kulzer & Co Gmbh CIRCUIT ARRANGEMENT FOR OPERATING A LOW-PRESSURE GAS DISCHARGE LAMP

Family Cites Families (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4096413A (en) * 1976-02-20 1978-06-20 General Electric Company Flicker eliminating intensity controller for discharge lamp dimming circuit
DE2938529C2 (en) * 1979-09-24 1981-10-15 Siemens AG, 1000 Berlin und 8000 München Ignition and operating device for a high pressure lamp

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EP0165893A2 (en) 1985-12-27
EP0165893B2 (en) 1993-06-09
DE3569864D1 (en) 1989-06-01
EP0165893A3 (en) 1986-04-09
ATE42663T1 (en) 1989-05-15

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