EP0043591A1 - Antenne - Google Patents

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Publication number
EP0043591A1
EP0043591A1 EP81105311A EP81105311A EP0043591A1 EP 0043591 A1 EP0043591 A1 EP 0043591A1 EP 81105311 A EP81105311 A EP 81105311A EP 81105311 A EP81105311 A EP 81105311A EP 0043591 A1 EP0043591 A1 EP 0043591A1
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European Patent Office
Prior art keywords
antenna
helix
loop
conductor
toroidal
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EP81105311A
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German (de)
English (en)
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James F. Corum
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Individual
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Individual
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q7/00—Loop antennas with a substantially uniform current distribution around the loop and having a directional radiation pattern in a plane perpendicular to the plane of the loop
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/16—Resonant antennas with feed intermediate between the extremities of the antenna, e.g. centre-fed dipole
    • H01Q9/26—Resonant antennas with feed intermediate between the extremities of the antenna, e.g. centre-fed dipole with folded element or elements, the folded parts being spaced apart a small fraction of operating wavelength
    • H01Q9/265—Open ring dipoles; Circular dipoles

Definitions

  • My invention relates to antennas used for either transmitting or receiving or both.
  • an antenna The main purpose of an antenna is to transmit electromagnetic energy into (or receive electromagnetic energy from) the surrounding space effectively.
  • a transmitting antenna launches electromagnetic waves into space and a receiving antenna captures-radiation, converting the electromagnetic field energy into an appropriate form (e.g. - a voltage to be fed to the input of a receiver).
  • a transmitting antenna converts the radio frequency (RF) energy fed by a generator connected to its input into electromagnetic radiation. This radiation carries the generator's energy away into space.
  • the generator is giving up energy to a load impedance.
  • this load impedance may be replaced by a lumped element which merely dissipates the energy which the previous antenna radiated away.
  • antenna efficiency The equivalent resistor, which would dissipate the same power as the antenna radiated away, is called the "antenna radiation resistance”.
  • an antenna structure has losses (power dissipating mechanisms) due to the structure's finite conductivity, imperfect insulation, moisture and physical environment. To the generator, these loss mechanisms absorb some of the power fed into the antenna structure, so that all of the input power is not radiated away. The ratio of the radiated power to antenna structure input power is called the antenna efficiency.
  • Typical vertical antennas must be on the order of one-eighth to one- quarter of a free space wavelength high in order to have R A large enough to be considered as efficient antennas -- . unless extensive measures are taken to make R L negligible.
  • a vertically polarized antenna structure is often the most desirable or only acceptable solution (in spite of the physical and economical disadvantages).
  • the single vertical radiator has another feature which is often desirable. It is omnidirectional in the horizontal plane - that is, equal amounts of vertically polarized radiation are sent out in all directions on the horizontal plane.
  • antenna pattern an array of towers or antenna elements spaced an appreciable portion of a wavelength may be used to direct the radiation.
  • the resultant physical distribution of the electric field intensity in space is called the antenna pattern.
  • antenna gain is defined as the ratio of the maximum field intensity produced by a given antenna too the maximum field intensity produced by a reference antenna with the same power input.
  • An additional antenna property is antenna resonance.
  • the voltage and current at the antenna terminals are complex quantities; that is, they have real and imaginary mathematical components.
  • the ratio of the complex voltage to the complex current at the terminals is called the antenna input impedance.
  • the generator frequency is varied (or alternatively, if the generator frequency is fixed and the antenna dimensions are varied) there will be a particular frequency (or antenna dimension) for which the voltage and current are in phase.
  • the impedance will be purely resistive and the antenna is said to be resonant.
  • a resonant antenna structure is one which will support a standing wave current distribution which has an integral number of nodes.
  • An antenna will radiate at any frequency for which it will accept power.
  • the advantage of having a resonant antenna structure is that it is easier to match to the generator for efficient power transfer. This means that the system losses can be decreased and, hence, the overall system efficiency is increased at resonance.
  • a vertical tower for example, is not self-resonant unless it is electrically one quarter wavelength tall. At a frequency of 550 KHz (the low end of the AM broadcast band) a self-resonant tower must be about 447 feet tall. At 15 KHz it would have to be 16,405 feet tall:
  • My invention is not a toroidal inductor.
  • a perfect toroidal inductor has zero radiation efficiency, and so is not an antenna at all.
  • My invention is not what is commonly termed “the small loop antenna”, which produces the well-known azimuthally directed (horizontal) electric field with a sin e pattern, where 9 is the angle of from the spherical coordinate polar axis, where the loop lies in the azimuthal plane.
  • My invention is not what is commonly called a "normal mode helix”; which is a solenoidally wound structure, having a distinct beginning and ending to the helix.
  • My invention is not what is commonly called the “multiturn loop antenna”, which has multiple windings which either lie in the azimuthal plane or are coiled along the loop's axis of symmetry.
  • a solenoidally wound coil or helix is shown in Figure l(a).
  • the antenna current to be uniform in magnitude and constant in phase over the entire length of the helix
  • Kraus has shown that a normal mode helix (one whose dimensions are much less than a free space wavelength and that radiates normal to the solenoid axis) may be decomposed into a single small loop as in Figure l(b) plus a single short dipole as in Figure l(c).
  • a normal mode helix one whose dimensions are much less than a free space wavelength and that radiates normal to the solenoid axis
  • Equation (1) There is an alternative way to derive Equation (1) which proceeds from the introduction of a fictitious conceptual aid.
  • This very useful tool is a great assistance to performing field computations for helices and solenoids.
  • Kraus has shown that a loop of electric current, i.e., -electric charges flowing around the circumference of a loop, produces the same radiation fields as those of a flow of fictitious magnetic charges moving up and down the axis of the loop.
  • the fields external to a helically wound solenoid can be found by assuming a flow of electric charges around the helix, or by assuming a flow of fictitious magnetic charges moving along the axis of the solenoid.
  • the latter computation is much simpler to perform analytically than the former.
  • Figure 2 shows the different types of polarization obtainable from a normal mode helix.
  • Figure 2(a) is the general case of elliptical polarization.
  • antennas in my invention are important features that even though they can have a much smaller physical size than prior antennas, they can transmit or receive electromagnetic waves with a very high antenna efficiency.
  • the antennas of the invention possess greater radiation resistance and radiation efficiency than loop antennas of similar size.
  • antennas according to the invention radiate controllable mixtures of vertically, horizontally and elliptically polarized electromagnetic waves and possess radiation power patterns different from those produced by small loop antennas.
  • Antennas according to preferred embodiments of the invention are configured to behave as slow wave devices.
  • the antennas are configured to establish a closed, standing wave path.
  • the conductor configuration and the path established thereby inhibit the velocity of propogation of electromagnetic waves, and the path supports the standing wave at a pre-selected frequency.
  • the preferred embodiments of the invention described herein include various arrangements of conductors arranged in loop configurations; but the conductor or conductors are configured so that they are not arranged in simple circles, and rather are wound about real or imaginary support forms to increase the length of the physical path of the conductor while maintaining a relatively compact antenna.
  • the path in each case is configured to inhibit the velocity of the electromagnetic wave and to support a standing wave at a pre-selected frequency.
  • An antenna comprises an electrical conductor configured with multiple, progressive windings in a closed or,substantially closed geometrical shape.
  • This shape can be established by a physical support form or it can be a geometrical location as where the antenna has self-supporting conductors.
  • Such a shape can be topologically termed a "multiply connected geometry"; for example, a conductor can be in the form of more than one winding in a geometrically closed configuration or multiply connected geometry.
  • the cross-section of this configuration can be circular (as where the configuration is a toroidal helix), or it can have the general form of an ellipse, a polygon, or other shapes not generally circular in cross-section; the configuration can be symmetrical or assymmetrical, polygonal, and it can be essentially two dimensional or configured in three dimensions.
  • a quadrifiliarly wound toroidal helical antenna according to the invention is shown in perspective.
  • Fig. 16 shows the RMS filed pattern produced by a toroidal loop antenna of the type producing the pattern of Fig. 8, but with its feed point rotated 90° from the antenna to which Fig. 8 relates.
  • Figure 4 shows an antenna 41 which is an embodiment of my invention.
  • An electrical conductor 42 which can be, for example, an elongated conductor such as a length of conducting tape, wire or tubing is helically wound about a non-conducting toroidally shaped support 43.
  • the turn-to-turn spacing "s" between each winding is uniform.
  • the dimension “b” i's the radius of each winding and 2b may be termed the "minor diameter" of the antenna.
  • the dimension "a” is the radius of the circle which comprises the centerline axis 44 of the toroid.
  • Figures 5(a), 5(b), 5(c) show an antenna 51 similar to antenna 41, but adapted to balanced feed.
  • the helically wound conductor 52 is not continuous, but rather has two ends 52a, 52b which are used as the feed point taps for the antenna.
  • these ends 52a, 52b are as close to each other as possible without electrically interfering with each other.
  • These ends 52a, 52b should be near each other, that is, the ends should be near enough that the electromagnetic waves on the antenna follow a closed path.
  • Figure 6 shows another toroidal helix antenna 61, which is adapted for unbalanced feed from an unbalanced transmission line 62.
  • the conductor 63 is continuous.
  • a sliding tap 65 connects the two conductors 63, 64.
  • One side of the transmission-line is connected to one end of the shorter conductor 64 and the other side is attached to the continuous conductor 63.
  • the sliding tap 65 is moved to a point for proper impedance matching. This point is found empirically by actually testing the antenna at the chosen frequency and moving the sliding tap 65 to the optimum position.
  • helical structures possess the property that electromagnetic waves propagating on them travel with velocities much less than waves propagating in free space or on wires.
  • the helix diameter and pitch By properly choosing the helix diameter and pitch, one.can control the velocity of propagation in a manner well known in the science of transmission line engineering. Since the velocity of propagation for these traveling waves on helical structures is much less than that of waves traveling in free space, the wavelength ⁇ G of a wave on the helix will be much less than the wavelength X o for a wave traveling in free space at the same frequency.
  • the slow wave feature of helices which is employed in the toroidal loop antennas of my invention permits the construction of a resonant structure whose circumference is much less than a free space wavelength, but whose electrical circumference is nevertheless electrically a full wavelength. Such a structure is resonant.
  • categories or types of antennas :
  • the toroidal loop embodiments of my invention behave as the superposition of a loop of magnetic current and a loop of electric current.
  • the electric loop component generates a horizontally polarized radiation field
  • the magnetic loop component generates a vertically polarized radiation field.
  • the current distribution is non- uniformly distributed along the azimuthal angle ⁇ .
  • the helix can be decomposed into a continuous loop of (simusoidally distributed) electric current plus a continuous loop of (sinusoidally distributed) magnetic current.
  • the radiation properties can then be ascertained by employing the principle of superposition. The following discussion proceeds through these separate computations and combines them to determine the toroidal loop's radiation properties.
  • An element of the ring of current has an electric dipole moment where P is the electric dipole moment per unit length of the wire.
  • the electric and magnetic fields are related to the potentials as where ⁇ is the permeability of space, and X is a vector potential, where V is a scalar potential, and in the radiation zone, where Z o is the characteristic impedance of free space.
  • ⁇ is the phase constant and ⁇ o is the permeability of free space. so that Equation (13) now leads to
  • the first integral will vanish because the integrand is odd.
  • Equation (26) becomes
  • Equations (24) and (33) must now be substituted back into Equation (3).
  • An element of the ring of magnetic current has a magnetic dipole moment where P m is the magnetic dipole moment per unit length of the source. From Maxwell's equations we have where E is the permeability of the medium. where F is the electric vector potential. This time which can he written as whence One writes this out explicitly as
  • the analysis so far has prepared the way so that one can consider the toroidal helix to be composed of a single resonant magnetic loop (due to an actual solenoidal flow of electric charge around the rim of the torus) plus a single resonant electric loop (due to the electric charge flowing along the turn-to-turn spacing of the helix).
  • This is the basic assumption for the present analysis of the toroidal loop antenna.
  • a more rigorous analysis could be made by assuming a spiral electric current around the helically wound torus. Such an analysis would require a great deal more effort but would probably be desirable for near field effects. However, the radiation zone effects should be consistent with this approximate analysis.
  • Equation (45) The radiation fields of the helically wound toroidal loop antenna are given by the linear superposition indicated in Equation (45) where the component fields are'taken from Equations (24), (33), (43) and (44). These results are collected here for later reference.
  • Equation (35) vanishes.
  • the radiation fields then reduce to the classical loop field of Equation (1).
  • the average power delivered to a resistive load by a sinusoidal source is
  • Equating Equations (54) and (55) gives an expression for the radiation resistance as
  • an omnidirectional vertically polarized radiating element is desired.
  • the previous embodiment demonstrates how an antenna constructed of two toroidal loops could produce a figure eight vertically polarized radiation field. If one now takes a second pair, that are also arranged to produce vertical polarization, and excited them and the previous pair with currents of equal magnitude but in phase quadrature (i.e., a 90 degree phase shift), the resultant field would be given by the expression which reduces to
  • the maximum amplitude of Eg is unity at some instant during each cycle.
  • the RMS field pattern is azimuthally symmetric as shown by the circle in Figure 14. The pattern rotates as a function of time, completing one revolution per RF cycle.
  • so-called “turnstile antennas”, that is, the use of multiple antennas with varying currents but with constant phase differences to obtain an antenna with omnidirectional coverage, are not new. See Kraus, Antennas, supra, at page 424 and G. H. Brown, "The Turnstile Antenna", Electronics, April, 1936.
  • the embodiments of my invention now under discussion differ from the foregoing prior art by using toroidal loops instead of other elements.
  • Figure 15 shows an embodiment for implementing this method for obtaining omnidirectional vertical polarization.
  • Figure 15(a) shows a quadrifilarly wound toroidal helix phased for producing omnidirectional vertical polarization (that is, perpendicular to the plane of the torus). This configuration is obtained by superimposing two bifilar helices, each of the type shown in Figure 13, and feeding them in phase quadrature.
  • Figure 15(b) shows schematically the feed distribution for the antenna of Figure 15(a).
  • Omnidirectional horizontal polarization may be produced by feeding bidirectional horizontal polarization elements in an analagous manner.
  • Toroidal loops may be arranged so as to produce a circularly polarized radiation field.
  • the antenna pattern of Figure 8 produced by the basic toroidal loop.
  • a second loop is constructed but with its current distribution (that is, the feed points) rotated by 90 degrees.
  • the second toroidal loop produces the pattern shown in Figure 16.
  • the superposition of these two patterns will produce circular polarization in the azimuthal plane if the two loops are excited in phase quadrature.
  • Omnidirectional circular polarization can be produced by rotating the antennas producing the pattern of Figure 10 by 90 degrees and feeding them in phase quadrature with the antennas producing the pattern of Figure 12.
  • AM broadcast stations employ an array of several vertical towers spaced some portion of the wavelength and directly excited with various amplitudes and phase shifted currents. Such antennas are called driven arrays.
  • the fields from the driven element induce currents on these other elements, which have no direct electrical transmission line connection to a generator.
  • Such elements are called parasitic elements, and the antenna system is called a parasitic array.
  • the toroidal loop may be employed in both the driven array and parasitic array configurations.
  • the entire array, or only portions of it, may be constructed of toroidal loops.
  • the driven element is a resonant linear element 1701 and the parasitic element is a tuned parasitically excited toroidal loop 1702.
  • Parasitic arrays have been constructed entirely of toroidal loops as in Figure 18, which shows configuration for a typical two element toroidal loop parasitic array.
  • the center toroidal loop 1801 is resonant at the frequency of interest and the parasitic element 1802 tuned as a director (resonated about 10% higher in frequency) and with a mean diameter about one-tenth of a wavelength greater than the mean diameter of the driven element for the given frequency of interest.
  • toroidal loop configurations can be constructed and typical resonant resistances can be varied (typically between a hundred ohms to several thousand ohms), depending upon the values a, b, and s and the order of the mode n excited on the loop as these terms were used in the equations herein. The variation of these parameters has also. permitted a variety of polarization types and radiation patterns.
  • Example A a conceptual elementary toroidal loop antenna for use with a home FM receiver.
  • the fields can be determined from Equations 50 and they will be elliptically polarized with different axial ratios in different directions.
  • Example B - a conceptual toroidal loop for use at LF.
  • the desired operating frequency is 150 KHz.
  • ⁇ o 2,000 meters or 6,562 feet.
  • the major radius is
  • the antenna was constructed as in Figure 5.
  • the vertical polarization scheme of Figure 13 has been built and measured.
  • the bifilarly wound loop was fed at AA'.
  • the ratio of vertical to horizontal polarization field strength (or axial ratio) was 46. That is, the polarization produced was predominantly vertically polarized.
  • the antenna's VSWR was measured through a 4 to 1 balun transformer and 50 ohm coaxial cable. The VSWR curves are shown in Figures 20 and 21 for two separate resonances of the antenna.
  • the loop was constructed at a mean height of 3.5 ft. above soil with a measured conductivity of 2 milli- mhos/meter.
  • the graph shows two sets of curves.
  • One set of curves 2201 shows the feed point impedance vs. frequency for the situation where 40 twenty foot long conducting ground radials were symmetrically placed below the torus at ground level.
  • the second set of curves 2202 shows the same data for the case where the ground radials have been removed.
  • the conducting ground plane has very little effect on the feed point impedance. This is to be expected if the electric current tends to zero and the major fields are produced by the magnetic current, 1 m .
  • the theory which was developed above was for an isolated single toroidal helix. It would be applicable to multifilar helices if mutual effects are neglectable.
  • An HF toroidal loop was constructed in a rectangular shape with 116 equally spaced turns of #18 gauge wire wound on a 2 1/2 inch (O.D.) plastic pipe form.
  • the rectangle was 27 inches by 27 inches and the feed point was at the center of one leg of the rectangle. See Figure 23.
  • the feed point impedance was measured and is shown in Figure 24.
  • the resonant frequency for this structure occurs where the reactive component of the impedance vanishes: 27.42 MHz.
  • a VHF parasitic array was constructed from a driven resonant quarter wavelength stub (above a 2 wavelength diameter ground plane) and a parasitically excited toroidal loop, as in Figure 17.
  • the loop had a major radius of 1/10 wavelength and was tuned to resonate at a frequency 10% higher than the driven linear element.
  • the measured gain over the driven element alone was 4 db.
  • the array was constructed at 450 MHz.
  • a structure consisting of two helices wound in opposite directions at the same radius is called a contrawound helix.
  • Slow wave devices have been constructed as contrawound helices (operating as non-radiating transmission lines, or as elements in traveling wave tubes). See C.K. Birdsall and-T.E. Everhart, "Modified Contrawound Helix Circuits for Hihg Power Traveling Wave Tubes", Institute of Radio Engineers Transactions on Electron Devices, ED-3, October, 1956, P. 190. See Figures 25a and 25b.
  • I have constructed contrawound helices as in Figure 25b and pulled them into the form of a closed torus and operated them, not as transmission lines, but as resonant radiating toroidal helix antennas.
  • Figure 25b shows three additional useful parameters: the ring thickness "rt”; the angular arc “aa”; and the slot width "sw".
  • the ring thickness was 1/2"
  • the angular arc was about 25°
  • the slot width was 1/4".
  • the 78 turn device operated as a resonant antenna structure at 85 MHz with a radiation. resistance of approximately 300 ohms.
  • Example 9 Contrawound Helical Torus for Producing Vertical Polarization.
  • it is necessary to establish a uniform magnetic current along the helical structure in order to make n 0 and cancel out the E: component in the radiation field.
  • This mode of operation is especially appealing for VLF antennas.
  • Such a device was constructed as shown in Figure 27 of #10 gauge copper wire.
  • the major radius of the 32 turn toroidal helix was 4-3/4", the minor (or ring) radius was 11/16", the slot width was 3/4", the ring thickness was 1/8" and the resonant frequency was measured as 135 MHz.
  • the antenna of Figure 27 is made by bending the helix of Figure 25b around into a toroid and then dividing it into four parts 2701, 2702, 2703, 2704.
  • This arrangement is the-magnetic current analog to the electric current "cloverleaf” antenna.
  • the electric loop cloverleaf antenna see Kraus, Antennas, supra, P. 429 and P.H. Smith, "Cloverleaf Antenna for FM Broadcasting", Proceedings of the Institute of Radio Engineers, Vol. 35, PP. 1556-1563, December, 1947.
  • the feed currents cancel, producing no radiation fields and the contrawound resonant toroidal helix supports an effective azimuthally uniform magnetic current which produces the omnidirectional vertically polarized radiation.
  • This structure would also be appropriate as an element in a phase array configuration.
  • Figure 28 shows an embodiment of my invention in which a variable capacitor 2801 is used as a means for varying or tuning the resonant frequency of the antenna without changing the number of turns of the antenna.
  • the antenna of Figure 28 consists of two toroidal helices. One is fed at points AA' and the other at CC'.
  • the variable capacitor 2801 is placed across the feed points CC'. As the capacitance is varied, the resonant frequency of the antenna is varied.
  • the helix on a torus winding feature permits the formation of a resonant antenna current standing wave in a region of electrically small dimensions, and it permits the controlled variation of antenna currents, resonant frequency, impedance, polarization and antenna pattern.
  • the helices can have right-hand windings, left-hand windings, bifilar windings in the same direction (both right-hand or both left-hand), or bifilar windings which are contrawound (one right-hand, one left-hand).
  • the toroidal helices can be used with other configurations of the conducting means as well.
  • an electrical conducting means cause the antenna system to function as a slow wave device according to the invention, with a velocity factor less than 1 (i.e. V f ⁇ 1).
  • the electrical conducting means should be configured to establish a closed standing electromagnetic wave path, the path inhibiting the velocity of propogation of electromagnetic waves and supporting a standing wave at a predetermined resonant frequency.
  • Such configuration should have a substantially closed loop geometry. Such geometry could be described as being multiply connected.
  • the electrical conducting means would not have an essentially linear shape, and it would not be a simple circle lying substantially in a single plane (in a strict mathematical sense, a wire'or other elongated conductor would necessarily be 3 dimensional and extending in more than one plane, but for the purposes of this discussion an antenna is considered to lie in one plane if it could rest on a flat surface and not rise from that surface more than a small fraction of its length - i.e. a conductor is considered as lying in one plane if in ordinary parlance it could be described as being flat).
  • a simple ring shaped conductor 3401 of the type shown in Fig. 34 would not satisfy the criteria of the invention.
  • a conductor 2901' has a wavey pattern. and extends around a non-conducting toroidal support 2902.
  • a conductor 3001 is shown in Fig. 30 having a zig-zag shape and is disposed around an imaginary cylinder.
  • Another zig-zag arrangement is shown in Fig. 31, where a conductor 3101 lies in a single plane.
  • the conducting means can lie in a single plane so long as it is noncircular. (It could be circular in projection, if it lies in more than one plane).
  • the conducting means could have linear and curved components, such as the configuration 3201 in Fig. 32.
  • the conducting means need not be a single .element or even a plurality of physically connected elements; for example, the antenna-3301 of Fig. 33 comprises a plurality of spaced rings 3302 arranged about a circle. Rings 3302 would be inductively coupled in response to the transmission of electromagnetic waves in antenna 3301.
  • the various antenna arrangements of Figs. 29-33 must be dimensioned and have the characteristics to fulfill the requirement that they establish a closed standing wave path for electromagnetic waves, which path inhibits the velocity of'the waves along the path and supports a standing wave at a preselected resonant frequency.
  • the invention may be summarized as follows:

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EP81105311A 1980-07-09 1981-07-09 Antenne Withdrawn EP0043591A1 (fr)

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US167329 1980-07-09

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US5734353A (en) * 1995-08-14 1998-03-31 Vortekx P.C. Contrawound toroidal helical antenna
US6218998B1 (en) 1998-08-19 2001-04-17 Vortekx, Inc. Toroidal helical antenna
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JP3877408B2 (ja) * 1997-12-25 2007-02-07 三菱電機株式会社 車載用冷却器
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DE443959C (de) * 1919-01-30 1927-05-13 Augustus Taylor Richtantennensystem
US1615755A (en) * 1925-11-11 1927-01-25 George T Kemp Loop antenna
US1803620A (en) * 1927-03-25 1931-05-05 Smith M Jester Antenna
DE864707C (de) * 1950-11-28 1953-01-26 Hans Schieren Ultrakurzwellen-Falt-Dipol-Antenne
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US3235805A (en) * 1957-04-01 1966-02-15 Donald L Hings Omnipole antenna
DE1129191B (de) * 1960-12-14 1962-05-10 Siemens Ag Richtantenne fuer sehr kurze elektromagnetische Wellen
US3122747A (en) * 1961-12-21 1964-02-25 Dominion Electrohome Ind Ltd Multi-turn loop antenna with helical twist to increase the signal-to-noise ratio
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Cited By (37)

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EP0544136A1 (fr) * 1991-11-14 1993-06-02 Compagnie Generale Des Etablissements Michelin-Michelin & Cie Structure d'antenne adaptée pour la communication avec une étiquette électronique implantée dans un pneumatique
US5319354A (en) * 1991-11-14 1994-06-07 Compagnie Generale Des Etablissements Michelin-Michelin & Cie Antenna structure for communicating with an electronic tag implanted in a pneumatic tire
FR2683951A1 (fr) * 1991-11-14 1993-05-21 Michelin & Cie Structure d'antenne adaptee pour la communication avec une etiquette electronique implantee dans un pneumatique.
US6028558A (en) * 1992-12-15 2000-02-22 Van Voorhies; Kurt L. Toroidal antenna
US6204821B1 (en) 1992-12-15 2001-03-20 West Virginia University Toroidal antenna
US5654723A (en) * 1992-12-15 1997-08-05 West Virginia University Contrawound antenna
AU706459B2 (en) * 1995-06-07 1999-06-17 West Virginia University Contrawound antenna
WO1996041397A1 (fr) * 1995-06-07 1996-12-19 West Virginia University Antenne a bobinages a sens d'enroulement opposes
KR100416630B1 (ko) * 1995-06-07 2004-07-01 웨스트 버지니아 유니버시티 콘트라와운드안테나
AU699283B2 (en) * 1995-06-07 1998-11-26 West Virginia University Toroidal antenna
KR100416631B1 (ko) * 1995-06-07 2004-06-04 웨스트 버지니아 유니버시티 환형안테나
WO1996041398A1 (fr) * 1995-06-07 1996-12-19 West Virginia University Antenne toroïdale
US5734353A (en) * 1995-08-14 1998-03-31 Vortekx P.C. Contrawound toroidal helical antenna
EP0870344A1 (fr) * 1995-08-14 1998-10-14 VorteKx P.C. Antenne helicoidale toroidale a contre-spiralage
US6239760B1 (en) 1995-08-14 2001-05-29 Vortekx, Inc. Contrawound toroidal helical antenna
US5952978A (en) * 1995-08-14 1999-09-14 Vortekx, Inc. Contrawound toroidal antenna
EP0870344A4 (fr) * 1995-08-14 1998-10-14
US6320550B1 (en) 1998-04-06 2001-11-20 Vortekx, Inc. Contrawound helical antenna
US6218998B1 (en) 1998-08-19 2001-04-17 Vortekx, Inc. Toroidal helical antenna
US6300920B1 (en) 2000-08-10 2001-10-09 West Virginia University Electromagnetic antenna
US6437751B1 (en) 2000-08-15 2002-08-20 West Virginia University Contrawound antenna
US6593900B1 (en) 2002-03-04 2003-07-15 West Virginia University Flexible printed circuit board antenna
US9515369B2 (en) 2005-02-18 2016-12-06 Cpg Technologies, Llc Use of electrical power multiplication for power smoothing in power distribution
US8629734B2 (en) 2005-02-18 2014-01-14 Cpg Technologies, Llc Systems and methods for power smoothing in power distribution
US8638182B2 (en) 2005-02-18 2014-01-28 Cpg Technologies, Llc. Systems and methods for electrical power multiplication
US9118216B2 (en) 2005-02-18 2015-08-25 Cpg Technologies, Llc Parametric power multiplication
US9513652B2 (en) 2005-02-18 2016-12-06 Cpg Technologies, Llc Electrical power multiplication
US7808124B2 (en) 2007-02-02 2010-10-05 Cpg Technologies, Llc Electric power storage
US7969042B2 (en) 2007-02-02 2011-06-28 Cpg Technologies, Llc Application of power multiplication to electric power distribution
US8310093B1 (en) 2008-05-08 2012-11-13 Corum James F Multiply-connected power processing
US8716890B1 (en) 2008-05-08 2014-05-06 Cpg Technologies, Llc. Multiply-connected power processing
US9407095B2 (en) 2008-05-08 2016-08-02 Cpg Technologies, Llc Multiply-connected power processing
RU2492560C2 (ru) * 2011-03-18 2013-09-10 Общество с ограниченной ответственностью "Скоростные Системы Связи" Антенна
WO2017044287A1 (fr) 2015-09-10 2017-03-16 Cpg Technologies, Llc. Émission par réseau à déphasage hybride
CN108352594A (zh) * 2015-09-10 2018-07-31 Cpg技术有限责任公司 混合相控阵传输
CN111585017A (zh) * 2020-05-15 2020-08-25 广东工业大学 一种法向模螺旋天线
CN113300093A (zh) * 2021-06-18 2021-08-24 广东工业大学 一种全向圆极化辐射介质螺旋天线

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CA1186049A (fr) 1985-04-23
AU7264481A (en) 1982-01-14
AU548541B2 (en) 1985-12-19

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