DE1937412A1 - Ballistics calculator - Google Patents

Description

Applicant; Stuttgartj July 21, 1969

Hughes Aircraft Company P 2015 S / kg Centinela and Teale Street
Culver City, Calif., V.St.A.

Ballistics calculator

The invention "relates to a ballistics calculator for use with a distance measuring circuit, ~ d "i: e a distance signal is generated

In known ballistic computers, the distance information was previously fed to a computing circuit which generated output _{signals relating to the ballistics of a projectile 8} if the physical parameters such as projectile speed, ambient atmospheric conditions, gravity, shape, mass and spin of the projectile are known or accepted

009809/1507

- 2 - -

was. In general, these signals were generated by function generators that were specially designed for a certain type of projectile. For example, puncture generators have been established that made use of electromechanical range tracking servos to adjust padded range function potentiometers. Since other projectiles because of other speeds, masses, shapes and the like other W may have ballistic properties, it was necessary to change the function generator so that the output signals generated below the ballistic properties of the new floor in the desired relationship were "

The effects of deviations of the variables from their standard values have heretofore been treated by one of three methods when these deviations were small with respect to the absolute values. These methods consisted in disregarding such deviations, in fully mechanizing the circuit, regardless of the be- fc. ■ ■ limited the dynamic range of the variables, and to mechanize the circuit with a Taylor approximation of the first order. For the general case of several variables such as F (u, v, w), the mechanization equation for the Taylor method is F (u ₀ , v _Q , w _q ) + F * (u, v _q , w _q ) (u-Uq ) + F '(v »U ₀ TW ₀ ) (V- ^ v ₀ ) + F' (w, u _Q , VqXw-Wq). To mechanize this equation it is necessary to use the function Pi U ₀ , V ₀ , Wq) for standard conditions and the partial derivatives F '(u, V ₀ , Wq), F ^r (v, Uq, W ₀ and F ^r ( w, Uq, V ₀ ) to mechanize, each of the partial derivatives with the corresponding change in their _: variables to multiply and the four terms to be

■■ '- V - ■, ■ -. ■ ^; '■' ■ - ■ -. '■■' ■■ - .. - - ^; ■■■■■ .. "■" * / · ■■■■:. ■ ■: ■■■

009809/1507

add up, so it was necessary. To create function generators for each partial derivative ^: and to add these partial derivatives to the function · Furthermore, this method has the consequence that a change in one variable has no noticeable influence on the effect caused by the change in another variable.

In contrast, the invention is based on the object to create an improved ballistics calculator that is able to generate signals related to the function of the input signals for standard conditions and Deviations from the standard conditions in relation stand. Furthermore, the generator should be able to perform such BallX3tik functions for a variety of different To generate GoschoBarten

This object is achieved according to the invention by a ballistics computer, which is characterized by a first multiplication device which multiplies the distance gas signal by a ballistic .. ^f Jerm, which is characteristic of the properties of a certain projectile and special environmental conditions, and thereby a generated normalized range signal, a second multiplier which multiplies the normalized range signal by a first and a second function, which functions are applicable to projectiles and are independent of the projectile properties and the environmental conditions, and thereby generates a first and a second ballistic function signal, a

■; "■. ■" ■■ .- .- ■ '■ "." ■ ./· V 009809/1507

- A -. "■■" ■ - ''■■; ■: ■■■ ^:

third and fourth multipliers, one of which is the first and the other the second ballistic function signal with a ..term. multiplied that for the properties of the special bullet and the special environmental conditions is characteristic, and thereby a time-of-flight signal or an attachment angle signal generated, and a constant multiplier, which is optional the time-of-flight signal and / or the attachment angle signal are multiplied by constants, thereby making corrections for ballistic deviations based on deviating ballistic and environmental conditions · -.

In the ballistic computer according to the invention, selected ballistic conditions are accordingly used as constants processed to correct ballistic angular deviations and kinematic angles. This will be achieved the advantages that a small number of function generators sufficient to assign functions of an input signal with one or more variables produce that deviations from standard conditions such as air density as a result of changes in the atmosphere spherical pressure and temperature, deviations in air resistance as a result of changes in the Mach number caused by changes in air temperature changes in muzzle velocity due to tube wear and propellant temperature, and Changes in crosswind and headwind coefficients caused by the changes specified above, be compensated outside of the function generation * can, and that the ballistics calculator according to the invention

009809/1507

even to a realization in solid-state construction leads, simplified compared to other known arrangements and is small in size.

In a further embodiment of the invention, the Computers have one or more parallel channels, from which each channel receives input information, such as a distance signal if the computer is designed as a ballistic computer. the Distance information R for several of the channels is by an adjustable ballistic term multiplier which normalizes the distance information R with a specific distance normalization element R, which is derived from standard ballistic and atmospheric conditions for each type of projectile. After that, the normalized distance information R / R passed through a multiplier circuit that divides the signal with the partial derivative of the vom Standard deviating air temperature and the air pressure deviating from the standard multiplied. in the In the general case, the multiplication factor is a delay-free partial approximation of the first Order (1 + Kr ~) of a partial derivative. Who as in a common case,

f (u) ο u ^k ,
then

f '(u) »ξ f (u)
and

_k .

under the conditions

Au << u
^and 009809/1507

In a ballistic style calculator there is the delay-free partial derivative for changes AR in the normalization term 1 / R _n as a result of variations in the air pressure AP and in the air temperature 6T. As a result, the delay-free correction factor AK _n

(1 ± -TT- ') · With other words the function is activated with multiplied by a GXied that depends on the ratio of the condition change to produce a product, and also added to this product. Since it has also been found that the normalization term

i / r
'η is inversely proportional to a function of the air temperature T and proportional to the air pressure P, the factor AR _n ZR _{n is} proportional to ΔΡ / Ρ - k & T / T. The partially corrected signal is then fed in parallel on each of said channels to a function generator which processes the normalized range signal according to a function which is itself normalized and is therefore related to the ballistics of a plurality of projectiles. The output signal of each individual function generator is then fed to a different, individually adjustable ballistic term multiplier, which processes the received function signal and generates an output signal that is characteristic of a selected projectile. and an attachment angle information £ q, which inromations are related to the ballistics of the selected projectile at the specific distance.By setting the two multipliers, the ballistic terms are changed to those assigned to a different projectile type *

009809/150?

Both the attachment angle signal and the plug time signal are passed through the multiplier circuit, which multiplies these signals by the partial derivative of a temperature deviating from normal temperature and a pressure deviating from normal pressure, and through another multiplier circuit which continues to multiply by. a first order approximation (1 + k- ^) of a partial derivative of a propellant charge temperature deviating from the noriaal value and an effective full charge, after which the attachment angle signal and the time-of-flight signal are corrected for the conditions deviating from the standard. Since it is more a matter of the partial derivative of the initial speed V _Q , the partial derivative is characteristic of changes in the initial speed ΔV «, which are based on changes in the propellant charge temperature T and the effective full charge EFO

are things. As a result, the partial multiplication factor becomes (T- k- ^ 2-). _{Furthermore, since} the approach angle is a function of the initial speed Vq and the flight time is inversely proportional to the initial speed V ", the multiplication factor for the approach angle becomes (1 - 2 LK- ^. F (EFO) \ ~]) and for

the flight time (1 - [Ap - f (E $ G) kl).

In the more general case, the serial partial technique; for multiplier functions F (u, v, w) by a single function generator to generate the function F (uq, Vq, Wq) for predetermined conditions and by multiplying this function by the partial series multiplication factors (1 + k- ~) , (1 + ! & -) ' and (1 + k——) realized. Furthermore, the computer compensates for a ballistic drift by multiplying

009809/1507,

the attachment angle signal and crosswind effects Multiply the time-of-flight signal by a own ballistic constant for each selected ammunition *

Further details and embodiments of the invention can be found in the following description, in which the invention is based on that shown in the drawing Embodiment is described and explained in more detail. The features that can be taken from the description and the drawing can be used in other embodiments the invention can be used individually or collectively in any combination. Show it

Fig. IA and IB block diagrams of a ballistics computer according to the invention and a Resolver interconnection,

2 shows the circuit diagram of an adjustable ballistic term multiplier, as it is used in the computer according to FIGS. 1A and 1B,

3 shows the block diagram of a main-sub-multiplier, as he in the calculator after the; Figs. 1A and 1B are used »

Fig. 4 is a timing diagram of the signals that were in the main en multipliers according to Fig. 3 are generated,

Fig. 5 & B.0 schematic circuit diagram of a function generator as it is used in the arithmetic circuit according to Fig. 1A »

0 098D9 / tSOT '

ΤΙ374Ϊ1 - 9 -

Fig. 6 the, diagram of a signal * that of .- - ,, . F / utiktiön ^^^^ n & ch Fig · 5 erjz «ugt _; will ^

7 shows the circuit diagram of a follow-up and clamping circuit, as they are in the computing circuit according to FIG. 1B Use; finds, and · ':,

Fig * 8. the circuit diagram of an analog switch ^; again

in the arithmetic line according to Fig. «. 1B use . finds · ^ - .- -, ·; V. - .-. '..

Bei.dem in FIGS. 1B and 1Λ dargeatellt & n.Ausführungsbeispiel that a ballistic '.. 95P contact distance information R, and information about deviations from standard conditions in a Rechner.eingegeben which sat on a _s ^ ,, zwinltel signal a signal flight time t ^, a ballistic drift signal t \ q and an en »crosswind coefficient y \ are generated according to ballistic equations, which are then used to generate fire control signals such as elevation E. and deflection D.

In addition to the distance, the ballistic properties of the projectile and the environmental conditions must also be taken into account; . "Be known in order to be able to produce in accordance with the ballistic equations fire control example is erforderlieh, the effects of the projectile mass, _{.Anfangsgeschwindigkeit;} of: ;; Fo.rm ^ of size,". Swirl, air density, air temperature, air pressure, cross wind, propellant charge temperature, angular velocity, swivel movement etc. to know *. · _IVt , _ _t . ■ -; _ .. ■■■■ _.-- *,% ^ i ^ ■■ -: ',,. ■ ■: ..- ■■■

■ - ■■ "■ '" ■ ''. .A

00 9009 / tSM / öfeaw

Since some of the ballistic properties are part of different gear sizes or different munitions. change, the recruiting ■■■■ S ± g --- ■ --nale like the Auf sat ζ angle Z , the flight time t ^. _{t is} the ballistic drift \ q and the crosswind coefficient

K _Wm also change for each storey, cw

It was found that the non-linear, equations for the ballistic flight from which the sat ζ wave 1 £ _ ^ and the flight time t ^ Q for standard conditions for a variety of projectiles from one

first adjustable multiplier.95 ^, which combines the range signal R with an individual ballistic term 1 / R. multiplied for each individual floor, function generating circuits 956 and 958 for generating the functions f ' _t (R / R) and f. (E / Rj relating to a plurality of floors, and variable multipliers 960 and 962 for multiplying the Functions can be generated with second ballistic terms iq and t Q associated with each particular projectile. It can be stated that the ballistic terms R-nt \ q " ⁰ ^ * _n o ^a ^ ^s W constants for a set of Standard conditions can be viewed.

For example, the equation for the angle of attack ^ ₀ under standard conditions, which is the angle at which a vehicle, such as a gun, must be raised over the line of sight to the target,

2RE / m 009809/1507

The equation for the plug time t ~ q of the projectile is under standard conditions

4- m [RK / m "\

In these equations is

Kp a drag coefficient R = distance K = Pd ² K ₁ ,

ρ β air density d => Bullet diameter

m = bullet mass

Vq «> initial speed of the projectile g = acceleration due to gravity β

The ballistic drift TIq under standard conditions is according to the equation

proportional to the attachment angle £ -q. In this equation is K, a term derived from the moment of inertia and the The speed of rotation of the projectile, as well as the coefficients of lift and momentum, depends on the size can be determined for each ammunition. The crosswind coefficient K under standard conditions. is by the equation

determined, in the K_ one of the Mun'itiqü |. ^ jbLängiger Coefficient is. O*.·

QO98O9 / 1507

As stated earlier, signals that are a function of ballistic equations can be extracted from circuitry are generated which the range information R in accordance with ballistic Process separation and normalized functions

For example, the angle of incidence £ _{0 is} generated by a circuit arrangement which processes the distance signal E according to the following equation:

2 (E / EJ

2 (E / E _n ) Y

? ¹ -j

in the

K pd

iTa

^5/2

d ²

A. ³ ^ ⁰ HUf; The signal relating to the time of flight tj 'is generated by a circuit arrangement which processes the range signal E according to the following equation

0 0980 9/1507

1S37412

in the

From these equations ereichtlichV -is that "free of realization of the circuit arrangements E, ± and t terrae sindj to a particular bombarded or bestiminten; be fixed set of standard conditions ^treated; associated Munitiprt and certain conditions' unds ^a l ^g constants Eden for ^ can, whereas f (R / iO and f. (H / R ") are functions that can be applied to all floors regardless of floor and conditions, or in other words. The advantage of this is that only one function generator for one Multiple floors need to be set up and that signals for deviations from standard conditions can be fed to the computer outside of the function generator, as will now be explained.

As can be seen from the block diagram according to FIG. IA Mher, the distance signal ^ R - first '- is normalized by multiplying with a standard condition term 1 / S _n Q. BallistilÜ? Onstänten ^ 9.5 ^ »^ Λ ^β i ^m -

following ^: ä \ rcn as "BaiiistikWeripultiplikatör ^. ^ ^ b§-,. _: • .'- sign will'and can be set for each * ammunition.

ÖADOftMSIWAk

As will be explained in more detail later. the normalization term 1 / R_ corrected for iiiiderimgen ^ EL, which result from changes in the air pressure / UP and changes - "" in the air temperature ^ Ϊ by multiplying the "! derm" with a partial multiplication factor (Λ - B), by doing

.is. As a result, the equations for "the values of the approach angle tw and the flight time t» /. * ^; - ·

ei f β)

'fl

As indicated above, the iormalization term 1 / ^ of a puncture is inversely proportional to the air temperature T and proportional to the air pressure P, so that the factor AR can be generated by the part of the circuit arrangement according to FIG. 1A which contains the summing amplifier 940.

009aG9 / 150

V /.

The summing amplifier 94-0 receives a signal At / Tq for the measured air temperature at one input and multiplies it by a temperature constant K. Her summing amplifier 94-0 also receives a signal AP / Pq for the measured air pressure at a second input. These signals are summed and it is then the output signal B of the amplifier 94Φ

vif - _K | s ν:: ::

n ° ¹ O,

As later with reference to FIGS. 1A and 1B; in detail will be explained, the partially corrected Angle of elevation and time of flight signals fc ^ and t ^ completely on the deviations from standard conditions corrected by continuing with the partial multiplication factors (1 + B) and (-1 - KH) are multiplied, one of which is due to changes in the normalization term Ί / Κ- due to variations in air temperature & .T and the air pressure ΔΡ and the other of changes in the initial speed AVq as a result of of changes in a function from the effective one full charge EFO and variations in the propellant charge temperature ΔίΓ_

The partially corrected superelevation signal fc ^ \ j is accordingly further corrected for deviations from standard conditions and is then given by the following equation * \. : ■:.

009 8 09 / IBQ 7

- ■ '.16 -

£ - 1 _Λ (1 + Β) (1 - 2H)

- 2nd

with B "

and H ■ ■■ ■ rr ~~ ·
^V O

The partially corrected time-of-flight signal t for deviations from standard conditions further corri greed and will

t _f - t _f1 (1 + B) (1 - H)

The factor H can be generated by the circuit according to FIG. 1A, in which a signal AT_ / 5D_ for the measured propellant temperature received from an adjustable ballistic term multiplier 942, with a separate ballistic term K multiplied for each selected ammunition and then an input one Summing amplifier 94-8 is fed * A signal EFC for the effective full charge is received by an adjustable ballistic term multiplier 944, with / a separate, ballistic term JL for each selected

009809/1507

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Ammunition multiplied and you generator 946 directed. With the function generator 946 can be a generator that supports the Function by two or more rectilinear = sections approximated and described in more detail below will be. This function generator generates

an output signal f (K EFC), which a different Eih_

output of the summing amplifier 948 is supplied. That resulting output signal of the summing amplifier 948 is the factor H according to equation. *. · ..

AV

- f (K _e EFC) - K f

A signal B, which represents a coefficient for temperature and pressure deviations from the normal state and is to be applied to the distance signal R / R ~ normalized to standard conditions, is generated by a main multiplier 964 as a function of input signals ^ a? / TQ \ uli & ÖB ^ EQ , ¹ öie von Luft- '' * ■ temperature-: and; _; running pressure sensors are supplied. The normal distance signal, based on standard conditions, is directed to the pressure-temperature coefficient ^; B multiplizie: 3? It ^ ϊ & ο that. an output signal ^ / R _n Q "generated;'will,.;daa; a ^ x ^ nyiertierend-eKiEingaiig of an ■ operation amplifier ^ 68: j3tü ^ e leads · isti DaS ^ gMI'll / R _n0 wirä ^Y '"also ddj3ekfe» -a% aeji nichtii ^^ rJiö ^ e ^ föen ^ Efegäng'des '' operational amplifier 968 is fed to an output signal \ _; .

0 0 9 8 0 9/1 5 0 1 -H S v *. '' ^ ^: £ ? -

to produce, In.the above equation is

^the '-formal ^^ ized distance signal, · _; - _; for standard conditions, _r ·. -; ■ '"- · _ ■■ _ ■ _. · ..'. ■

^ _That: norffial ± catalyzed Entrernüngssignal ^r - · - ■ ^"; - lor-Abwedchmigeü of ^ 'to: ^·;' Standardbedingurigen. Xtiia ^ · ...-:

B ο (AP / P _Q , - KM /% Q) y nut ''_; /

Deviations from the Ιιΐί £% άΓΛΐοΚ « ^; from the

Standard lift printing
Temperature coefficient,; ν ■ -;., -. ;;. r--

Dev

Standard air piperainir ^f . ;; ν

Standard ventilation temperature. . "

The normalized distance signal ·! ^ (^ B ^ is then supplied to ν-EunktiorLSge.nerator ^ g ^ g and 958, which are arranged parallel to one another and ballistic function signals ^ fc ^ - ^ n ^ "^ ^z ^ ·,? t ^ ^{! R} / ^R n ^ ^{&Ι> 2} · ^Θ υ ^ βη ·. |) i ^ © Eu ^ nction signals are then supplied to ballistic constants , multipliers 96D b ^ w. 962, which in the following: - also · as Ballistic term multipliers denote? Rerdeii: Uiid this function ^? ·; Signals, with-ballistic term ^

conditioneil, mulfcipld ^ ieren ^ JIpf-olgedessen, relates; itself ;: the output signal f _nQ f ^ (RZR _n ) of the ballistic constant multiplier 960 on the attachment angle '. £ ,. for the

009809 / f5tf7

'which is special bullet "at the specific distance R according to the mentioned above ballistic equation partially corrected for non-standard temperature and pressure conditions Also, the off transition signal T n ^ * -. äes ballistikkonstanten multiplier 962 (^ / ^ _n.) related to the flight time t _{f /} . of the selected projectile at the specific distance R according to the above equation (7) for the flight time t ^, which is partially corrected for temperature and pressure conditions deviating from the standard ...

As can be seen from FIG. 1A, a main multiplier 970 receives input signals K AT ₀ ZiT ₀ . and f (EFC) »K _o

g g g - - e -

of sensors for the propellant charge temperature and the effective full charge in order to generate an ignition speed coefficient H, which is used together with the temperature-pressure coefficient B to generate the partially corrected contact angle and flight time signals 2. λ and t « ^ to correct with the aid of the circuit arrangement illustrated in FIG. 1B. The partially corrected attachment angle signal {. is passed through a first secondary multiplier 972 in which it is multiplied by the temperature-pressure coefficient B to produce an output signal t * B which is fed to an input of an operational amplifier 974-. The partially corrected top angle signal Z * is also fed "directly to" another input of the operational amplifier 974, so that its output signal assumes the value £ ^ (1 + B)

σθ98Ο9 / Ί507

by multiplying it by the muzzle velocity coefficient H do produce a signal% * (1 + B) H which is fed to an input of an operational amplifier 978 to be inverted and multiplied by the factor 2 · the signal . fc. * (i + B) is also fed directly to another input of the operational amplifier 978, so that this operational amplifier generates a top angle signal fc which is corrected for conditions deviating from the standard and has the following form:

% = I ₁ (1 + B) (1 - 2H)

^Δν ο

H = π— -

= f (EFO) _A + γ

In these equations is. _ »"

f (E.F.O.) a function of the effective full iC ~ Charge for a selected ammunition

"ΆΤ_ the deviation of the propellant charge temperature

from a default value _

Ί? Q? Friction charge temperature under standard conditions

K. Temperature coefficient for an excellent

gA.

■ chose ammunition.

009809/1507

If37412:

& i, äei 'corrected ^ flight & eifaigiial t £ ^ is directed by a-triegen ftebe ^ ültipiikätör 980i by using it with; ■ a & m Ee ^ eratur-Druck ^ &' ^: mutäpli.isi <B £ t' ■

We df '' aö that ■ an output signal t ^ B eiii: ts # eht - _{s is the} one input of an ■ ÖperÄtionsverGitürker 98S. The partially corrected "SloigsieiiisiGnal also üniiiitii'elTDar another input of the

t ^ (t + B) '

The corrected FluggBitsigiial iv is passed through a second secondary multiplier 98 ^, in which it is multiplied by the muzzle velocity coefficient, so that a signal t ^^ (1 + B) H is generated: is fed to an inverting input of an operational amplifier 986 · is further corrected: Klugsseitsignal t ,, ^ (1 + B) and another input of the operational amplifier 986 is supplied unmi-ttelfeor £ iüirt _f t, a corrected for deviations from Standardbedingtffigen flight time * signal. generated, the ^{1 to} the expression

same: 1st ^ The ^ plug time signal 't ^ is, eiitem ^ Eaupt murtiplikatoii * 988 for the use of öX & flight time multiplication signal v Φ added ^. ^ ie: ea ^; ? later melü? described in the NEN ^

The computer 950 also generates a Paretllaxen signal ρ to compensate for the distance betweenEt Sicto ^ nie'uhd ^ d ^ distance signal R becomes a lunictionsgeneraiior 9 @ Ö and fed to a rectifier 992 * How later meha? will be explained in detail, will ^ dsff

VA

37412

signal äeä rectifier eiiiiiö-Miökpixiiktwähler zt ^ ßefelte; _ί del? the Änstiegväistärltung and the ^r · ·. Setting of the function generator 99Ö determined so that a Färallä ^ em ^ örrekMoüssigiial ρ for the distance R generates the following (KLeiehüng obeys:

In this # n öleiöhuhgeir is

ß the distance between dei? Power lineuM ^ the pipe axis,

R, the measured distance and> ,; - .v

'R- dia cutting distance, -in döi? the line of sight ' ¹ intersects the pipe axis »....;>

For päral-lax corrections in the elevation gil%

Here is

a constant for '^ ede ^ for example the fig one

009809 / 1ViW

For parallax correction in azimuth (deflection) is applicable

.-- ^D pd ^{(1 / R} V..

Again, D, a constant for any gun arrangement, is for example that of a tank.

The ballistics calculator will now be described in more detail below. The range signal R is applied to the ballistic term multiplier 954, shown in detail in FIG. 2, for generating the normalized range signal R / R q for a selected one of a plurality of projectile types. The ballistic term multiplier 954 is an operational amplifier which has a number of η parallel input resistor branches which are used for gain adjustment and each of which contains one of the area field effect transistors 996 to 996n, which is connected in series with one of the plurality of resistors 998a to 99 ^ ¹¹ is switched. The resistor branches are connected to an input of an amplifier 1000. The index η denotes the circuit elements in the nth resistance branch and is equal to a corresponding number of the floors »In operation, only one of the surface field effect transistors 996 to 996n is switched on by a positive voltage + V, which is fed to the gate electrode via one of the resistors 1002 to 1002n is, while all other of the transistors 956 to 956n by a

- ■ ^{; ; ;} ■■ - Y YY ■■■ "" ■■■ - -: a

00980971507

negative voltage -V are locked to their gate electrodes is supplied via the corresponding resistors 1002 to 1002n

It is now assumed that the selected projectile or the selected I.Iunition has a ballistic terra 1 / R _n Q, which is expressed in the ballistic multiplier 954 by the sum of the series resistances in the circuit.

branch between the cathode and the anode of the activated area effect transistor 996 and des Y / iderstandes 998 between transistor 996 and the Input of the operational amplifier 1000 is entered. An ammunition selector switch 1004 is in operation to 10Ö4n set so that a voltage + V above. the resistor 1002 of the gate electrode of the field effect transistor 996 is fed to turn this transistor on, while all other transistors like the transistor 996n receives a voltage -V via the switch on its saddle electrodes and is therefore blocked are. The operational amplifier 1000 can it is a high performance surgical amplifier

w of the type Fairchild / aA7O9, which is manufactured by Fairchild Semiconductor Corporation and in their manual "Fairchild Semiconductor Linear Integrated Circuits Applications Handbook ¹¹ , 196?" is described and illustrated.

The operational amplifier 1000 is for a gain factor of 1 compensated and it is its output through a feedback resistor 1006 to one of its Inputs connected »so that the gain of the ballistic term multiplier 954 the ratio of the value of the

6ADORlGtNAi.

Feedback resistance a 1006 is proportional to the sum of the resistances between the cathode and the anode of the switched-on field effect transistor 996 and the resistor 998 and can be expressed _{by the term 1 / R n Q.} The received range signal R is multiplied by the 3allistic term 1 / R q so that the output of the ballistic term multiplier 954- is a normalized range signal R / R q under standard conditions for the selected ammunition. Any gain resulting from the resistance circuits containing the switched-off field effect transistors can be disregarded, since the resistance between the cathode and the anode is very high in relation to the other circuit resistances. The offset of the operational amplifier 1000 can be set with the aid of the gown tap of a potentiometer 1008, at which the tapped voltage is essentially 0 V and from which it is fed to an input of the operational amplifier 1000 via a resistor network. The ballistic term 1 / R ^ has a different value for other projectiles, because the values of the resistances 998 to 998n are selected so that they correspond to the different ballistic terms for different projectiles. Accordingly, the selected normalized distance signal R / R _n0 is specifically associated with the selected bombarded · The output signal R / R ^ q then wirjd ballistic function generators 956 and fed to the 958th r -. V

Before that normalized

Function generation pyeii. sugesfulir-fc ^ yä _f ^ iy ^ ^ a for yont

BAO0BJGINAL

Standard deviating temperature and air pressure conditions in a main IT even multiplier or 964, 966 corrected with time division. With the multiplier with timing it can be one act electronic multiplier, the output signal of which is the mean value of a pulse train in which da3 duty cycle is equal to the ratio of two variables and the amplitude of another Variables is controlled. Such a main life .multiplier " with time division is shown in FIG. 3 and consists of the main multiplier 964 and love multiplier 966. Although in Fig. 3 only an I-life multiplier 966 is shown, a Main multiplier can be used to operate a larger number of IT secondary multipliers, such as shown in Fig. 1A.

The main multiplier shown in Fig. 3 receives DC input signals e, = R / B_ and e = ΔΡ / Pq KAT / Tq and generates two output square-wave signals B and B, the same amplitude and phase, but opposite polarity. The main multiplier 964 includes a first main inverter 1010 which receives the DC input signal e 1 and performs an inverse operation on that signal. It delivers the signal —e “, that is, the inverted signal to the input signal. A second main inverter 1012 receives the inverted DC input signal -e ,, performs an inversion operation on this signal and delivers an output signal e. Accordingly, the first and second main inverters 1010 and * 1012 deliver output signals e _d and, respectively . A first main switch 1014 and a second main switch 1016 of opposite polarity.

aaaaoa / tio? ./·

The first main inverter 1010 also effects an amplitude adjustment of the signal -e ,, which is fed to the first main switch 1014, and an adjustment of the amplitude of the signal e ,, which is fed to the second main switch 1016 via the second main inverter 1012. If a system gain of unity is desired, the first main inverter 1010 can be set to ground to provide signals to switches 1014 and 1016 which have a gain of unity in relation to the amplitude of the DC input signal e. The second main inverter 1012 always works with a ¹ unity gain factor. With a system gain of one, the input signal e must be greater than the direct current input signal & P / Pq - ΚΔτ / Ί *, if the circuit arrangement is to work properly.

The first main switch 1014 and the second main switch 1016 continue to receive gate signals B and B in opposite directions Polarity from output terminals 1018 and 1OgO of a switch 1022, which signals rahlweise the first main switch 1014 and the second main switch 1016 are fed to these switches to enable successive work.

A summing integrator 1024 is connected to the outputs of the first and second main switches 1014 and 1016, which also receives the signal 4P / Pq -KAT / Tq in order to sum or integrate the currents generated by the signals ΔP / Pq - KA T / Tq as well as -e _d and e _{d are} generated »A threshold detector 1026 receives the

009809/1507

Output signal of the summing integrator 1024 and speaks depending on the trigger signal of a trigger switch 1028 to any change in the threshold value from the Suinmier integrator 1024 to the switch driver 1022 to cause the polarity of its gate signals of opposite polarity to terminals 1018 and 1020 to switch. The output signal of the trigger circuit 1028 is fed to the threshold detector 1026 to cause the threshold detector at Receiving the trigger signals from the trigger circuit 1028 to change the state of its output signals and thereby the period of the gate signal for the main multiplier equal to the period of the trigger circuit 1028 to receive α The gate signals B and B at the output ski emmen 1018 and 1020 have a duty cycle, i.e. a ratio of the switch-on time to the period duration and are alternating between

AP JiT

"switched back and forth *

The minor multiplier 996 contains a first-minor -... inverter 1OJO, a second lifting inverter 1032, a first lift holder 10J4 and a second lift switch 1036. These circuit parts work in the same way Vieise like it did above for main inverters 1010 and 1012 and the main switches 1014 and 1016 of the main multiplier 964 * The input signal of the

00 9809 / 1.5 07

ORlQlNAL

However, the first secondary inverter 1030 is an alternating current signal (E / B. ^) slnQ ^ Js) _r whose period is large compared to the period of the output signal of the main * -: multiplier. The first secondary switch 1034 and the second secondary switch 1036 are connected to the Klerir.en 1018 and 1020 of the Ilauptmultiplikatörs 964 via Torkleninen 1038 and 1040 of the secondary multiplier 966, so that the first secondary switch 1034 "and the second secondary switch 1036 are alternately caused according to the Threshold values detected by the threshold value detector 1026 to change their state. The output signals of the first and second NeTD switches 1034 and 1036 are fed together to a filter 1042 to produce a filtered product output signal which can be represented by the following relationship ;. ■

(R / R _n sinfot)) / ^ -

The main part 964 divides the quantity 4P / P ₀ - KÄT / O? ₀ by * the quantity e _d in order to generate a quotient (ΔΡ / Pq - KAT / T ₀ ) / e _d , while the life part 966 multiplies this quotient by the quantity R / & _n sin (iöt) »by that given above Form product.

. The operation of the master-slave-multiplier with time division of Figure 3 vvird Referring now to the diagram of FIG explained in more detail 4 * In dieseiä Dia · -. Gramm illustrate the Kürveii A and B, the EOR Äüsgangsspanhtingen to the Auagftngskiemmein 1Ö18 and 102Ö

1937A12

■ - 30 -

of the switch driver 1022, curves G and D the output currents of the first and second main switches 1014 and 1016, respectively, curve E the output voltage of the Suminier integrator 1024 and curve F the output voltage of the threshold value detector 1026. All curves of FIG special times tQ, t ^, tp »t% and t ^, and it is the time span t,. = t ^. - t _Q tmd the time period T ₂ » H ^ . ■ * - ■ t ^.

At time t «, the gate signal B at the terminal 1018 becomes negative and brings the first main switch 1014 into the" off "or non-conductive state. Correspondingly, the gate signal B at the terminal 1020 becomes positive and brings the second switch 1016 into the "on" or conductive state, as is shown by curves A and B * during the time period T _x . the first switch 1014 remains "off" and the second switch 1016 remains "on". During the time period T, the summing integrator 1024 is charged by the current e ^, which is supplied by the second main switch 1016 (curve D) and by the current ΔΡ / Pq - K (ÄT / Tq. Ψ. Integrator a falling voltage, which is reproduced by curve E. During the first time period T 1, the first main switch 1014 does not supply the summing integrator 1024 with any charging current -e falling voltage reaches the negative (-) threshold value of the threshold value detector 1026 at time t ^, the output signal of the threshold value detector 1026 changes from a negative value to a positive value.

word detector 1026 changes from negative value to changes positive value, the switch driver 1022 changes the polarity of its gate signals B and B on the clenua 1010 and 1020.

As a result, gate signal B at terminal 1018 becomes positive at time b- and the first switch 1014 changes from "off" - or non-conductive state to "on" or conductive state negative and causes the second main switch 1016 to change from the "on" or conductive state to the "off" or non-conductive state. During the time period T ~ "the first main switch 1014" remains on "and the second main switch 1016" is off. Furthermore, during the time period T ~ ^ the summing integrator 1024 is switched on by the current supplied by the first main switch 1014 (FIG. 3) and charged by the current FlP / P ₀ - KÄT / T _Q from the negative (-) in the direction of the positive (+) threshold value and generates a positively increasing voltage, which is represented by the curve E. There is no charging current during the period T ~ e, from the second switch 1016. When the positive rising voltage reaches the positive ". (+ ■) threshold at the threshold detector 1026 at time tp, the output of the threshold detector 1026 changes from a positive to a negative value. When the output of threshold detector 1026 changes from a positive value to a negative value, switch driver 1022 changes the polarity of its gate signals at terminals 1018 and 1020. From time tp on, it repeats

'. . ■ ■ "■ · -. ■■"'"■■■ - ■; ^V: ■' ■ ';''' ./ ^.; ■ ·""■ 009809/1507., _If «, -, -. -, .-.

BAD ORlGWAL

the operation of the circuit according to Piß. 3, because the time interval t, - to is identical to T., and the time interval t ^, - t * is identical to T ₀ .

Another analysis of the curves of the diagram according to Pig. 4 shows that the main multiplier 964 or the time-dividing section of the time-dividing multiplier according to Pig * 3 supplies the pivot information e _m / e- in the form of a duty cycle. The duty cycle is the ratio of the total "on" time T ₂ - Tx ₁ to the total time T ^ + Tg * Recall that the summing integrator 1024 during

this "total cycle time" T, + Tg three charging currents

are fed. The current 21P / Pq - ΚΔΤ / Τ «v / ird during the total time T, - + Tg, whereas the current e, from switch 1016 only during time T ,, (curve B) and the stream -e. from switch 1014 only during Time Tg (curve C) is supplied. The mean of the Charging currents that are fed to the summing integrator are therefore given by the following equation

(T "> +. S_ ί.. Ο

^H 1

In this equation, R ", R and R _{x are} different,

2 ?. circuit resistors, not shown, which are used to control the system gain. For example, the summing integrator 1024 can contain an operational amplifier (not shown in more detail) in which R ^, Rg and R, the input resistances, τ »οη which for ¹ each to one of the input signals Δ P / pQ - ΚΔΤ / Tq, θ, and - e.

■ - "- ■■ -." -. ■ ■ -...- -. "-. · * / · Q09809 / 1507 ^

responds and which are connected to a common summation point. If body 964 and its components are designed for unity system gain, then R _-1 ■ = R «R- * and it becomes the equation

T ₁ ) + e _d (T ₁ ) + <-e _d ) (T ₂ ) = O.

If all the terms of the above equation are divided by ^e d ^ 2 ⁺ ^ ₁ ), similar terms combined and others rearranged, the result is the expression.

¹ 2

It y / urde. accordingly stinging that the quotient (4p / Pq e _{d is} obtained by a pulse width modulation and in a duty cycle of the form

is present.

The multiplication by the multiplier with time division takes place with the help of "the secondary multiplier 966, by optionally adding the derived duty cycle and its Negation via terminals IO38 and 1040 to the first and the second life switch 1034 or 1036; fed while the signal —R / Rq sin (tob) is sent to the switch 1034 and the signal R / R ^ sinfat) the switch is supplied

1337412

Since the switch 1036 is in the "on" or conductive state during the time Tp of the total time T, - + Tg and in the "off" or non-conductive state during the time T _x ., As curve A in FIG. 4 shows , the current R / Rq sin («Jt) flows through the switch 1036 to the filter 1042 only during the time Tg *. Furthermore, since the switch 1034 is only in the "on" or conductive state during the time T. of the total time T ^ + T and in the ^{"off" or non-conductive state during the time Tg ^ - m} , as shown by curve B in FIG. 4 shows, the current -E / E q sin (^ t) flows only during the time T ,. to the filter 1042. If the llebenmultiplikator is operated 966 with a gain of one by the switch 1034 and the output signal of the filter is represented by R / R _n o sin (yt) B 1042, then the flow of the currents R / R _n0 can sinfat ) and -R / R _nQ sin (wt) can be represented by the following equation:

T ₂ T ₁

e _n <= (R / R. ,,, sin (wt) + -R / R_ _n sin («t) o no Tp + T ^ no. / x« +

By factoring out the factor R / R Q sin («Jt) from the Outlining the right hand side of the equation and combining the terms becomes the equation

(T - T)

R / R _n0 sinCwt) B = R / R _n0 sin (Wt)

By replacing (Tg - T ^;) / (Tp + ^ η} '- ^du FCh the corresponding expression / ^ P / B ^ - ΚΔΤ / Tq, the equation finally becomes *

sin (^ t) B f ■ - ■ (R / R.

^e d -

⁰ d

000809/1507

It should be noted that in the above equations the value of the factor R / R Qsinu / t) is contained during the duration of a "certain clock period. Since, as mentioned above, this clock period is much shorter than the period of R / R _Q sin (vt) _s , the change in the magnitude of R / R _Q sin (wt) .during one clock period is relatively small. The output signal R / R _n Q sin (Wt) B is the partially corrected normalized range signal R / R which is fed to function generators 956 and 956.

5 illustrates a function generator 956? äer an output function f ^ (R / R) is generated by means of a number of curve segments. The function generator comprises a break point selector and a switched resistor network 104-6 having a number of resistor branches which are selectively summed in response to output signals provided by the breakpoint selector 1044. The selective summed resistors are connected to the input of an operational amplifier 1048 to increase its gain approximately in accordance with the desired function, such as that shown in FIG. 6, for example Function f ^ R / R).

The function generator according to FIG. 5 can either with a DC voltage or an AC voltage can be used as the analog input voltage, for example the normalized distance signal R / R. at an analog AC input voltage is a Four-way switch IO5O in the alternating current position,

009809/15 07;: - ■; '

- sad original

-26 -

so that both the supplied at the input terminal 1052 Distance input signal as well as the reference AC voltage supplied to terminal 1054 with the help of precision rectifiers 1056 and 1058 in output DC voltages can be implemented that corresponds to the rms value of the corresponding V / alternating voltages are proportional. The precision rectifier 1056 generates a positive DC output voltage that proportional to the normalized distance signal R / E whereas the precision rectifier 1058 produces a negative DC output voltage, 'that of the AC reference voltage is proportional. The normalized distance signal E / R and the reference AC voltage are fed directly to the switched resistor network 104-6 because they can can be used without having previously been converted into DC voltages.

With an analog input DC voltage and a constant DC reference voltage, the switch 1050 is in the DC position, as illustrated in FIG. 5. In the above-mentioned alternating flow position, the four-way switch 1050 _{v is switched} from the position illustrated in FIG. 5. When the switch IO50 is in the DC position, the normalized DC distance signal E / E _{n is} fed directly from the input terminal 1060 to the "kink point roller 1044" and the switched resistor network 1046 Resistor network 104-6 and also via a

- ■;.; ■ ": ■ />;;'■' ■■■ ■■ · / · ^: ■■:" ■ '■

00980971507

Inverter 1064 fed to the break point selector 1044, because a negative (-) DC reference voltage is required for the correct operation of the breakpoint selector 1044 will..

The circuit arrangement according to Pig · 5 is described below for the use of the normalized DC voltage distance signals 3 R / H _n and a reference voltage. From the preceding and the following explanations it becomes clear how the function generator would work in the presence of a normalized AC input signal H / R and a constant reference AC voltage.

The break point selector _v 1044 contains a number of operational amplifiers 1066, 1068 and 10? 0. Each operational amplifier has an inverting input (2), a non-inverting input (3) and an output (6). Resistor 1072 connects the non-inverting input to Hasse to minimize the bias current error inherent in operational amplifiers. Comparison circuits, each consisting of resistors 1074 and IO76, 1078 and 1080 as well as 1082 and 1084, are connected in parallel between the input terminals 1060 and the output of the inverter 1064 via the switch 1050 and are used to receive and compare the normalized distance signal H / iL and the constant DC reference voltage. The junctions of the resistors of each comparison circuit are

009809/1507

each connected to one of the inverting inputs of the operational amplifiers 1066, 1068 and 1070. Each of the operational amplifiers 1066, 1068 and I070 produces a negative output signal when a positive voltage is applied to its inverting input. In the case of a distant target, the range, and consequently the amplitude of the normalized range signal R / R-, is greater than "in the case of a near target. The size of the resistors 1074, IO76, 1078, 1080, 1082 and 1084 is chosen so that with a continuous Increase in distance H first the operational amplifier 1066, then, with a further increase in distance R, next the operational amplifier IO68 and finally, when the distance ... R increases even further, the operational amplifier IO7O is switched on are achieved when the normalized distance signal R / R voltage V ^ _{5 reaches} a voltage Vjj and a voltage V- illustrated by points A, B and 0 in Fig. 6. When the voltage level V. from the normalized distance signal R / R _{n is} exceeded, the output voltage of the operational amplifier 1066 will be low or negative »The operational amplifier can be a Fair child / Λ / Α7Ο9 high performance operational amplifier manufactured by Fair child Semiconductor Corporation and described and illustrated in their "Fairchild Semiconductor Linear Integrated Circuits", Application Handbook, 1967 **. The output of the operational amplifier 1066 is passed through a resistor 1084 to the base

009809/1507

8AD ORIGINAL

- ■ 39 -

a PNP transistor 1086 is supplied to the transistor 1086 to turn and to cause _s that moved by the voltage drop at the Kollektonviderstand 1088die collector voltage from a negative value to a positive value, the taken off at the collector of transistor 1086 signal is hereinafter referred to as switching or ICnicl ^ uiüct-Wählsignal A designates and has a positive potential at this time

If, as a result of a further increase in the target distance R, the normalized distance _{signal R / R n} exceeds the voltage level VD, the output signal of the operational amplifier 1068 becomes low or negative. The output of operational amplifier 1068 is fed through a resistor 1090 to the base of a pnp transistor 3 1092 to turn on transistor 1092 and cause the voltage across collector resistor 1094 to change from a negative to a positive value The picked up signal is referred to below as the switching or breakpoint selection signal B and has a positive potential at this point in time.

Should the target distance increase further, the amplitude of the normalized range signal R / R also increases further. When the normalized distance signal R / R exceeds the voltage level V " illustrated by point G in Figure 6, the output of operational amplifier 1070 goes low or negative. The output signal of the operational amplifier 1070 is passed through a resistor 1096 of the

00980971 SO 7

Base of a / pnp-2? Transiator 1098 fed to this Switch on transistor, with transistor 1098 conducting, the voltage at collector resistor 1300 changes from a negative to a positive value. The signal tapped at the collector of transistor 1098 is hereinafter as switching or break point selection signal 0 and is positive at this point.

These switch or break point selection signals A, B and 0 P are fed to the resistor network 1046 in order to generate the Selectively change the gain factor of the operational amplifier 1048.

The resistor network 1046 includes a first set of parallel resistor branches 1102 which are supplied with the normalized distance signal R / R_ and which are responsive to the breakpoint selection signals A, B and 0 for setting the slope gain, i.e. the slope factor a. of the limb a. χ the function f _£ (RZR _n ), which is generated at the output of the operational amplifier 1048. The x factor of the element a-χ is k the analog input voltage R / R ″, which is fed to a resistor 1104 and the cathodes of field effect transistors 1106, 1108 and 1110 via the switch 1050. This analog input voltage R / R_ or the R / R factor has, in connection with the resistance offered to the inverting input of the operational amplifier 1048 by the first set of parallel resistance branches 1102, through the previously described mode of operation of the circuit arrangement the production

00980S / 1507
SAP

of the element a.χ of the function f £ (R / R), which is formed at the output of the operational amplifier 1048, to the result »The resistor network 1046 also contains a second set of parallel resistor branches 1112, which are jointly connected to the input terminal 1062 via the switch 1050 are to receive the reference voltage, and respond to the reference voltage and the IQiickpunkt-Wähl signalsei.A, B and C to adjust the intended slope gain so that the coordinates of the function f ^ (R / R _n ) in the points A, · = B and C according to FIG. 6, which represent the voltages V, V «and V ~. These coordinate intersections determine the ordinate intersections or stresses bp, b, and b ^. · The intersection stress b ,. occurs before the breakpoint select voltage V ^ because it is part of the equation ax + b. of the first curve segment. The creation of the limb b. the function ft (R / R), which the cutting stresses b., bpi ¹ OX and b ^. at the output of the operational amplifier 1048 is represented by the. Effect of the resistor is achieved, which is offered to the inverting input of the operational amplifier 1048 by the second set of parallel resistor branches in cooperation with the reference voltage.

When the amplitude of a distance analog input voltage is smaller than the breakpoint voltage V. only the rise resistance 1104 and a Intersection resistance 1114 with the input of the Operational amplifier 1048 verbundea, because there are

009809/150

- 42 - -. - .. '■■■ - ■■ / ■■. ■., .. ■; ■' ■

Koine positive break point signals A, B or C before that keep one of the area effect transistors could that both in deia first. sentence parallel resistor branches 1102 as well as in the second set of parallel V / iderstandssT / oige 1112 are included. As a result, the output signal becomes of the "operational amplifier 1048 by the equation fv (R / iO = a ^ x + b. of the first curve segment befc wrote.

The operational amplifier 1048 contains an amplifier 1116, for example an amplifier of the type mentioned above / * A709 »and has an Eücldcopplunss-" V / resistor 1118, which its Auagaiic (6) with its inverting "input (2) connects »In addition, the non-inverting input (J) is connected to a reference potential via a resistor 1120 in order to keep the bias voltage error, which is inherent in such operational amplifiers, to a minimum the resistance determining the amplification factor, so that the amplification of the operational amplifier corresponds to the ratio of the resistance value of the feedback resistance 1118 to the sum of the parallel resistance values of the increase resistance 1104, to which the input signal R / R is applied, and the SchnittpunkfeEriderstandes 1114, at which the _be; zugsspannung abuts ₉ is proportional "

Under these conditions the ^

956 a first » in ^ ig · 6 aary racks

until the increasing analog input voltage is indicated by the point Λ in Pig. 6, the voltage "V. exceeds. If the amplitude of the normalized distance signal R / E exceeds the first break point or switching voltage V., the positive content or break point selection signal A is generated by the break point selector 1044 and via resistors 1122 and 1124 the gate electrodes of the field effect transistors 1126 and 1128 of the first and the second set of parallel resistor branches 1102 and 1112, respectively, in order to switch these field effect transistors on activated field effect transistor 1126 and the resistor 1150 effectively reduces the rise resistance of the operational amplifier 1048, whereby the rise of the second curve segment between the voltages V ^ and VL _1, which are shown in Fig. 6 as points A and B, is increased - preamble tion the sum of the parallel resistance values of the resistor 1114 and the resistance branch, which comprises the resistance between the cathode and the anode of the switched-on field effect transistor 1128 and the resistor 1132, to the reference voltage in order to bias the gain of the operational amplifier 1048 so that a projection of the second Curve segment intersects the ordinate of the diagram according to FIG. 6 at a specific point bp, not shown.

009809/1507

1937U2

In the same way, the curve segment between the. Break point voltages V ^ and V-, _φ represented by points B and C in Fig. 6, generated when the cross point selection signal B changes from a negative potential to a positive potential and through a resistor 1134- the gate electrode of a field effect transistor 1136 and through a resistor 1138 - the gate electrode of a field effect transistor 1140

^ is fed. The positive switching or break point

Select signal B switches the field effect transistors 1.136 and 1140 on, so that their respective cathode-anodon resistors and the resistors 1142 and 1144 are connected in parallel to the resistor branches described above in order to further reduce the rise resistance of the operational amplifier 1048 and thereby the rise of the third curve segment between to increase the voltage levels ν * and V_, which are illustrated in FIG. 6 by the points B and 0. Furthermore, in cooperation with the reference voltage, the gain of the operational amplifier 1048 is further biased so that a projection of the third curve

The segment intersects the ordinate of the diagram according to FIG. 6 at a predetermined point b, not shown.

The fourth curve segment, which is the knee point voltage Vq which is illustrated by point 0 in FIG. 6 is generated when the switch or break point selection signal C changes from negative to positive, voltage and through resistors 1146 and 1148 den

00 9 809/15 0

Gate electrodes of field effect transistors 1150 and 1152 is supplied to turn on these field effect transistors. The resistance branches that make up the resistance between the cathode and the anode of the field effect transistor 1150 or 1152 and the resistances 1154 and 1156, respectively, become the previous ones described resistors connected in parallel to continue the gain gain of the operational amplifier 1048 and continue to bias the operational amplifier so that the fourth curve moment, when projected, the ordinate of the graph 6 in a further, not shown Point bj, intersects.

It should be emphasized that it is possible to improve the accuracy of the Increase curve approximation with the help of this function generator by adding for each additionally desired curve segment an additional comparison circuit, an additional operational amplifier and transistor circuit for the break point selector 1044 and an additional one Resistance branch in the first and in the second set of parallel resistance branches 1102 and 1112, each with a field effect transistor and a resistor can be provided. The creation of additional curve segments and additional Buckling parts would give the desired steady curve reproduces the required function, approximate better. The resulting output signal% (R / R) k at the Output terminal of operational amplifier 1048 is approximated by the function given by the equations above is described.

Ö09809 / 1507

The resulting output signal f ^ (R / R) at the output terminal of the operational amplifier 104-8 is received by the adjustable ballistic star multiplier 960 (Fig. 1Λ) by multiplying it by the ballistic tq Ballistic term multiplier 960 the same as the adjustable ballistic term multiplier 95 ^ - after. Fic _"S 2 except that the values of the resistors 998 to 998n ^ and the feedback resistor 1006 genaß the Ballistikkonstante ™ ir _n0 for each Ilunition gev / are äliit.

The output signal of the adjustable Taaliism constant multiplier 960 is proportional to the attachment angle £ * according to the equations for the attachment angle £ * described above.

The ballistic function generator 958 for generating the Ballistic function f ^ (R / R) and the one divisible

χ »η

Ballistiktermmültiplikators 962 to llultiplizieren the function with the Balliatiktermt "Q according to Pig x 1A or 5 · the adjustable Jk ^ bare Ballistiktermmultiplikator 95 are in the same V / else formed as the Ballisijikfunktionsgenerator 956 of FIG. Apart to Fig 2y · the fact that the Values of the resistances contained therein are chosen so that the resulting ballistic function and the multiplication term approximate the continuous curve and the expression that is represented by the time-of-flight equations; is used to generate the partially corrected flight time signal t ^ *

As described above with reference to FIG. 1B, the partially corrected attachment angles! Signal £.,. and the partially corrected time of flight signal t _{f /} . each headed by a pair Hebenmultiplilcatoren in order to forward with respect to deviations from standard conditions gei.iäß the partial derivatives of W and H iia to korrigicren _e Mohr individual is the partially corrected Gas cap zwinkelsignal \ t by the lifting multiplier 972 * the operational amplifier 974 · "the secondary multiplier 976 and the operational amplifier 978 passed to the Aufsatζwinkel- output signal £ for conditions deviating from the standard

t -E ₁ (I ₊ B) (1 - 2H) where B »ÜH _n / R _n and H

The partially corrected time-of-flight _{signal "t f /} . Is passed through the secondary multiplier 980, the operational amplifier 982, the secondary multiplier 984 and the operational amplifier 986 to generate the time-of-flight signal. T" for deviations from standard conditions

t _f = t _f1 (1 + B) (1 - H) to create _s in which in turn B = ΔΕ / R_ and H = AVq / Vq.

The four lift multipliers 972, 976, 980 and 984 ■ are all realized in the same way as that Minor multiplier 966 of Figure 5. The major multiplier 970 »the one for controlling the secondary multipliers 976 and -984 is designed in the same way like the main multiplier 964 * according to Fig. 3 ·

■. '.;'' - "■ - ' : ■■ .' ■ ■ ./. ■: ■ .- ■ =. 009809/1507

The parallax correction signal ρ is used by the radio tion generator 990 »the rectifier 992 and the Breakpoint selector 994- generated that in the same Are designed like the circuit arrangement according to Fig. 5 * However, since the parallax ρ «1 / R - 1 / R"

has an inverse dependence on distance, The function dor parallax ρ as a function of the distance is generated by the puncture generator the number of parallel resistor branches is reduced, when the distance increases, which is exactly the opposite of the working method described with reference to Pig 5

Like from Pig. 1B, the elevation control signal E and the deflection control signal D for controlling the fire control system in height or in the deflection based on the attachment angle _{signal E and the time-of-flight signal t f are} generated by these signals for the ballistic drift angle 7 ^, the wind deflection angle ^, the tower angular speed ' Hj., Parallax p, jumping movements D., E. and oblique position D ,, E, can be corrected ·

The attachment angle signal £ is passed through a Ballistiktermmultiplikator 1160 in Fig 2dargestellten. Kind by being multiplied by a selected Ballistikdriitkonstante E ^ for each selected ammunition * This Ballistiktermmultiplikator 1160 may include a delay-free multiplier of the above type contain a drift angle signal 7 ^ _d according to the equation described above. This drift angle signal τ ^. is then fed to a summing input of an operational amplifier 1162,

G09809 / 1507

whereupon this circuit of this ballistic drift angle ν signal used to control the elevation signal E ■ and to correct the deflection control signal D, such as, it will be explained in more detail shortly.

The side wind signal V received by the anemometer is passed through a variable ballistic term multiplier 1164 of the type previously described by multiplying it by a side wind coefficient IC ^ for each selected ammunition to produce a signal, V K-. This signal is then passed through a love multiplier 1166 of the type explained with reference to FIG . Signal VI is also applied directly to a non-inverting input of operational amplifier 1168 so that an output signal VK (1-B) is generated to correct for deviations from standard conditions. This signal is passed through a secondary multiplier 1170 in that it is multiplied by the signal T (Q? - t ^) when the input signal RQÜiL * from. a hand control switched on ^. _; is * y / ¹ ^ b generate the wind deflection angle signal ν * , z \ i ,, .. djas a second ■ input of the siimmenden, n _K Q $ erati, onsyerstärkers 1162, ^ after which. _r esi da, z ^ bjs is used to correct the deflection signal D and the elevation signal E

00 9 809/1507.

The flight time multiplier T for the secondary multiplier I17O is generated when the time-of-flight signal t _{f is added to} the main multiplier 988. The main / secondary level multiplier 986, 1170 with time division is of the type has been described above with reference to Fig., and may be operated with an ac input signal e = t ~ sin Vt received by the output multiplier 988 and a dc input signal VK received by the life multiplier 1170. As stated above, the period of the alternating current signal t _f sin Vt must be much larger than the period of the main multiplier 988. As a result, the current multiplier operates essentially as described above for a DC input signal for any particular duty cycle.

If, however, the input signal t _f sin <U t is a partial current signal, the output signal t _f sin A; t / e _d = (T ₂ - T ^) / T ₂ + T ^ j) of the main multiplier changes 988 from period to period and gives a pulse width modulated output signal. I3T example, the input signal e _m - _£ sin t 0, the Summierintegrator 1024 is no current e "supplied and it is the output signal be a Hechteckwelle with T ^ = T _2. As the signal t ^ sin A / t increases from sin 0 ° to sin 90 °, the time T ₂ increases, until the duration of T is very short with respect to the time T ₂ . If the signal t _£ sin «t changes in the range between sin 90 ° and sin 270 °, the duration of T ^ increases until T _{2 is} short with respect to T. When the signal t »sin Wt changes from sin 2? 0 ° to sin 360 °, the duration of T ₂ increases and the duration increases

009809 / ί507.

by T ^. until the output signal is again a square wave with T. = T ~. The output of the main multiplier 988 changes in the manner described above during each period of e _ffl .

The first Kebenachalter 1034 · and the second Ifebeschalter 10 ^ 6 received as described above, the Output signal T of the main part 988 and deliver a Output signal at their common outputs that is your pulse width modulated output signal of the main part 988 corresponds to · The output of the first lift switch 1034- and the second IT-side switch 1036 are fed to an averaging filter 1042 so that a filtered output signal is generated which can be represented by the following expression:

^sin

The waveforms shown in Fig. Λ are also applicable to a main IT even multiplier with time division, in which an alternating current signal t ~ sin (Jt is supplied to the main part 988 and a direct current signal VK (1-B) to the secondary part 1170.

The azimuth angular velocity V ₇ . of the tower is fed through a follow-up and clamp circuit 1172, in which it is stored as a direct current signal * when the input signal ETLL is received »-

A typical follow-up and clamping circuit that is suitable for ta _a and W _A in a disturbed or undisturbed

009809 / i507

To scan the fire control system is in Piß. "" 7 shown and comprises a switch 1182 which is responsive to a direct current signal cJ ,. appeals to. Dor input of an amplifier 1184 is grounded through a suitable resistor 1186 and connected to the switch 1182 via a resistor 1188 · Furthermore, the output of the amplifier is 1184 through one of a feedback resistor 1190 and a switch 1192 existing series circuit and also through a capacitor 1194 to the input tied together. Switches 1188 and 1192 respond to switch controls 1198, which in turn respond to the Respond in advance interlocking control signal RTLL. The switches 1188 and 1192 are closed for filter operation and open for a hold operation when the RTLL signal has ended · This condition applies to disturbed and undisturbed operation · For director operation the switches 188 and 1192 remain closed as shown, so that a filtering effect takes place In all operating modes, switch 1196 is closed in the absence of an RTLL signal · If the scanning and Holding circuit enable of the RTLL signal is used, the switch controller 1198 causes the switch to open Switches 1182 and 1192 so that the angular velocity is stored as a direct current signal «J, - ·

This DC signal is then passed through a secondary multiplier 1174 of the above by multiplying it by the time-of-flight signal T to form a kinematic lead angle signal 4 / ^ T. If it is a single circuit system, this kinematic lead angle signal A; JE is represented by an analog

009809/1507

switch 1176a as a single kinematic gyro lead angle ! signal n.Y. deni the other input of the operational amplifier 1162 for correcting the deflection signal D and the elevation signal E supplied.

The analog switches 1176a and 1176b illustrated in FIG. 8 receive the single kinematic gyro lead vortex signal "> | j_. = O ^ t- at an input terminal 1204 and the optional second kinematic gyro lead angle signal Wt-, as will be explained in more detail below

egg '

will be explained in detail at a second Input terminal 1206. The switching signal RTLL is on an input terminal 1212 received. This switching signal RTLL is usually on a lower level when the computer is not in the CALCULATE mode, so that the input signals at terminals 1208 and 1210 are at ground potential to output terminals 121-4- and 1216 arrive.

When in detail the Sehaltsignal RTLL, which is fed to the terminal 1212, is low, the diode circuit 1218 is acted upon in the forward direction, so that one end of the base current resistor 1220 is at ground potential. This signal with ground potential v / ird is passed through a threshold circuit 1222 which contains two diodes connected in series in order to block an npn transistor 1224. Furthermore, a base-emitter resistor 1226 is connected between the base and the emitter of the transistor 1224. A bias network comprising resistors 1228 and 1230 and connected between the collector and a + 12V terminal

009809/1507

BATH ORIGINAL

a resistor 1232 UBiflt, is -between the + 12V terminals and a + 5OV KIeCiEIe at one end and the base of a transistor 1234- switched "to" the base voltage keep it at 12V + A.V depending on the state of the transistor 1224. \ 7If, for example, transistor 1224 is in its normally blocked state, is that fed to the base of transistor 1234 Voltage greater than + 12V and the transistor 1234 is blocked, -the-part of a differential- ^ is stronger. When transistor 1234 is blocked, the other transistor 1236 of the differential amplifier leading what resol. the voltage at the emitter, which is from the current flow through the emitter resistor 1238. results, and the potential formed at the collector resistor 1240 is to be traced back.

In this state of the differential amplifier the area field effect transistors 1242 and 1244 of .-. a - 'signal switched on, which their saturated electrodes is supplied by the Köllektor voltage applied to Collector resistance 1240 is present. When switched on Area effect transistors 1242 and 1244 become the signal received at "input terminals 1208 and 1210" with I.lasaepotential via the cathode-anode lines of field effect transistors 1242 and 1244 to output terminals 1214 and 1216. Because the transistor 1234 of the differential amplifier is blocked the voltage drop across the collector resistor 1246 low, so that the gate electrodes of the field effect transistors 1248 and 125Ο a signal of low voltage is supplied, which blocks these transistors. As a result-

009809/1507

& mm

- 55 - '"■' ■ - ' - ■■■; ■.

do s 3 on, the input signals e 4 / ,, t_ and ta _a t _r die

(X vx - ■ "

fed to input terminals 1204 and 1206, cannot be forwarded to output terminals 1214 and 1216 «

The diode circuit when the input terminal 1212 supplied switching signal RTLL aimiinnt a high value _r v / ith 1218 applied in the reverse direction, whereby the level of the signal at the lower end of the Basisstromwider- ■: ■ object 1220 increases "This signal is the over the threshold value circuit 1222 Transistor 1224 supplied to bring it into the conductive state. When transistor 1224 is on, the flow of current through the bias network comprising resistors 1228, 1230, and 1232 causes the voltage across the circuit to decrease. Base of transistor 1234 to a value below + 12V, whereby transistor 1234 is switched on «

When transistor 1234 of the differential amplifier is on, the other transistor 1236 is off. As a result, the voltage drop across the collector resistor 1246 increases, whereas the voltage drop across the collector resistor 1240 decreases. As a result, the collector voltage 1234 is fed to the gate electrodes of the field effect transistors 1248 and 1250 in order to switch these transistors on, whereupon the input signals A / ^ t ^ and Q ₆ ^ f are fed to the output terminals 1214 and 1216 via the cathode-anode paths of the field effect transistors «The decrease in voltage at the collector of transistor 1236 is fed to the gate electrodes of field effect transistors 1242 and 1244 to block these transistors,

. ■■■ "" -. '; ■ -: ■: ■■■■ "." ■: ■:' ■■ ■ · / ·: ■■■

0 09809 / Ί507

after which "the signal at ground level, which is fed to input terminals 1208 and 1210, no longer applies can be routed to the output terminals.

The output signal B of the operational amplifier 1162 then becomes B = * u + ti + η. .. However, if there is a two-circle system, the switching contacts of a Einkreiseschalters 1178 are switched and ea is then this kinematic Vorhältwinkelsignal ^ I ^ f ^e i fed ^nem input of an operational amplifier 1180, and it is the signal B to ** !, " + i? _w

Da3 on sat zwinlceloignal t is also immediately a The input of an operational amplifier 1252 is fed to produce a signal A which is equal to £ (A "« ■■ £ ").

The output signals A and B of the operational amplifier 1162 and 1252 can be switched directly through analog switches 1254-a and 1254b of the type previously described eu inputs from operational amplifiers 1180 and 1257 when the skew signal C is on the "Off" level is »If the tilt signal is 0 "A" is it can first through an inclined position resolver 1256 before it passed over that Analog switches 125 ^ -a and 1254b to the inputs of the Operational amplifiers 1180 and 1257 is fed when the skew solver is on. Even though If an inclined solver has been specifically named, it is understood that "instead, other types of He-solvers could be used ";

809L / -T5

Assuming that the inclined position resolver 1256 is in operation, the output signals A and B of the operational amplifiers are fed to a winding of the Hesölver and resolved into tower coordinates which take into account the angle of inclination of the tower with respect to the horizontal and generate output signals which, in accordance with this Lean angles are resolved. One way to accomplish this is to have a first winding connected to a pendulum so that the first winding is moved relative to a stationary second winding so that the inductive coupling between the legs of the windings with the position of the movable winding changes. The output of the lean resolver 1246 then becomes an uncorrected deflection signal D ¹ and an uncorrected elevation signal E 'of the shape

D ¹ = Bcos C + AsinC
and

E ¹ = AcosO + BsinO.

These uncorrected deflection and elevation ^{signals D 1} and E ¹ are then fed through the analog switches 1254a and 1254b to one of the summing inputs of the operational amplifiers 1180 and 1267, in which they are further corrected. Other inputs of operational amplifiers 1180 and 1257 receive jump signals D. and

E. Supplied by variable attenuators 1258 and 1260 for each selected ammunition. Another input of the operational amplifiers 1180 and 1257 receives the parallax coefficient 1 / H-1 / R- » der of

009809/1507

generated by the function generator 990 according to Pic; · 1A will. Another input signal to the operational amplifier is the hanging of the gun barrel in the deflection D-, and the elevation E ,. The inputs of the Operational amplifiers contain an adjustable resistor for the reinforcement of the parallax coefficient multiplied by the deflection parallax constant D, which is intended for each tank * The OperajL tion amplifier 1257 has a setting ™ in the input Resistance for the gain, the parallax coefficient with the elevation parallax constant D multiplied, which is determiiant for each tank. If it is a. Is a two-circle system, that will SignalÖ t from the product of the tower angular speed

■ - ■ - ■. ■ ex ■. ■ -. "'■ ■ -. ■" ■.

koit in the elevation and the flight time ^{fed to another input of the operational amplifier 125 r} r in order to compensate for the kinematic Vorhaitev / inkel in the elevation »

If a two-circuit system is used, a Signal «J_ for the speed of the finish line

|| supplied in the elevation of a second follow-up and clamping circuit 1262 of the type described above with reference to Fig. 7, which stores the signal al3 DC signal cj. This direct current signal Q v / ird by a

IT secondary multiplier 1264 · of the type described above, in that it is multiplied by the time-of-flight signal I in order to generate an output signal A) t - which is the kinematic lead angle. acts in elevation. This kinematic flow angle in elevation 4) _e t _f becomes one through the analog switch 1176b and the single-circuit switch 1178

009809/1507

8AD ORIGINAL

Input of operational amplifier 1257 is led and the kinematic correction angle in the deflection {/,.t ,, supplied 1180im deflection conduit through the Einlcreiseschalter 1178 one input of the operational amplifier · _"-:.;

The output signals of the operational amplifiers 1180 and 1257 are switched by analog switches 1278a and 1278b of the type described above that routed the signal only then forward when the EECIflTEH Will be received. '. ■ '

Operational amplifiers 1280 and 1282 receive the Output signals of analog switches 1278a and 1278b together with the target line correction signal D, in the deflection or the target line correction signal E. in

the elevation. These;? Operational amplifiers 1280 and 1282 generate the deflection - "- correction signals D and the elevation correction signal E, which signals a Servo amplifiers are supplied

00980971507

Claims (10)

Patent claim Ballistic calculator for use with a distance measuring circuit, which is a distance signal generated, characterized by a first. Lhilti-— application device that sends the distance signal multiplied by a "ballistic term" representing the properties of a particular projectile and special environmental conditions is characteristic, and thereby generates a normalized distance signal, a second multiplier, which is the normalized distance signal multiplied by a first and a second function, which functions are applicable to floors and the properties of the bullet and the environmental conditions are independent, and thus a first and generates a second ballistic function signal, a third and a fourth multiplier, one of which is the first and the others use the second ballistic function signal multiplied by a term that represents the properties of the special projectile and the special environmental conditions is characteristic, and thereby generates a time-of-flight signal or an attachment angle signal, and a constant multiplier that the time-of-flight signal and / or the attachment angle signal multiplied by constants and thereby makes corrections for ballistic deviations based on deviating ballistic and environmental conditions « 009809/1507 2. Ball is tiler ecliner according to claim 1, characterized in that that the ballistic iDerme for the first, the third and fourth multiplication devices are adjustable so that ballistic function signals for one selected from a number of ammunition types certain · ammunition are produced. 5 · Ballistic computer according to Claim 1 or 2, characterized in that the constant multiplication device one on a detected crosswind signal Has appealing device and the time-of-flight signal with one for a ballistic constant characteristic signal and the determined crosswind signal to correct a crosswind deflection multiplied. 4. Ballistikre.chner according to claim 3 »characterized in that that the constant multiplier can be set to any type of ammunition, around the plug time signal with a characteristic for a corresponding ballistic constant Signal and the crosswind signal to multiply for each one of different types of ammunition « 5 ballistic calculator according to one of the preceding claims, characterized in that the constant multiplier comprises a ballistic drift "multiplier" which provides the head angle signal with a signal characteristic of a ballistic constant for correction of the ballistic Drift multiplied * 009809/1507 i & iAifföiSi ^ it s ^ 8AO OfUOiNAt 6. Ballistic style calculator according to claim 5 »thereby. Marked, that the ballistic drift multiplier can be adjusted to any type of ammunition in order to Attachment angle signal with a characteristic for a corresponding ballistic constant Ballistic drift correction signal for each of a number of different types of ammunition the selected type of ammunition. P 7 · Ballistic computer according to one of the preceding claims, characterized in that the constant multiplication device furthermore has a kineiaati— see lead angle multiplier which multiplies a signal characteristic of the angular speed of a tower in azimuth by the time-of-flight signal and thereby generates an azimuth angle signal * 8. Ballistic calculator according to one of the preceding Claims, characterized in that the constant multiplication device still a jkiuemati- * see lead angle multiplier on v / eist, which is a the signal characteristic of the angular velocity of a tower in elevation is multiplied by the time-of-flight signal and thereby an elevation angle lead signal generated. _S that it comprises 9 »ballistic according to any one of the preceding claims, characterized in that a summer summing the sum of the constant multiplier signals and producing a corrected generated Ballistilcsignales. 10. Ballistic computer according to one of the preceding claims, characterized in that a circuit arrangement for multiplying the normalized range signals3 with one or more: i _: terms of the type (1 + Kf ¹ Cu)) is arranged in series with the first! .Iultiplikationaeinrichtung, in which terraces K is a predetermined constant and f '(u) is the ratio of the change in a standard condition to this standard condition, which is assigned to a corresponding ballistic tern of the first multiplier. 11 * ballistic computer according to one of the preceding claims, characterized in that the third and / or fourth multiplication device Circuit arrangement for multiplying the flight time signal or the attachment angle signal with a Term of the type (1 + Kf '(u)) naclige schalt et is, in which term K is a predetermined constant and f '(u) is the ratio of the change in a standard condition to that of the standard condition corresponding to the ballistic Tex'm the third bzvr. fourth multiplier facility assigned. 12 * ballistic calculator according to claim 10, characterized in that that the normalized distance signal is 'multiplied' by the term (1 - B), with B « A3? / I? O - K4T / Tq, AP of the deviation of the ruling Air pressure from the air pressure Pq under standard conditions, K is a temperature coefficient and Δ T is the deviation of the prevailing temperature from the temperature Tq at standard conditions. 009809/1507 13 · Ballistic calculator according to claim 11, characterized in that the time-of-flight signal is multiplied by the terms (1 + B) and (1-H) and / or the top / angle signal is multiplied by the terms (1 + B) and (1-211) , with B = ΔΡ / Pq - KÄT / T _Q , ΔΡ the deviation of the prevailing air pressure from the air pressure Pq under standard conditions, K a temperature coefficient, ßT the deviation of the prevailing temperature from the temperature T _Q under standard conditions, H = ΔV / Vq and ΔY of the deviation of the muzzle velocity from a standard muzzle velocity Vq as a function of the effective full charge, deviations in the propellant charge temperature and the temperature coefficient of a selected ammunition. 009809 / ISO? BW