DE102018010285B3 - Packet detector / decoder for a radio transmission system - Google Patents

Abstract

Embodiments provide a data receiver, wherein the data receiver is adapted to receive a wideband signal, the wideband signal comprising at least two sub-data packets distributed in time and / or frequency, the data receiver having a filter bank configured to dividing the received wideband signal into a plurality of subband signals for detection or decoding of the sub-data packets, the plurality of subband signals having different subbands of the wideband signal, the filter bank having a polyphase filter, the filter bank being a first filter bank configured to divide the received wideband signal into the plurality of subband signals for the detection of the sub-data packets, the data receiver having a second filter bank configured to convert the received broadband signal into a plurality of subband signals for decoding the sub-data split, wherein the plurality of subband signals have different subbands of the wideband signal, wherein the second filter bank comprises a polyphase filter.

Description

Embodiments relate to a data receiver and, more particularly, to a data receiver for receiving a wideband signal having a plurality of sub-data packets distributed in time and frequency according to a time-hopping pattern. Some embodiments relate to a packet detector / decoder for a radio transmission system.

From the DE 10 2011 082 098 B4 a telegram splitting based radio transmission system is known in which a data packet (or message) to be transmitted is split into a plurality of sub-data packets, wherein the plurality of sub-data packets are each shorter than the data packet, and wherein the plurality of sub-data packets Data packets are transmitted in accordance with a time-hopping pattern in the time and frequency distributed.

From the EP 3 125 453 A1 For example, a data receiver for receiving payload data sent by a data transmitter by means of at least one data packet over a communication channel is known. The data receiver comprises means for receiving data packets configured to receive the at least one data packet, the at least one data packet having channel-coded user data and at least one indicator, wherein the means for receiving data packets is adapted to provide for the at least one data packet receive received data packet comprising the received channel-coded user data and the at least one received indicator. Furthermore, the data receiver comprises a device for the further processing of received data, which is designed to determine the received channel-coded user data and the at least one received indicator from the received data, and the at least one received indicator of the at least one received data packet with at least one reference indicator , which is known to the data transmitter and data receiver, and to determine based on the comparison between the at least one received indicator and the at least one reference indicator at least one degree of interference of the received channel coded user data of the at least one received data packet, wherein the means for further processing of received data is adapted to weight the received channel-coded user data of the at least one received data packet based on the determined at least one degree of interference for decoding, and one of the Gewich tion of the received channel-coded user data dependent channel decoding to perform the payload data.

The publication [ JAISWAL, K .: Spectral Sensing of Adaptive Frequency Hopping Signal for Cognitive Radio. In: IEEE International Performance, Computing and Communications Conference, 7 - 9 December 2008, pp. 360 - 365 ] refers to the detection of a frequency hopping signal based on a filter bank, the filter bank having a polyphase filter.

In the simultaneous or temporally overlapping transmission of a plurality of data packets divided into sub-data packets by a plurality of data transmitters, the computing power required for the data receiver to detect and decode the sub-data packets increases considerably.

The object of the present invention is to reduce the computing power required for the detection and decoding of partial data packets in the data receiver.

This object is solved by the independent claims.

Advantageous developments can be found in the dependent claims.

Embodiments provide a data receiver, wherein the data receiver is adapted to receive a wideband signal, wherein the wideband signal comprises at least two sub-data packets [eg wherein the at least two sub-data packets comprise different parts of a data packet] which corresponds, for example, to a hop pattern the time and / or frequency are distributed, wherein the data receiver [eg comprises a detector which is designed to perform a detection of the at least two partial data packets in the wideband signal, and by at least one detection parameter [eg detection time and / or detection frequency] for the detected sub-data packets [for example to provide a detection parameter (eg detection time and / or detection frequency) for each of the detected sub-data packets or, for example, only one detection parameter (eg (reference) detection time and / or (reference) detection frequency) For to provide the hopping pattern of the at least two partial data packets, wherein by the definition of the hopping pattern receiving times and / or receiving frequencies of the at least two partial data packets are implicitly known], wherein the data receiver [eg Decoder configured to perform decoding of the detected sub-data packets using the at least one detection parameter, wherein the data receiver is adapted to detect the at least two sub-data packets and the decode the detected sub-data packets ] separately from each other or process.

In embodiments, the detection parameters may relate, for example, to the data packets in the sense that they specify a reference point from which a localization of the sub-data packets can take place with the aid of a jump pattern. As a rule, however, there is no sub-data packet at the reference point itself, since no sub-data packet with time offset = 0 and frequency offset = 0 is usually contained in the jump patterns.

In embodiments, the detection parameters allow localization of the sub-data packets of the detected data packets by serving as reference points for the hopping patterns.

In embodiments, the data receiver [e.g. the detector of the data receiver] be designed to perform the detection continuously.

In embodiments, the data receiver [e.g. the decoder of the data receiver] may be designed to perform the decoding in dependence on an available computing power of the data receiver [for example to perform the decoding of one of the detected partial data packets if sufficient computing power is available for this purpose].

In embodiments, the data receiver may be configured to detect the detection and the decoding in various [e.g. separate] processes to execute or process

In embodiments, the data receiver may be configured to detect the detection and the decoding at different [e.g. separate] processors of the data receiver or at different [e.g. separate] processor cores or threads of a processor of the data receiver to execute or process.

In embodiments, the data receiver may include separate signal processing devices [e.g. Detector in the FPGA, decoder in the DSP or GPP], which are connected to one another via a data interface, wherein the data receiver is designed to execute or process the detection and the decoding on different signal processing devices.

In embodiments, the at least two sub-data packets may comprise a first plurality of sub-data packets and a second plurality of sub-data packets, the first plurality of sub-data packets including first data [e.g. a first telegram or a first sub-data packet] divided into the first plurality of sub-data packets [e.g. distributed according to a jump pattern] on a plurality of frequency channels and transmitted at different timings, the second plurality of sub-data packets including second data [e.g. a second telegram or a second sub-data packet] divided into the second plurality of sub-data packets [e.g. distributed according to a jump pattern] on a plurality of frequency channels and transmitted at different times, wherein the data receiver is adapted to decode detected partial data packets of the first plurality of partial data packets and decode detected partial data packets of the second plurality of partial data packets. Perform data packets in parallel [eg in different (e.g., separate) processes].

In embodiments, the first plurality of sub-data packets and the second plurality of sub-data packets may be transmitted by the same data transmitter

In embodiments, the first plurality of sub-data packets and the second plurality of sub-data packets may be transmitted by different data transmitters.

In embodiments, the data receiver may be configured to start the decoding of the detected sub-data packets of the first plurality of sub-data packets or the second plurality of sub-data packets independently of the other decoding, if all the sub-data packets of the respective plurality of sub-data packets Data packets were detected or if enough sub-data packets of the respective plurality of sub-data packets for a likely successful decoding were detected taking into account a sender-side redundancy-introducing coding.

In embodiments, the data receiver may be formed [e.g. the data receiver may comprise a signal ring memory which may be configured to receive the received wideband signal or a further processed version of the wideband signal [e.g. For example, a version of the wideband signal (e.g., a subband-separated version of the wideband signal) divided into a plurality of subband signals [for example, a ring buffer having the maximum delay length of the signal (plus any processing times)] may be used for decoding.

For example, the data receiver may have a ring memory, wherein the ring memory has the maximum delay length of the signal (plus any processing times).

In embodiments, the further processed version of the wideband signal may be a version of the wideband signal divided into a plurality of subband signals.

In embodiments, the data receiver may be configured to temporarily store, in time and / or frequency, a subsampled version of the wideband signal or the further processed version of the wideband signal.

For example, only every second, third, fourth frequency line and / or time line can be stored to reduce memory requirements.

In embodiments, the data receiver [eg, the signal ring memory of the data receiver] may be configured to store the received broadband signal between, wherein the data receiver [eg, the decoder of the data receiver] is configured to generate a subsample U (= f _WB / f _SYNC = M _WB / M _SYNC ) [eg such that a sample rate f _SYNC (= M _SYNC * f _sym ) of a further processed version of the received wideband signal [eg a version divided into a plurality of subband signals and filtered (eg, channel filter and / or matched filter) of received wideband signal] is less than a sampling rate f _W (= M _WB · f _sym ) of the received wideband signal]

In embodiments, the data receiver may be configured [eg, the detector of the data receiver may comprise a first filter bank that may be configured] to divide the wideband signal for the detection of the plurality of sub-data packets into a plurality of subband signals, wherein the plurality of Subband signals different [eg partially overlapping] subbands of the wideband signal, the data receiver [e.g. the detector of the data receiver] is adapted to perform the detection of the at least two sub-data packets in the different sub-bands of the plurality of sub-band signals [e.g. by correlating the plurality of subband signals with a (known) synchronization sequence or synchronization sequences contained in the sub-data packets.

In embodiments, the data receiver [e.g. the first filter bank of the detector of the data receiver] may be configured to convert the wideband signal by a polyphase filtering or a polyphase filter bank [e.g. and dividing an N-point DFT or N-point FFT] into the plurality of subband signals.

In embodiments, the data receiver [eg, the first filter bank of the detector of the data receiver] may be configured to perform a subsampling U _DET (= f _WB / f _DET = M _WB / M _DET ) when dividing the wideband signal into the plurality of subband signals [eg, FIG a sampling rate f _DET (= M _DET * f _sym ) of the plurality of subband signals is less than a sampling rate f _WB (= M _WB * f _sym ) of the received wideband signal].

In embodiments, the at least two sub-data packets may comprise a first plurality of sub-sub data packets, the first plurality of sub-data packets including first data [e.g. a first telegram or a first sub-data packet] distributed on the first plurality of sub-data packets on a plurality of frequency channels and transmitted at different times, wherein the data receiver [eg the detector of the data receiver] is further configured to a [eg coarse] frequency and / or time offset of the detected partial data packets of the first data, the detection parameters also being determined by the determined [e.g. coarse or estimated] frequency and / or time offset

In embodiments, the plurality of subband signals to which the wideband signal is split may be the further processed version of the wideband signal which is cached [eg in the signal ring memory] for decoding, the data receiver [eg, the data receiver decoder]. is designed to extract the detected partial data packets using the detection parameters [eg detection times and / or detection frequencies] from the respective subband signals buffered [eg in the signal ring memory] [eg by filtering (eg channel filter and / or matched filter) and / or (fine) (time and / or frequency) synchronization] [and decode, for example].

In embodiments, the data receiver [eg, the data receiver decoder] may be configured to perform an oversampling M (= f _SYNC / f _DET = M _SYNC / M _DET ) of the plurality of buffered subband signals [eg, so that a sample rate f _SYNC (= M _SYNC · f _SYM ) of a further processed version [eg, a filtered version (eg, interpolation filter) of the plurality of cached subband signals] is greater than a sampling rate f _DET (= M _DET * f _SYM ) of the plurality of cached subband signals.

In embodiments, the data receiver may be formed [e.g. the data receiver decoder may comprise a second filter bank which may be configured to divide the wideband signal for decoding the detected sub-data packets into a plurality of subband signals, the plurality of subband signals having different [e.g. partially overlapping] subbands of the wideband signal, the data receiver [e.g. the decoder of the data receiver] is adapted to detect the detected sub-data packets using the detection parameters [e.g. Detection timings and / or detection frequencies] from the respective subband signals [e.g. by filtering (e.g., channel filters and / or matched filters) and / or (fine) (time and / or frequency) synchronization] [and e.g. to decode].

In embodiments, the data receiver [e.g. the decoder of the data receiver] to select a suitable subband signal of the plurality of subband signals for the decoding of the detected sub-data packets, and to extract the detected sub-data packets from the respective subband signals [for example, the data receiver using the respective detection parameters (eg, detection times and / or detection frequencies) select appropriate (time) portions of appropriate subband signals for decoding the respective detected sub-data packets and extract the respective detected sub-data packets from the selected subband signals [eg, by filtering (eg, channel filters and / or Matched filter) and / or (fine) (time and / or frequency) synchronization] [and eg to decode].

In embodiments, the data receiver [e.g. the second filter bank of the decoder of the data receiver] may be configured to convert the wideband signal by a polyphase filtering or polyphase filter bank [e.g. and dividing an N-point DFT or N-point FFT] into the plurality of subband signals.

In embodiments, the data receiver [eg, the second filter bank of the decoder of the data receiver] may be configured to perform a subsampling U _IM (= f _WB / f _IM = M _WB / M _IM ) when dividing the wideband signal into the plurality of subband signals [eg a sampling rate f _IM (= M _IM * f _sym ) of the plurality of subband signals is less than a sampling rate f _WB (= M _WB * f _sym ) of the received wideband signal].

In embodiments, the data receiver [e.g. the second filter bank of the decoder of the data receiver] to divide the wideband signal into a plurality of subband signals having overlapping subbands, the subbands [e.g. [For example, passbands of adjacent filter channels of the second filterbank may overlap by at least the bandwidth of one of the sub-data packets so that the sub-data packets are extracted without significant distortion from one of two overlapping filter channels can].

In embodiments, the data receiver [eg, the second filter bank of the decoder of the data receiver] may be configured to divide the wideband signal into a plurality of subband signals having overlapping subbands, wherein in dividing [eg, filtering (eg, polyphase filtering)] the wideband signal a sum from a bandwidth of a passband for one of the subband signals and a stopband bandwidth [eg width of the transition from passband to stopband] of a subband signal adjacent to the subband signal is not greater than a double sampling rate f _IM (= M _IM * f _sym ) of the plurality of subband signals For example, the stopband width must not be greater than the passband].

In embodiments, the data receiver [eg, the decoder of the data receiver] may be configured to provide a keying U (= f _IM / f _SYNC = M _IM / M _SYNC ) of the plurality of subband signals perform [eg, such that a sample rate f _{SYNC of} a further processed version of the plurality of subband signals [eg a filtered version (eg channel filter and / or matched filter) of the plurality of subband signals] is higher or lower than a sample rate f _{IM of} the plurality of subband signals].

In embodiments, the keying may be subsampling U (= f _IM / f _SYNC = M _IM / M _SYNC ) [eg such that a sample rate f _{SYNC of} a further processed version of the plurality of subband signals [eg a filtered version (eg channel filter and / or matched Filter) of the plurality of subband signals] is less than a sampling rate f _IM the plurality of subband signals].

In embodiments, a sampling rate f _IM (= M _IM * f _sym ) of the plurality of subband signals (eg provided by the second filter bank of the decoder) for decoding the detected sub-data packets may be greater than a sampling rate f _DET (= M _DET * f _sym ) of the plurality of subband _signals (eg provided by the first filter bank of the detector) for the detection of the at least two sub-data packets.

In embodiments, a number of subband signals N _IM the subband signals for the decoding of the detected sub-data packets (eg provided by the second filter bank of the decoder) are less than a number of subband signals N the subband signals (for example provided by the first filter bank of the detector) for the detection of the at least two sub-data packets.

In embodiments, the data receiver may be configured to divide the received wideband signal by means of different filter characteristics into the plurality of subband signals for the detection of the at least two sub-data packets and the plurality of subband signals for the decoding of the detected sub-data packets [for example, the first filter bank of Detector and the second filter bank of the decoder have different filter characteristics].

In embodiments, the different filters may have different frequency responses.

In embodiments, a bandwidth of the wideband signal may be at least as large that the at least two sub-data packets may be transmitted at a maximum allowable frequency offset between data transmitter and data receiver [e.g. due to the inaccuracy of the quartz crystals used] can be received by the data receiver.

Further embodiments provide a method of receiving a wideband signal, wherein the wideband signal comprises at least two sub-data packets transmitted over different frequencies [e.g. Frequency channels] are distributed. The method includes a step of detecting the at least two sub-data packets in the wideband signal to provide at least one detection parameter for the detected sub-data packets. Furthermore, the method comprises a step of decoding the detected sub-data packets using the detection parameters, wherein the detection and the decoding are performed or processed separately from each other.

Further embodiments provide a data receiver, wherein the data receiver is adapted to receive a wideband signal, wherein the wideband signal comprises at least two sub-data packets which [e.g. distributed in time and / or frequency, the data receiver having a filter bank configured to convert the received wideband signal into a plurality of subband signals for a [e.g. splitting subsequent detection or decoding of the sub-data packets, the plurality of sub-band signals having different [e.g. partially overlapping] subbands of the wideband signal, wherein the filter bank comprises a polyphase filter.

In embodiments, the filter bank may include an N-point DFT or N-point FFT.

In embodiments, the filter bank may include an N-channel mixer.

In embodiments, the filter bank may be configured to subsample the received wideband signal such that a sample rate of the plurality of subband signals is less than a sample rate of the received wideband signal.

In embodiments, the filter bank may be a first filter bank configured to divide the received wideband signal into the plurality of subband signals for the [eg, subsequent] detection of the sub-data packets, wherein the data receiver comprises a second filter bank configured to to divide the received wideband signal into a plurality of subband signals for the [eg, subsequent] decoding of the sub-data packets, the plurality of subband signals having different sub-bands of the broadband signal, the second filter bank having a polyphase filter.

In embodiments, the second filter bank may include an N-point DFT or N-point FFT.

In embodiments, the second filter bank may be configured to subsample the received wideband signal such that a sample rate of the plurality of subband signals is less than a sample rate of the received wideband signal.

In embodiments, the second filter bank may be configured to divide the wideband signal into a plurality of subband signals having overlapping subbands, the subbands [e.g. [For example, passbands of adjacent filter channels of the second filterbank may overlap by at least the bandwidth of one of the sub-data packets so that the sub-data packets are extracted without significant distortion from one of two overlapping filter channels can].

In embodiments, the second filterbank may be configured to divide the wideband signal into a plurality of subband signals having overlapping subbands, wherein in the division [e.g. Filtering (e.g., polyphase filtering)] the wideband signal is a sum of a bandwidth of a passband for one of the subband signals and a stopband bandwidth of a subband signal adjacent to the subband signal is not greater than a double sample rate of the plurality of subband signals.

In embodiments, a sample rate f _IM (= M _IM * f _sym ) of the plurality of subband signals provided by the second filter bank for decoding the sub-data packets may be greater than a sample rate f _DET (= M _DET * f _sym ) from that of the first Filterbank the detector provided plurality of subband signals for the detection of the sub-data packets.

In embodiments, a number of subband signals N _IM the sub-band signals provided by the second filter bank for the decoding of the sub-data packets are less than a number of sub-band signals N of the sub-band signals provided by the first filter bank for the detection of the sub-data packets.

In embodiments, the first filter bank and the second filter bank may have different filter characteristics.

In embodiments, the data receiver may include a detector that may be configured to detect the at least two sub-data packets in the different subbands of the plurality of subband signals [eg, by correlating the plurality of subband signals with a (known) one contained in the sub-data packets. Synchronization sequence] to provide detection parameters [eg, detection timings and / or detection frequencies] for the detected sub-data packets [eg, to provide at least one detection parameter (eg, detection timing and / or detection frequency) for each of the detected sub-data packets].

In embodiments, the data receiver may include a decoder, which may be configured to extract detected sub-data packets from the respective sub-band signals using detection parameters [e.g. by filtering (e.g., channel filters and / or matched filters) and / or (fine) (time and / or frequency) synchronization] [and e.g. to decode].

Further embodiments provide a method for receiving a wideband signal, wherein the wideband signal comprises at least two sub-data packets transmitted over different frequencies [e.g. Frequency channels] are distributed. The method comprises a step of filtering the received wideband signal with a filter bank to convert the received wideband signal into a plurality of subband signals for a [e.g. splitting subsequent detection or decoding of the sub-data packets, the plurality of sub-band signals having different [e.g. partially overlapping] subbands of the wideband signal, wherein the filter bank comprises a polyphase filter.

• 1 ein schematisches Blockschaltbild eines Systems mit einem Datensender und einem Datenempfänger, gemäß einem Ausführungsbeispiel der vorliegenden Erfindung;
• 2 in einem Diagramm eine Belegung des Übertragungskanals bei der Übertragung einer Mehrzahl von Teil-Datenpaketen entsprechend einem Zeitfrequenzsprungmuster;
• 3 ein schematisches Blockschaltbild eines Datenempfängers, gemäß einem Ausführungsbeispiel der vorliegenden Erfindung;
• 4 in einem Diagramm eine Belegung des Übertragungskanals bei der Übertragung von Datenpaketen unter Verwendung von vier unterschiedlichen Übertragungsverfahren;
• 5 ein schematisches Blockschalbild eines einkanaligen Detektors eines Datenempfängers, gemäß einem Ausführungsbeispiel;
• 6 ein schematisches Blockschaltbild eines Vielkanal-Detektors eines Datenempfängers, gemäß einem Ausführungsbeispiel;
• 7 ein schematisches Blockschalbild eines Vielkanal-Detektors eines Datenempfängers, gemäß einem Ausführungsbeispiel;
• 8 ein schematisches Blockschalbild eines Signal-Ringspeichers eines Datenempfängers, gemäß einem Ausführungsbeispiel;
• 9 ein schematisches Blockschaltbild eines Decoders eines Datenempfängers, gemäß einem Ausführungsbeispiel;
• 10 ein schematisches Blockschaltbild eines Datenempfängers, gemäß einem Ausführungsbeispiel;
• 11 ein schematisches Blockschaltbild eines Datenempfängers, gemäß einem weiteren Ausführungsbeispiel;
• 12 ein schematisches Blockschaltbild eines Datenempfängers, gemäß einem weiteren Ausführungsbeispiel;
• 13 ein schematisches Blockschaltbild einer Filterbank eines Decoders eines Datenempfängers, gemäß einem Ausführungsbeispiel;
• 14 in einem Diagramm Durchlassbereiche benachbarter Filterkanäle der in 13 gezeigten Filterbank, gemäß einem Ausführungsbeispiel;
• 15 in einem Diagramm einen Durchlassbereich und eine Sperrbandbreite eines Filterkanals der in 13 gezeigten Filterbank, gemäß einem Ausführungsbeispiel;
• 16 zeigt ein Flussdiagramm eines Verfahrens zum empfangen eines Breitbandsignals, gemäß einem Ausführungsbeispiel, und
• 17 zeigt ein Flussdiagramm eines Verfahrens zum empfangen eines Breitbandsignals, gemäß einem weiteren Ausführungsbeispiel.

Embodiments of the present invention will be described with reference to the accompanying figures. Show it:

• 1 a schematic block diagram of a system with a data transmitter and a data receiver, according to an embodiment of the present invention;
• 2 in a diagram an occupancy of the transmission channel in the transmission of a plurality of sub-data packets according to a time-frequency hopping pattern;
• 3 a schematic block diagram of a data receiver, according to an embodiment of the present invention;
• 4 in a diagram an occupancy of the transmission channel in the transmission of data packets using four different transmission methods;
• 5 a schematic block diagram of a single-channel detector of a data receiver, according to an embodiment;
• 6 a schematic block diagram of a multi-channel detector of a data receiver, according to an embodiment;
• 7 a schematic block diagram of a multi-channel detector of a data receiver, according to an embodiment;
• 8th a schematic block diagram of a signal ring memory of a data receiver, according to an embodiment;
• 9 a schematic block diagram of a decoder of a data receiver, according to an embodiment;
• 10 a schematic block diagram of a data receiver, according to an embodiment;
• 11 a schematic block diagram of a data receiver, according to another embodiment;
• 12 a schematic block diagram of a data receiver, according to another embodiment;
• 13 a schematic block diagram of a filter bank of a decoder of a data receiver, according to an embodiment;
• 14 in a diagram passages of adjacent filter channels of in 13 shown filter bank, according to an embodiment;
• 15 in a diagram, a passband and a blocking bandwidth of a filter channel of in 13 shown filter bank, according to an embodiment;
• 16 shows a flowchart of a method for receiving a wideband signal, according to an embodiment, and
• 17 shows a flowchart of a method for receiving a wideband signal, according to another embodiment.

In the following description of the embodiments of the present invention, the same or equivalent elements are provided with the same reference numerals in the figures, so that their description is interchangeable.

Telegram splitting based radio transmission system

1 shows a schematic block diagram of a system with a data transmitter 100 and a data receiver 110 , The data transmitter 100 can be trained to receive a signal 120 to send, with the signal 120 at least two separate sub-data packets 142 having. The data receiver 110 can be trained to receive the signal 120 (or a version of the signal modified by the transmission channel 120 )), which contains the at least two separate sub-data packets 142 having.

As in 1 can be seen, are the at least two separate sub-data packets 142 separated or spaced apart in time and / or in frequency. The distribution of the at least two separate sub-data packets 142 in time and / or frequency can according to a hopping pattern (hopping pattern) 140 respectively.

In embodiments, the data transmitter 100 a transmitter (or transmitter module, or transmitter) 102 which is adapted to the signal 120 to send. The transmitting device 102 can with an antenna 104 of the data transmitter 100 be connected. The data transmitter 100 Furthermore, a receiving device (or receiving module, or receiver) 106 which is configured to receive a signal. The receiving device 106 can with the antenna 104 or another (separate) antenna of the data transmitter 100 be connected. The data transmitter 100 may also have a combined transceiver.

In embodiments, the data receiver 110 a receiving device (or receiving module, or receiver) 116 which is adapted to the signal 120 to recieve. The receiving device 116 can with an antenna 114 of the data receiver 110 be connected. Furthermore, the data receiver 110 a transmitter (or transmitter module, or transmitter) 112 which is configured to transmit a signal. The transmitting device 112 can with the antenna 114 or another (separate) antenna of the data receiver 110 be connected. The data receiver 110 may also have a combined transceiver.

In embodiments, the data transmitter 100 be a sensor node while the data receiver 110 a base station can be. Typically, a communication system comprises at least one data receiver 110 (Base station) and a variety of data transmitters (sensor nodes, such as heating meters). Of course it is also possible that the data transmitter 100 a base station while the data receiver 110 is a sensor node. Furthermore, it is possible that both the data transmitter 100 as well as the data receiver 110 Sensor nodes are. Furthermore, it is possible that both the data transmitter 100 as well as the data receiver 110 Base stations are.

The data transmitter 100 and the data receiver 110 may be configured to send or receive data using a telegram splitting method. In this case, a data packet (or telegram) containing the data is divided into a plurality of sub-data packets (or sub-data packets). 142 split and the partial data packets 142 be according to a jump pattern 140 distributed in time and / or distributed in frequency by the data transmitter 100 to the data receiver 110 transmit, wherein the data receiver 110 the partial data packets 142 reassembles (or combines) to get the actual data packet. Each of the sub-data packets 142 contains only a part of the data package 120 , The data packet can also be channel-coded, so that not all partial data packets are used for error-free decoding of the data packet 142 but only part of the sub-data packets 142 is required.

The temporal distribution of the majority of sub-data packets 142 can, as already mentioned, according to a time and / or frequency hopping pattern 140 respectively.

A time-hopping pattern may indicate a sequence of transmission times or transmission time intervals at which the partial data packets are transmitted. For example, a first partial data packet may be transmitted at a first transmission time (or in a first transmission time slot) and a second partial data packet at a second transmission time (or in a second transmission time slot), the first transmission time and the second transmission time being different. The time jump pattern can define (or specify, or specify) the first transmission time and the second transmission time. Alternatively, the time-jump pattern may indicate the first transmission time and a time interval between the first transmission time and the second transmission time. Of course, the time jump pattern may also indicate only the time interval between the first time and the second transmission time. There may be transmission pauses between the partial data packets in which no transmission takes place. The sub-data packets may also overlap in time (overlap).

A frequency hopping pattern may indicate a sequence of transmission frequencies or transmission frequency jumps with which the sub-data packets are sent. For example, a first partial data packet with a first transmission frequency (or in a first frequency channel) and a second partial data packet with a second transmission frequency (or in a second frequency channel) can be transmitted, wherein the first transmission frequency and the second transmission frequency are different. The frequency hopping pattern can define (or specify, or specify) the first transmission frequency and the second transmission frequency. Alternatively, the frequency hopping pattern may indicate the first transmission frequency and a frequency spacing (transmission frequency jump) between the first transmission frequency and the second transmission frequency. Of course, the frequency hopping pattern may also indicate only the frequency spacing (transmission frequency hop) between the first transmission frequency and the second transmission frequency.

Of course, the majority of sub-data packets 142 also distributed in both time and frequency by the data transmitter 100 to the data receiver 110 be transmitted. The distribution of the plurality of sub-data packets in time and in frequency may be in accordance with a time-hopping pattern. A time-hopping pattern may be the combination of a time-hopping pattern and a frequency hopping pattern, ie a sequence of transmission times or transmission time intervals with which the sub-data packets 142 are transmitted, wherein the transmission times (or transmission time intervals) transmission frequencies (or transmission frequency jumps) are assigned.

2 shows a diagram of an occupancy of the transmission channel in the transmission of a plurality of sub-data packets 142 according to a time-frequency hopping pattern. The ordinate describes the frequency and the abscissa the time.

As in 2 it can be seen, the data packet 120 for example on n = 7 partial data packets 142 divided and distributed according to a time-hopping pattern in the time and frequency of the data transmitter 100 to the data receiver 110 be transmitted.

As in 2 can be further seen, the plurality of sub-data packets 142 next to data (data symbols 146 in 2 ) also pilot sequences (pilot symbols (or synchronization symbols) 144 in 2 ) based on which the data receiver 110 the partial data packets 142 in a received signal 120 or can detect receive data stream. In some embodiments, the detection could also take place without the use of the pilot sequences, this case occurring for example in the radio reconnaissance, if the pilot sequences are not yet known.

In the simultaneous or temporally overlapping transmission of a plurality of data packets divided into sub-data packets by a plurality of data transmitters, however, the computing power required to detect and decode the sub-data packets in the data receiver increases considerably.

In order to reduce the computing power required for the detection and decoding, in embodiments the detection and decoding of the sub-data packets takes place separately or separately from one another, as will be explained below.

Exemplary embodiments of the data receiver (system description)

Embodiments of the present invention relating to signal processing and data storage in the detection and decoding of data packets in the data receiver will now be described 110 a radio transmission system relate.

3 shows a schematic block diagram of a data receiver 110 , according to an embodiment of the present invention. The data receiver 110 is designed to be a broadband signal 120 to receive, with the broadband signal 120 at least two partial data packets 142 having, according to a jump pattern 140 distributed over different frequencies (eg frequency channels).

The data receiver 110 can be a detector 122 which is configured to detect the at least two partial data packets 142 in the broadband signal 120 perform and at least one detection parameter 126 (eg, a detection time and / or a detection frequency) for the detected sub-data packets.

For example, the detector 122 be formed to a detection parameter 126 (eg, a detection time and / or a detection frequency) for each of the detected sub-data packets. Of course, the detector can 122 also be designed to only one detection parameter (eg, a (reference) detection time and / or a (reference) detection frequency) for the jump pattern 140 the at least two sub-data packets 142 provide, by the definition of the jump pattern (eg, transmission times and / or transmission frequencies) the reception times and / or reception frequencies of the at least two partial data packets 142 implicitly known.

The data receiver 110 can also have a decoder 124 formed to be formed using the at least one detection parameter 126 to perform a decoding of the detected sub-data packets, for example by decoded packets 149 to obtain.

The detector 122 and the decoder 124 can be carried out separately or separately, so that the detector 122 the detection (the at least two partial data packets 142 ) and the decoder 124 the decoding (the detected sub-data packets) can perform or process separately. The data receiver 110 is thus designed to detect (the at least two partial data packets 142 ) and decoding (the detected sub-data packets) separately or to process.

In embodiments, the detector 122 be formed to the detection (the partial data packets 142 ) continuously.

In embodiments, the decoder 124 be formed to the decoding depending on an available computing power of the data receiver 110 perform.

For example, the decoder 124 be configured to perform the decoding of one of the detected sub-data packets when sufficient computing power is available for the decoding of the respective detected sub-data packet.

In other words, 3 shows the components, a packet detector 122 for detecting the packets in a wideband signal 120 and a packet decoder 124 for the evaluation of the detected packets. The detected packets represent the detection times at which presumably a packet at the receiver 110 has arrived.

As in 3 is shown by way of example, the data receiver 110 a detector (packet detector) 122 and a decoder (packet decoder) 124 exhibit. Of course, the data receiver 110 also be implemented by means of a processor, microprocessor or other programmable logic circuit, in which case the in 3 shown circuit blocks, for example, can be implemented by appropriate algorithms.

4 shows a diagram of an occupancy of the transmission channel in the transmission of data packets using four different transmission methods. It describes in 4 the ordinate the frequency and the abscissa the time. In other words, 4 shows four possible methods for transmitting a single packet.

A first transmission method (case 1 ) comprises a continuous transmission of a data packet at a constant frequency.

A second transmission method (case 2 ) comprises a continuous transmission of a data packet in connection with a frequency hopping method.

A third transmission method (case 3 ) comprises a discontinuous transmission of a data packet (telegram splitting) at a constant frequency.

A fourth transmission method (case 4 ) comprises a discontinuous transmission of a data packet (telegram splitting) in connection with a frequency hopping method.

Embodiments of the data receiver 110 are relevant to all four methods if a plurality of packets to be received by different transmitters asynchronously and at different frequencies are to be received, such that the wideband signal 120 at the input has a much higher bandwidth than the (sub) packets (in the case 1 Packages, in the fells 2 to 4 Part packages). Particularly relevant are embodiments of the data receiver 110 in the case 4 which enables a particularly high degree of parallel asynchronous packet transmissions.

On top of that, in the transmitters 100 For cost reasons frequency generators are used with relatively high tolerance, so that in all four cases a frequency offset between transmitter 100 and receiver 110 occurs, which is a multiple of the symbol rate f _sym the part packages 142 can amount. Since this effect reduces the likelihood of packet collisions, the maximum throughput of the transmission system can be increased by selectively adding a stochastic component to the transmission frequencies. As a result, the transmission frequencies in the receiver 110 basically unknown.

The detection and synchronization of the packets in the receiver 110 can with the help of synchronization sequences (pilot sequences with synchronization symbols 144 ) in the (sub) packages. In general, these sequences are in the middle of the sub-packages 142 arranged (midamble). However, embodiments are applicable to all possible arrangements of the synchronization sequence (preamble, midamble, postamble).

Signal processing in the detector

5 shows a schematic block diagram of a single-channel detector 122 , according to an embodiment. The detector 122 can a DDC 150 (= digital down converter, dt. Digital down converter), which may be formed to the wideband signal 150 to mix and filter. For this purpose, the DDC 150 for example, a mixer 152 and a channel filter 154 exhibit. Furthermore, the detector can 122 a matched filter 156 , a correlator 158 and a packet detection 160 exhibit.

In other words, 5 shows the signal processing in a single-channel detector 122 at known reception frequency f _C , Thereby the sampling rate of the signal in the DDC becomes 150 from the sampling rate f _WB of the broadband signal 120 on the sampling rate f _DET the following components 156 . 158 reduced. The channel filter (CF) 154 can act as an anti-aliasing filter for sub-sampling and can have a sufficiently high stopband attenuation for this purpose.

On the DDC 150 follow a matched filter (MF) 156 for pulse filtering, a multi-level correlation (CORR) 158 for the synchronization sequences of the sub-packets and their summary, and the actual packet detection 160 ,

In the following, all sampling rates are additionally in multiples of the symbol rate f _sym the part packages 142 specified. For the detector 122 applies: $${\text{f}}_{\text{WB}}={\text{M}}_{\text{WB}}\cdot {\text{f}}_{\text{sym}}{\text{and f}}_{\text{DET}}={\text{M}}_{\text{DET}}\cdot {\text{f}}_{\text{sym}}$$

Values for M _DET are for example (typically, for example) 2 and 4, ie the processing in the detector 122 can for example (eg usually) be done with twice or four times the symbol rate. The value for M _WB is usually (eg considerably) larger, ie it applies $${\text{f}}_{\text{DET}}<<{\text{f}}_{\text{WB}}{\text{or M}}_{\text{DET}}<<{\text{M}}_{\text{WB}}$$

Due to the frequency offset between transmitters 100 and receiver 110 can the detector 122 as a multi-channel detector with N parallel receive channels are executed, as in the following with reference to 6 is explained.

6 shows a schematic block diagram of a multi-channel detector 122 , according to an embodiment. In other words, 6 shows a multi-channel detector with N channels. As in 6 can be seen, the multi-channel detector 122 a mixer for each channel 152 , a channel filter 154 , a matched filter 156 and a correlator 158 exhibit.

kann von den verwendeten Synchronisationssequenzen und der Art der Korrelation abhängen und kann beispielsweise (z.B. in der Regel) 1/4...1/16 der Symbolrate f_sym betragen: $${\text{M}}_{\text{C}}=4\dots 16$$

The permissible channel distance $$\Delta {\text{f}}_{\text{C}}={\text{f}}_{\text{sym}}/{\text{M}}_{\text{C}}$$

may depend on the synchronization sequences used and the type of correlation and may, for example (eg, as a rule) 1/4 ... 1/16 of the symbol rate f _sym be: $${\text{M}}_{\text{C}}=4...16$$

This allows the data stream at the output of the matched filter 156 and at the output of the first stage of the correlation by the factor M _C · M _{DET be} greater than the data stream of the wideband signal 120 at the entrance. The number of channels is: $$\text{N}={\text{M}}_{\text{WB}}\cdot {\text{M}}_{\text{C}}$$

The realization of the mixer 152 , the channel filter (CF) 154 and the Matched Filter (MF) 156 can be done through a polyphase filter bank (CMFB) as shown in 7 is shown. The filters CF 154 and MF 156 to a polyphase filter (CF + MF) summarized.

In detail shows 7 a schematic block diagram of the detector 122 , according to an embodiment. The detector 122 includes a (first) filter bank 162 and the correlators 158 , the filter bank 162 may be formed to the broadband signal 120 by polyphase filtering (and, for example, an N-point DFT or N-point FFT) in N subband signals 164 to divide the correlators 158 may be configured to detect the partial data packets 142 in the N subband signals 164 perform, for example by correlation of the N subband signals 164 with one in the sub-data packets 142 contained (known) synchronization sequence or synchronization sequences As in 7 Further, multi-channel filtering can be done with an N-point DFT or, if N is a power of two, with an N-point FFT. The polyphase factor P gives the ratio of the number N _P the filter coefficients and the number N of channels and depends on the channel spacing - given by the factor Mc - and the required blocking attenuation of the filter. Values are, for example (typically, for example) in the range P = 1... 2. For P = 1 results in a common filter bank with N _P = N.

kann durch eine entsprechende Schrittweite im Breitbandsignal realisiert werden.The subsampling by the factor $${\text{U}}_{\text{DET}}={\text{f}}_{\text{WB}}/{\text{f}}_{\text{DET}}={\text{M}}_{\text{WB}}/{\text{M}}_{\text{DET}}$$

can be realized by a corresponding step width in the broadband signal.

The signals of the individual channels can be converted by a derotation into baseband signals (subband signals) without frequency offset.

The following table (Table 1) summarizes the parameters of the detector 122 together and gives examples of a system 1 with MWB = 96 and a system 2 with MWB = 1024. For both systems, MDET = 2 and MC = 8 are examples. Name of the parameter parameter equation System 1 System 2 Oversampling of the broadband signal M _WB 96 1024 Oversampling in time direction M _DET 2 2 Oversampling in frequency direction M _C 8th 8th Sub-scan = step size U _DET M _WB / M _DET 48 512 Number of channels = length of OFT / FFT N M _WB × M _C 768 8192 Polyphasenfaktor P 1 1 Number of coefficients of the filter N _P P · N 768 8192 Increase in the data stream K _DET M _C · M _DET 16 16

The computation required is very high due to the typically high number of channels N and depends only slightly on the number of packets detected.

Delay of the broadband signal

The processing in the packet detector 122 has a delay resulting from the delay of the filters and the distance between the synchronization sequences of the first and last sub-packets 142 can assemble. Therefore, the broadband signal can 120 by means of a signal ring memory 170 be delayed before it's the packet decoder 124 can be fed, as in 8th is shown.

In detail shows 8th a schematic block diagram of a signal ring memory 170 which is adapted to receive the received wideband signal 120 between to store a delayed wideband signal 120 ' to obtain. In other words, 8th shows a delay of the wideband signal 120 ,

In a software receiver 110 In addition, for massively parallel reception, the delay may include the time that may elapse from the detection of a packet to the actual processing of the packet.

Signal processing in the decoder

9 shows a schematic block diagram of a decoder 124 , according to an embodiment. The decoder 124 is designed to be based on that of the detector 122 provided detection parameters 126 (eg reference time (coarse) t _{PKT, C} , and frequency (coarse) f _{PKT, C} ) a detected partial data packet 142 to decode.

The decoder 124 for example, an extractor 180 which is configured to be based on that of the detector 122 provided detection parameters 126 (eg reference time (coarse) t _{PKT, C} , and frequency (coarse) f _{PKT, C} ) a suitable signal section (eg in frequency and time direction, symbolized by switches 181 and mixers 182 ). Furthermore, the decoder 124 a mixer 182 , a channel filter 184 , a matched filter 186 , a t / f synchronization 188 and a packet decoding 190 exhibit.

As in 9 can be seen, the processing in the decoder on the basis of the parameters (detection parameters 126 ) of a detected packet. Here, the reference time t _{PKT, C} the detection time in the packet detector 122 with a temporal granularity Δt _{PKT, C} = 1 / f _DET . The frequency f _{PKT, C} may correspond to the center frequency of the detector channel in which the packet was detected. The granularity Δf _{PKT, C} may correspond to the channel spacing Δf _C.

The desk 180 and the mixer 182 in 9 symbolize the selection of the signal sections of the sub-packets 142 in time and frequency direction based on the parameters (detection parameters) 126 , In the channel filter (CF) 184 a sub-sample can be sampled at the sampling rate. $${\text{f}}_{\text{SYNC}}={\text{M}}_{\text{SYNC}}\cdot {\text{f}}_{\text{sym}}$$

The associated sub-sampling factor is: $${\text{U}}_{\text{SYNC}}={\text{f}}_{\text{WB}}/{\text{f}}_{\text{SYNC}}={\text{M}}_{\text{WB}}/{\text{M}}_{\text{SYNC}}$$

This results for the subsequent t-synchronization t _{PKT, F} a granularity Δt _{PKT, F} = 1 / f _SYNC , Values are, for example (typically, for example) in the range M _SYNC = 4 ... 16.

Also in the decoder 124 can the channel filter (CF) 184 and the Matched Filter (MF) 186 to a single filter (CF + MF). Here, for example, the same filter as in the polyphase filter bank (CMFB) 162 of the detector 124 in 7 result. The filtering can be as ordinary polyphase filtering with a sub-sampling by the factor U _SYNC respectively. Alternatively, the filtering can be done by means of fast convolution (Fast Convolution) in the frequency domain. This is also useful because the signal portions of the subpackets are often so short that the fast convolution can occur in a block.

verursachte Symbolinterferenz zu beseitigen.The f-synchronization f _{PKT, F} can be detected by a corresponding rotation of the signal after the matched filter (MF) 186 respectively. However, in the case of increased requirements by a higher-level modulation method in conjunction with a high granularity Δf _{PKT, C} , it may be necessary to repeat the mixing and filtering with the more precise value f _{PKT, F} , by the frequency offset $$\Delta {\text{f}}_{\text{PKT}}={\text{f}}_{\text{PKT}.\text{F}}-{\text{f}}_{\text{PKT}.\text{C}}$$

to eliminate caused symbol interference.

After successful t / f synchronization, the symbols can be displayed with symbol rate f _sym taken and the packet decoding 190 be supplied

The following table (Table 2) summarizes example parameters in the decoder 124 together. Name of the parameter parameter equation System 1 System 2 Oversampling of the broadband signal M _WB 96 1024 Oversampling in time direction M _SYNC 12 8th undersampling U _SYNC M _WB / M _SYNC 8th 128 Number of coefficients (CF + MF) N _P see det. 768 8192

In the 9 The processing shown is for each detected sub-packet 142 ie the required computational effort is proportional to the number of detected sub-packets 142 , With massively parallel reception of the computational effort increases sharply and can the computational effort in the detector 122 exceed.

Interplay of packet detector and packet decoder

10 shows a schematic block diagram of a data receiver 110 , according to an embodiment. The data receiver 110 includes a detector 122 , a decoder 124 and a ring signal memory 170 ,

The detector 122 can be a first filter bank 162 which may be configured to receive the wideband signal 120 for the detection of the partial data packets 142 in N Sub-band signals 164 to divide, with the N Subband signals different (eg partially overlapping) subbands of the wideband signal 120 can have. The detector 122 may be configured to detect the partial data packets 142 in the N Sub-band signals 164 perform, for example, by correlation of N Sub-band signals 164 with one in the sub-data packets 142 contained (known) synchronization sequence or synchronization sequences to detection parameters 126 (eg detection times and / or detection frequencies) for the detected sub-data packets 142 provide.

For example, the detector 122 a correlation and packet detection 166 which may be configured to perform the correlation and packet detection. This can be done by correlation and packet detection 166 eg the in 7 shown correlators 158 exhibit.

The signal ring memory 170 may be configured to receive the received wideband signal 120 between to store a delayed wideband signal 120 ' provide.

The decoder 124 can be configured to the detected data packets 142 using the detection parameters 126 from the received broadband signal 120 (or from the delayed version of the received wideband signal 120 ' ) to extract.

This can be done by the decoder 124 For example, a plurality of in 9 shown extractors 180 and filtering 183 (eg channel filter 184 and matched filters 186 ) exhibit. There may be a number of channels of the decoder 124 with a number N of channels of the detector 122 to match. Of course, the decoder can 124 also have more or fewer channels than the detector 122 ,

With a small number of detected packets, this is in 9 shown embodiment of the data receiver 110 usable without problems. Because here are the signal sections with the sub-packets 142 from the broadband signal 120 is extracted due to the high subsampling U _SYNC a high computational effort, which can be problematic in massively parallel reception under certain circumstances.

This can be remedied in 11 shown embodiment of a data receiver 110 create where the subband signals 164 from the packet detector 122 also in the package decoder 124 be used.

In detail shows 11 a schematic block diagram of a data receiver 110 , According to another embodiment. The data receiver 110 includes a detector 122 , a decoder 124 and a ring signal memory 170 ,

The detector 122 can be a first filter bank 162 which may be configured to receive the wideband signal 120 for the detection of the partial data packets 142 in N Sub-band signals 164 to divide, with the N Sub-band signals 164 different (eg partially overlapping) subbands of the wideband signal 120 exhibit. The detector 122 may be configured to detect the partial data packets 142 in the N Sub-band signals 164 perform, for example, by correlation of N Sub-band signals 164 with one in the sub-data packets 142 contained (known) synchronization sequence or synchronization sequences to detection parameters 126 (eg detection times and / or detection frequencies) for the detected sub-data packets 142 provide.

For example, the detector 122 a correlation and packet detection 166 This may be configured to perform the correlation and packet detection. For this, the correlation and packet detection 166 eg the in 7 shown correlators 158 exhibit.

The signal ring memory 170 may be designed to be that of the first filter bank 162 of the detector 122 provided N subband signals 164 to save between.

The decoder 124 can be configured to the detected partial data packets 142 using the detection parameters 126 (eg detection times and / or detection frequencies) from the respective in the signal ring memory 170 cached subband signals 164 to extract, for example by filtering (eg channel filter and / or matched filter) and (fine) time and / or frequency synchronization.

This can be done by the decoder 124 for example, a plurality of extractors 180 and interpolation filters 185 exhibit. There may be a number of channels of the decoder 124 with a number N at channels of the detector 122 to match. Of course, the decoder can 124 also have more or fewer channels than the detector 122 ,

In 11 the selectors (SEL) and the switches symbolize the extraction of the signal sections of the sub-packets from the respective sub-band signals 164 of the packet detector 122 , A mixture is due to the derotation of the signals in the polyphase filterbank 162 of the packet detector 122 not mandatory.

durchgeführt werden. Der dazu erforderliche Rechenaufwand ist erheblich geringer, da die selektive Filterung bereits durch das Polyphasen-Filter im Paket-Detektor 122 erfolgt und deshalb eine einfache Interpolation im Frequenzbereich verwendet werden kann. Dadurch wird der erforderliche Rechenaufwand bei massiv parallelem Empfang im Vergleich zu dem in 10 gezeigten Ausführungsbeispiel des Datenempfängers 110 erheblich reduziertIn this arrangement, oversampling (interpolation) may be by the factor $${\text{f}}_{\text{SYNC}}/{\text{f}}_{\text{DET}}={\text{M}}_{\text{SYNC}}/{\text{M}}_{\text{DET}}$$

be performed. The required computational effort is considerably lower, since the selective filtering already by the polyphase filter in the packet detector 122 takes place and therefore a simple interpolation in the frequency domain can be used. As a result, the required computational effort at massively parallel reception in comparison to the in 10 shown embodiment of the data receiver 110 considerably reduced

However, that too has in 11 shown embodiment of the data receiver 110 under some circumstances, a disadvantage that may be that the data stream of the detector signals (subband signals 164 ) by the factor given in Table 1 K _DET is greater than the data stream of the broadband signal 120 This reduces the required size of the signal ring memory 170 also by the factor K _DET to. Values for K _DET are for example (eg typically) in the range 8th ... 16th For broadband signals 120 With a high bandwidth already takes the data stream of the broadband signal to high values. Another significant increase in these cases is problematic or even impossible. As an example, here are the values of the system 2 with M _WB = 1024 and a symbol rate f _sym = 2 kBaud. The sampling rate f _WB of the broadband signal 120 is in this case 2048 ksps. Assuming that the discontinuous transmission of the partial packets 142 of a packet takes about 5 seconds and the complex-valued wideband signal is in floating-point format with 8 bytes per complex sample, the data stream of the wideband signal is 16 MByte / s and the memory size of a signal ring buffer for the wideband signal 80 Mbyte. It follows with K _DET = 16 for a signal ring buffer for the detector signals a memory size of 1280 MByte. The use of other data formats can reduce the size of the memory, but the factor remains K _DET approximately obtained between the two variants.

The following table (Table 3) summarizes the characteristics of the two embodiments of the data receiver 110 out 10 and 11 together. arrangement computational complexity memory requirements 10 high low 11 low high

Using a pre-decomposition of the wideband signal

12 shows a schematic block diagram of a data receiver 110 , According to another embodiment. The data receiver 110 includes a detector 122 , a decoder 124 , a second filter bank 172 and a ring signal memory 170 ,

The detector 122 can be a first filter bank 162 which may be configured to receive the wideband signal 120 for the detection of the partial data packets 142 in N Sub-band signals 164 to divide, with the N Subband signals different (eg partially overlapping) subbands of the wideband signal 120 exhibit. The detector 122 may be configured to detect the partial data packets 142 in the N Sub-band signals 164 perform, for example, by correlation of N Sub-band signals 164 with one in the sub-data packets 142 contained (known) synchronization sequence or synchronization sequences to detection parameters 126 (eg detection times and / or detection frequencies) for the detected sub-data packets 142 provide.

For example, the detector 122 a correlation and packet detection 166 which may be configured to perform the correlation and packet detection. This can be done by correlation and packet detection 166 eg the in 7 shown correlators 158 exhibit.

The second filter bank 172 may be formed to the broadband signal 120 for the decoding of the detected sub-data packets 142 in N _IM Sub-band signals 174 to divide, with the N _IM Sub-band signals 174 different (eg partially overlapping) subbands of the wideband signal 120 exhibit.

This can be a number N _IM at subband signals of the second filter bank 172 provided subband signals 174 for the decoding of the detected sub-data packets 142 be less than a number N at subband signals of the first filter bank 162 of the detector 122 provided subband signals 164 for the detection of the at least two partial data packets 142 ,

The signal ring memory 170 may be formed to that of the second filter bank 172 provided N _IM Sub-band signals 174 to save between.

The decoder 124 may be configured to detect the detected sub-data packets using the detection parameters 126 (eg detection times and / or detection frequencies) from the respective in the signal ring memory 170 cached subband signals 174 to extract, for example by filtering (eg channel filter and / or matched filter) and (fine) time and frequency synchronization

For example, the decoder 124 be formed to each for the decoding of the detected partial data packets, a suitable subband signal of the N _IM Sub-band signals 174 select and the detected sub-data packets 142 to extract from the respective subband signals. For example, the decoder 124 using the respective detection parameters (eg detection times and / or detection frequencies) select appropriate (time) sections of suitable subband signals for decoding the respective detected sub-data packets and extract the respective detected sub-data packets from the selected subband signals, for example by filtering (eg channel filter and / or matched filters) and (fine) time and frequency synchronization.

This can be done by the decoder 124 for example, a plurality of extractors 180 and filtering (eg channel filter and / or matched filter) 183 exhibit.

This in 12 shown embodiment of the data receiver 110 is based on a pre-decomposition of the broadband signal 120 , As a result, a compromise between the computational effort in massively parallel reception and the memory requirement can be achieved.

The broadband signal 120 can with an additional polyphase filter bank (IMFB) 172 be subdivided into overlapping subbands, as in 13 is shown.

In detail shows 13 a schematic block diagram of the second filter bank 172 , according to an embodiment. As in 13 it can be seen, the second filter bank 172 be formed to the broadband signal 120 by polyphase filtering and N-point DFT or N-point FFT into the plurality of subband signals 174 divide.

The sampling rate can be based on the pre-decomposition rate f _IM be reduced. The associated sub-sampling factor is: $${\text{U}}_{\text{IN THE}}={\text{f}}_{\text{WB}}/{\text{f}}_{\text{IN THE}}={\text{M}}_{\text{WB}}/{\text{M}}_{\text{IN THE}}$$

1. 1. f_IM > f_SYNC: Unterabtastung in der Filterung (CF+MF) 183 erforderlich
2. 2. f_IM < f_SYNC: Überabtastung in der Filterung (CF+MF) 183 erforderlich
3. 3. f_IM = f_SYNC: keine Änderung der Abtastrate erforderlich

With reference to the sampling rate f _SYNC in the decoder 124 There are three cases:

1. 1. f _IM > f _SYNC : subsampling in the filtering (CF + MF) 183 required
2. 2. f _IM <f _SYNC : oversampling in the filtering (CF + MF) 183 required
3. 3. f _IM = f _SYNC : no change of the sampling rate required

Regarding the computational effort in pre-decomposition is the case 1 cheapest and the case 2 most unfavorable. Regarding the computational effort in the packet decoder 124 the conditions are exactly the opposite. There is no preference for memory requirements, as the sample rate is reduced f _IM the number N _IM the channels must be increased.

Even with a pre-decomposition, the data stream increases because the sum of the bandwidth of the subbands is greater than the bandwidth of the wideband signal given an overlap (eg required) 120 , The factor of increase is: $${\text{K}}_{\text{IN THE}}={\text{N}}_{\text{IN THE}}\cdot {\text{f}}_{\text{IN THE}}/{\text{f}}_{\text{WB}}={\text{N}}_{\text{IN THE}}\cdot {\text{M}}_{\text{IN THE}}/{\text{M}}_{\text{WB}}$$

However, this factor takes the maximum value in practice 2 on, ie the sum data stream of the subband signals 174 is at most twice the data stream of the wideband signal 120 ,

• • Die Durchlassbereiche benachbarter Filterkanäle können sich mindestens um die Bandbreite B_S eines Teil-Pakets 142 überlappen, damit ein Teil-Paket 142 in diesem Bereich ohne nennenswerte Verzerrungen entweder dem einen oder dem anderen Filterkanal entnommen werden kann, siehe 14 Beim Filterentwurf kann der zur Verfügung stehende Spielraum voll ausgenutzt werden: B_S = B_IM-Δf_CIM.
• • Die Summe aus der Bandbreite B_IM des Durchlassbereichs und der Sperrbandbreite B_IMS kann den Wert 2·f_IM nicht überschreiten, damit der Überlappungsbereich frei von Alias-Produkten bleibt, siehe 15. Auch hier kann der zur Verfügung stehende Spielraum beim Filterentwurf voll ausgenutzt werden: B_IM+B_IMS = 2·f_IM.

The Polyphase Filter (IMF) of the Polyphase Filter Bank (IMFB) 172 can fulfill two conditions:

• • The passbands of adjacent filter channels can be at least around the bandwidth B _s a partial package 142 overlap, hence a part package 142 in this area can be removed without significant distortion either the one or the other filter channel, see 14 When designing the filter, the available latitude can be fully exploited: B _S = B _IM -Δf _CIM .
• • The sum of the bandwidth B _IM the passband and the blocking bandwidth B _IMS can not exceed 2 · f _IM , so that the overlap area remains free of alias products, see 15 , Again, the available latitude in the filter design can be fully exploited: B _IM + B _IMS = 2 · f _IM .

• • Bandbreite eines Teil-Pakets: B_S = b_S·f_sym mit b_S = 1...2
• • Bandbreite des Durchlassbereichs: B_IM = B_IM·f_IM mit b_IM < 1
• • Kanalabstand: Δf_CIM = f_WB/N_IM

The following relationships can apply:

• • Bandwidth of a sub-packet: B _S = b _S · f _sym with b _S = 1 ... 2
• Bandwidth of the passband: B _IM = B _IM * f _IM with b _IM <1
• • Channel spacing: Δf _CIM = f _WB / N _IM

From this it follows with f _IM = M _IM * f _sym and f _WB = M _WB * f _sym the condition: $${\text{N}}_{\text{IN THE}}>{\text{M}}_{\text{WB}}/\left({\text{M}}_{\text{IN THE}}-{\text{b}}_{\text{S}}\right)$$

des Durchlassbereichs und einer normierten Sperrbandbreite $${\text{B}}_{\text{IMS}}/{\text{f}}_{\text{WB}}=\left(2\cdot {\text{M}}_{\text{IM}}-{\text{b}}_{\text{S}}\right)/{\text{M}}_{\text{WB}}-1/{\text{N}}_{\text{IM}}$$

entworfen werden. Die zur Erzielung einer ausreichend hohen Sperrdämpfung erforderliche Koeffizienten-Anzahl N_PIM ist in der Regel deutlich größer als die Kanalanzahl N_IM . Der erforderliche Polyphasenfaktor $${\text{P}}_{\text{IM}}={\text{N}}_{\text{PIM}}/{\text{N}}_{\text{IM}}$$

liegt beispielsweise (z.B. in der Regel) im Bereich 6...10.The values for b _s and M _WB are predetermined. From the value pairs ( M _IM . N _IM ), which fulfill the condition, the value pair is selected, for which the computational effort is minimized with massively parallel reception with the maximum expected packet rate. For each value pair ( M _IM . N _IM ) the associated polyphase filter (IMF) with a normalized bandwidth $${\text{B}}_{\text{IN THE}}/{\text{f}}_{\text{WB}}={\text{b}}_{\text{S}}/{\text{M}}_{\text{WB}}+1/{\text{N}}_{\text{IN THE}}$$

of the passband and a normalized stopband bandwidth $${\text{B}}_{\text{IMS}}/{\text{f}}_{\text{WB}}=\left(2\cdot {\text{M}}_{\text{IN THE}}-{\text{b}}_{\text{S}}\right)/{\text{M}}_{\text{WB}}-1/{\text{N}}_{\text{IN THE}}$$

be designed. The coefficient number required to achieve a sufficiently high stopband attenuation N _PIM is usually much larger than the channel count N _IM , The required polyphase factor $${\text{P}}_{\text{IN THE}}={\text{N}}_{\text{PIM}}/{\text{N}}_{\text{IN THE}}$$

is for example (eg usually) in the range 6 ... 10th

For the system considered as an example 1 M _WB = 96 and M _SYNC = 12. For the bandwidth of the sub-packets, b _S = 2. This results in the condition: $${\text{N}}_{\text{IN THE}}>96/\left({\text{M}}_{\text{IN THE}}-2\right)$$

$${\text{B}}_{\text{IMS}}/{\text{f}}_{\text{WB}}=\left(2\cdot 12-2\right)/96-1/16=\mathrm{0,1667}$$

To the case 3 to receive at the decoder 124 no change in sampling rate is required, M _IM = M _SYNC = 12 must apply. It follows for the number of channels: N _IM > 9.6. Thus theoretically a DFT of length N _IM = 10 could be used. This is the factor _IM but very close to unity, so that the polyphase filter (IMF) must have a very high number of coefficients. A good compromise is achieved in this case with an FFT of length N _IM = 16. In this case, the values for the normalized bandwidths of the filter are: $${\text{B}}_{\text{IN THE}}/{\text{f}}_{\text{WB}}=2/96+1/16=0.0833$$

$${\text{B}}_{\text{IMS}}/{\text{f}}_{\text{WB}}=\left(2\cdot 12-2\right)/96-1/16=.1667$$

zu. Hinsichtlich des Rechenaufwands im Decoder wäre ein geringerer Wert für M_IM anzustreben, z.B M_IM = 6. Dies erfordert N_IM > 24 In diesem Fall wäre eine FFT der Länge N_IM = 32 günstig. Ob dadurch der insgesamt benotigte Rechenaufwand bei der maximal zu erwartenden Paketrate verringert werden kann, muss experimentell ermittelt werden.A corresponding filter design with a blocking attenuation above 80 dB leads to a filter N _PIM = 96 coefficients. The polyphase factor is P _IM = 6. The data stream decreases by the factor $${\text{K}}_{\text{IN THE}}={\text{N}}_{\text{IN THE}}\cdot {\text{M}}_{\text{IN THE}}/{\text{M}}_{\text{WB}}=16\cdot /96=2$$

to. With regard to the computational effort in the decoder, a lower value for M _{IM would} be desirable, for example M _IM = 6. This requires N _IM > 24. In this case, an FFT of length N _IM = 32 would be favorable. Whether this reduces the total computational effort required at the maximum packet rate that can be expected must be determined experimentally.

• • Das in 10 gezeigte Ausführungsbeispiel des Datenempfängers 110 ist für sehr geringe Paketraten optimal. In diesem Fall kann der zusätzliche Rechenaufwand für die Vorzerlegung nicht durch einen verringerten Rechenaufwand im Paket-Decoder 124 kompensiert werden.
• • Das in 11 gezeigte Ausführungsbeispiel des Datenempfängers 110 ist bezüglich des Rechenaufwands für sehr hohe Paketraten optimal. Es entspricht dem Grenzfall einer maximalen Vorzerlegung, bei der die Teilbänder der Vorzerlegung jeweils einen Empfangskanal bilden und die drei beteiligten Filter - das Filter in der Vorzerlegung (IMF), das Kanal (CF) und das Matched Filter (MF) zu einem Filter zusammenfallen. Der Datenstrom nimmt dabei jedoch stark zu.

Generally, the optimal value for M _IM decreases with increasing packet rate. The term - b _s in the denominator of the above condition that the number N _IM of the channels when approaching M _IM at bs increases strongly. In this area, then the data flow increases more. The arrangements in 10 and 11 are to be regarded as borderline cases.

• • This in 10 shown embodiment of the data receiver 110 is optimal for very low packet rates. In this case, the additional computational effort for the pre-decomposition can not be reduced by a reduced amount of computation in the packet decoder 124 be compensated.
• • This in 11 shown embodiment of the data receiver 110 is optimal in terms of computational effort for very high packet rates. It corresponds to the limiting case of a maximum pre-decomposition, in which the subbands of the predistortion each form a receiving channel and the three filters involved - the filter in the pre-decomposition (IMF), the channel (CF) and the matched filter (MF) coincide to form a filter. However, the data stream is increasing strongly.

1. 1. Bestimmung des Teilbandes, in dem der Signalabschnitt liegt (SEL)
2. 2. Entnahme des Signalabschnitts aus dem Signal des Teilbandes (SW)
3. 3. Mischung des Signalabschnitts auf Frequenzlage Null (M)
4. 4. Schnelle Faltung (Fast Convolution) des Signalabschnitts mit dem Filter (CF+MF)

The extraction of the signal sections of the sub-packets 124 from the subbands can be done in four steps, see 12 :

1. 1. Determination of the subband in which the signal section lies (SEL)
2. 2. Removal of the signal section from the signal of the subband (SW)
3. 3. Mixing the signal section to zero frequency position (M)
4. 4. Fast convolution of the signal section with the filter (CF + MF)

1. 1. Transformation des Signalabschnitts mittels FFT in den Frequenzbereich
2. 2. Multiplikation mit der Frequenzbereichsdarstellung des Filters (CF+MF)
3. 3. Rücktransformation mittels IFFT in den Zeitbereich

The fast convolution can usually be done in a block due to the shortness of the signal sections. It includes the following three steps:

1. 1. Transformation of the signal section by means of FFT in the frequency domain
2. 2. Multiplication with the frequency domain representation of the filter (CF + MF)
3. 3. Back transformation using IFFT into the time domain

In cases where f _IM ≠ f _SYNC or M _IM ≠ M _SYNC , the required under- or oversampling is done by shortening or expanding (zero stuffing) the transformed section in the frequency domain. The IFFT in this case is shorter or longer than the FFT.

Further embodiments

Separate processing of detector and decoder

In general, in a receiver, the detector determines the necessary processing power of the system. If a telegram is detected in the detector, it must be further processed to extract the (presumed) transmitted data. In order for the system to be able to process the "additional" detections, it is necessary to estimate how many telegrams arrive on average at the base station, for example. These telegrams must be included in the calculation of the necessary computing power.

Typically, these detections are processed directly after detection in the same process. This offers the advantage that the data required for the processing need not be buffered. With massively parallel reception of telegrams, however, this approach can not be implemented because the computing power of the detector is no longer sufficient due to the additional processing of the telegrams.

One solution for this is the separate processing of detector and decoder (see 3 ). The detector 122 gives the detection parameters on successful detection 126 at the decoder 124 Next, which takes care of the following processing. This leaves the computing power of the detector 122 (almost) constant and easier to estimate.

The decoder 124 can be processed on one or more additional core (s) in systems with multiple cores (CPU) or on different processors. The calculation of the computing power of the decoder 124 is analogous to a system with combined detector / decoder.

Furthermore, it is also possible to use the detector 122 and the decoder 124 to operate on different signal processing units which are interconnected via a data interface (eg detector in the FPGA, decoder in the DSP or GPP)

Optionally, a separate decoder process can be started for each detected telegram. This process waits until the necessary data is available for decoding. Likewise, after receiving part of the data, it can already start a first decoding attempt and, if successful, terminate again. The further data must therefore no longer be decoded. If the attempt is unsuccessful, the decoder can wait for further data and later start another decoding attempt.

Another advantage in this type of processing is the possibility of processing the individual detections in parallel. Thus, a short telegram, which was detected later, can be processed earlier than a telegram, which requires even more data. This can reduce the system's maximum memory length by minimizing system latency.

Another advantage of this methodology is that with a (short-term) excessively high number of detected telegrams, it is relatively easy to discard individual detected telegrams without having to expose the detector. As a result, the subsequent telegrams are not affected by the (short-term) overload. The selection of which detected telegrams are discarded can be made by means of an overflow buffer or by means of the detection parameters (time, frequency offset, SNR).

In embodiments, the detector can 122 and the decoder 124 run in different modules. For multi-core systems, the detector can 122 in a different thread than the decoder 124 run, in multi-processor systems on a different processor. Between detector 122 and decoders 124 only the detection parameters 126 replaced.

In embodiments, the detection timings may be from the packet detector 122 stored in a "database" and by the packet decoder 124 are taken from this database to perform a decoding. If the system is (temporarily) overloaded, individual detected telegrams can not be processed immediately; they are only taken from the database for processing.

Data storage between detector and decoder

Signal ring buffer for the broadband signal

As per chapter 2.4 becomes a signal ring buffer 170 which uses the wideband signal 120 directly, ie without division into subbands, cached. The decoder 124 When a telegram is detected, it directly accesses the wideband signal and extracts the necessary telegram.

In terms of storage technology, this approach is the best solution because the ring buffer 170 only the data volume of the broadband signal 120 stores. In contrast, the data volume increases by dividing the wideband signal into subbands.

In embodiments, the data memory 170 between detector 122 and decoders 124 the broadband signal 120 without specific further processing included.

In embodiments, the decoder 124 the symbols from the broadband signal 120 Extract using a DDC (digital down converter)

Signal ring buffer for subband signals

Instead of storing the wideband signal 120 can as in chapter 2.4 also the subband signals 164 the filter bank 162 get saved. This has the advantage that the decoder 124 the subband signals 164 can process directly and therefore no DDC is needed anymore. This eliminates the computational effort for the DDC. The disadvantage is the increased storage requirements due to the higher data volume.

If the oversampling factor M _SYNC in the decoder 124 is higher than the oversampling factor M _DET in the detector 122 , can in front of the decoder 124 an oversampling by the factor M _SYNC / M _DET be carried out, for example with an interpolator.

Instead of completely storing the subband signals 164 of the detector 122 can also only every second, third, fourth subband signal in the data memory 170 be filed. For example, the frequency spacing between two adjacent subbands will be determined by the allowable error in the correlator of the detector. For processing in the decoder, a smaller frequency spacing may be sufficient, so that not all subbands are needed in the decoder, but only every second, third, etc.

Optionally, this can also be done in the time direction, so that only every second, third, fourth sample of the relevant subband signals is stored. This reduces the storage requirements. For example, the sampling rate F _DET in the detector is also determined by the allowable error in the correlator. It may be the case that F _DET is so high that for the transfer to the decoder a reduced sampling rate is sufficient.

In embodiments, the data memory 170 between detector 122 and decoders 124 Contain signals which the detection filter bank 162 were removed.

In embodiments, only every second, third, fourth subband signal and / or only every second, third, fourth sample of the subband signals can be stored in the signal ring memory in order to reduce the memory requirement.

In embodiments, the decoder 124 for decoding remove the symbols or part of the symbols (only every second, third, ... line of the FFT) from the filter bank, like the detector.

In embodiments, the subband signals may be the output signals of the DFT / FFT of the filter bank.

Separate filter banks for decoder and detector

This approach is exemplary in chapter 2.5 described. It represents the optimum of necessary computing power and memory requirements.

• • eine erste Polyphasen-Filterbank (CMFB) 162 oder andere Bandzerlegung zur Bereitstellung der Teilband-Signale 164 für den Paket-Detektor 122,
• • eine zweite Polyphasen-Filterbank (IMFB) 172 oder andere Bandzerlegung zur Vorzerlegung des Eingangssignals in Teilband-Signale 174 zur Minimierung des Rechenaufwands im Paket-Decoder 124,
• • optional eine Filterung der Signalabschnitte der Teil-Pakete 142 mittels schneller Faltung (Fast Convolution) in einem Block inklusive einer eventuell erforderlichen Unter- bzw. Überabtastung.

The system is characterized by:

• A first polyphase filter bank (CMFB) 162 or other band decomposition to provide the subband signals 164 for the packet detector 122 .
• A second polyphase filter bank (IMFB) 172 or other band decomposition for pre-dividing the input signal into subband signals 174 to minimize the computational effort in the packet decoder 124 .
• Optionally filtering the signal sections of the sub-packets 142 Fast convolution in one block, including any required under- or oversampling.

In embodiments, the decoder can extract the required signal detail from the associated subband signal with the aid of the detection parameters.

Synchronization with separate processing of detector and decoder

Typically, the detector and decoder terminate in processing one behind the other.

The detector assumes the task of detecting the telegrams and the decoder takes over the task of synchronizing the telegrams.

This leads to the restriction that only one telegram can be detected at the same time in parallel. However, in systems with relatively high frequency offsets compared to the data rate (e.g., by quartz tolerances or systematic offsets), it is possible for telegrams to be transmitted in parallel on multiple frequencies.

For this parallel detection to take place, the detection can investigate several frequency hypotheses.

Synchronization in the detector

The investigation of several frequency hypotheses and selection of those above the threshold corresponds to a frequency synchronization. Similarly, the detection in the time direction corresponds to a time synchronization.

Typically, the oversamples in the time and frequency directions are in the detector 122 lower than those in the subsequent decoder 124 , This can be increased for the combined detection and synchronization and / or using the adjacent channels / neighboring times interpolation be performed to increase the resolution of the synchronization.

In embodiments, the detector may be extended by the ability of synchronization.

In embodiments, the frequency and the time offset can be determined in a successful detection before the telegram is passed to the decoder.

Two-stage synchronization in the detector and decoder

The method described in the previous chapter has the disadvantage that as a rule a finer resolution of the detection in frequency and time direction is necessary and thus more computing power is required in the detector.

To avoid this problem and still be able to perform a parallel detection on several frequencies, a two-part synchronization is appropriate, as in 9 is shown.

In this case, the detection is carried out with the required resolutions in the time and frequency directions (coarse synchronization t _{PKT, C} / f _{PKT, C} ). If a detection occurs, the time and the frequency with the selected resolution will be sent to the decoder 124 to hand over. This uses these two parameters and performs the synchronization only within the remaining accuracies (fine synchronization t _{PKT, F} / f _{PKT, F} ).

Another advantage of this method is that the decoder 124 Due to the coarse synchronization less time and frequency hypotheses must be tested and thus the required computing power is lower.

In embodiments, the detector 122 the decoder 124 provide a coarse time and frequency offset (detection parameter).

In embodiments, the decoder 124 the fine synchronization based on the accuracy of the coarse synchronization of the detector 122 to calculate. The coarse frequency _offset f _{PKT, C} , in the synchronization in the detector 122 is compensated before the fine synchronization.

Different filters for the detector and decoder filter bank

By using two separate filter banks or by directly storing the wideband signal in the ring buffer, it is possible to use different filter characteristics.

Thus, instead of the matched filter (MF) in the detection, an approximation can be used which has a better stopband attenuation and thus improves the selection of the individual transmissions in the case of multichannel reception.

In the decoder 124 It may be advantageous to use a filter characteristic that improves the synchronization characteristics (eg with MSK RC or RRC filter instead of the MF).

In embodiments, different filter characteristics can be used in the filters or filter banks, which improve the functionality of the detector / decoder.

In embodiments, a filter bank IMFB employing an FFT or a DFT may be employed.

In embodiments, other methods of decomposing the wideband signal into subbands may also be used, e.g. Procedures that do not use FFT or DFT.

Further embodiments

16 shows a flowchart of a method 200 for receiving a wideband signal, the wideband signal comprising at least two sub-data packets distributed over different frequencies [eg frequency channels]. The procedure 200 includes a step 202 detecting the at least two sub-data packets in the wideband signal to provide at least one detection parameter for the detected sub-data packets. Furthermore, the method comprises 200 one step 204 decoding the detected sub-data packets using the detection parameters, wherein the detection and the decoding are performed or processed separately from each other.

17 shows a flowchart of a method 210 for receiving a wideband signal, the wideband signal comprising at least two sub-data packets distributed over different frequencies [eg frequency channels]. The procedure 210 includes a step 212 filtering the received wideband signal with a filter bank to divide the received wideband signal into a plurality of subband signals for [eg, subsequent] detection or decoding of the sub-data packets, the plurality of subband signals having different sub-bands of the wideband signal; wherein the filter bank comprises a polyphase filter.

Although some aspects have been described in the context of a device, it will be understood that these aspects also constitute a description of the corresponding method, so that a block or a component of a device is also to be understood as a corresponding method step or as a feature of a method step. Similarly, aspects described in connection with or as a method step also represent a description of a corresponding block or detail or feature of a corresponding device. Some or all of the method steps may by a hardware device (or using a hardware device), such as a microprocessor, a programmable computer, or an electronic circuit. In some embodiments, some or more of the most important method steps may be performed by such an apparatus.

Depending on particular implementation requirements, embodiments of the invention may be implemented in hardware or in software. The implementation may be performed using a digital storage medium, such as a floppy disk, a DVD, a Blu-ray Disc, a CD, a ROM, a PROM, an EPROM, an EEPROM or FLASH memory, a hard disk, or other magnetic disk or optical memory are stored on the electronically readable control signals that can cooperate with a programmable computer system or cooperate such that the respective method is performed. Therefore, the digital storage medium can be computer readable.

Thus, some embodiments according to the invention include a data carrier having electronically readable control signals capable of interacting with a programmable computer system such that one of the methods described herein is performed.

In general, embodiments of the present invention may be implemented as a computer program product having a program code, wherein the program code is operable to perform one of the methods when the computer program product runs on a computer.

The program code can also be stored, for example, on a machine-readable carrier.

Other embodiments include the computer program for performing any of the methods described herein, wherein the computer program is stored on a machine-readable medium.

In other words, an embodiment of the method according to the invention is thus a computer program which has a program code for performing one of the methods described herein when the computer program runs on a computer.

A further embodiment of the inventive method is thus a data carrier (or a digital storage medium or a computer-readable medium) on which the computer program is recorded for carrying out one of the methods described herein. The data carrier, the digital storage medium or the computer-readable medium are typically representational and / or non-transitory or non-transitory.

A further embodiment of the method according to the invention is thus a data stream or a sequence of signals, which represent the computer program for performing one of the methods described herein. The data stream or the sequence of signals may be configured, for example, to be transferred via a data communication connection, for example via the Internet.

Another embodiment includes a processing device, such as a computer or a programmable logic device, that is configured or adapted to perform one of the methods described herein.

Another embodiment includes a computer on which the computer program is installed to perform one of the methods described herein.

Another embodiment according to the invention comprises a device or system adapted to transmit a computer program for performing at least one of the methods described herein to a receiver. The transmission can be done for example electronically or optically. The receiver may be, for example, a computer, a mobile device, a storage device or a similar device. For example, the device or system may include a file server for transmitting the computer program to the recipient.

In some embodiments, a programmable logic device (eg, a field programmable gate array, an FPGA) may be used to perform some or all of the functionality of the methods described herein. In some embodiments, a field programmable gate array may cooperate with a microprocessor to perform one of the methods described herein. In general, in some embodiments, the methods are performed by any hardware device. This may be a universal hardware such as a computer processor (CPU) or hardware specific to the process, such as an ASIC.

The devices described herein may be implemented, for example, using a hardware device, or using a computer, or using a combination of a hardware device and a computer

The devices described herein, or any components of the devices described herein, may be implemented at least in part in hardware and / or software (computer program).

For example, the methods described herein may be implemented using a hardware device, or using a computer, or using a combination of a hardware device and a computer.

The methods described herein, or any components of the methods described herein, may be performed at least in part by hardware and / or by software.

The embodiments described above are merely illustrative of the principles of the present invention. It will be understood that modifications and variations of the arrangements and details described herein will be apparent to others of ordinary skill in the art. Therefore, it is intended that the invention be limited only by the scope of the appended claims and not by the specific details presented in the description and explanation of the embodiments herein.

Claims (15)

Data receiver (110), wherein the data receiver (110) is adapted to receive a wideband signal (120), the wideband signal comprising at least two sub-data packets (142) distributed in time and / or frequency, wherein the data receiver (110) comprises a filter bank (162,172) arranged to divide the received broadband signal into a plurality of subband signals (164,174) for detection or decoding of the sub-data packets (142), the plurality of subband signals (164,174 ) have different subbands of the wideband signal (120), wherein the filter bank (162, 172) comprises a polyphase filter; wherein the filter bank is a first filter bank (164) configured to divide the received wideband signal (120) into the plurality of subband signals (164) for the detection of the sub-data packets (142), wherein the data receiver (110) comprises a second filter bank (172) arranged to divide the received wideband signal (120) into a plurality of subband signals for the decoding of the sub data packets (142), the plurality of subband signals (174). have different subbands of the wideband signal (120), wherein the second filter bank (172) comprises a polyphase filter. The data receiver (110) of the preceding claim, wherein the filter bank (162, 172) comprises an N-point DFT or N-point FFT. A data receiver (110) according to any one of the preceding claims, wherein the filter bank (162, 172) comprises an N-channel mixer. A data receiver (110) according to any one of the preceding claims, wherein the filter bank (162, 172) is adapted to subsample the received wideband signal (120) so that a sample rate of the plurality of subband signals (164, 174) is less than a sample rate of the received wideband signal ( 120). The data receiver (110) of any one of the preceding claims, wherein the second filterbank (172) comprises an N-point DFT or N-point FFT. The data receiver (110) of any one of the preceding claims, wherein the second filter bank (172) is configured to subsample the received wideband signal (120) so that a sample rate of the plurality of subband signals (174) is less than a sample rate of the received wideband signal (120). A data receiver (110) as claimed in any one of the preceding claims, wherein the second filter bank (172) is arranged to divide the wideband signal (120) into a plurality of subband signals (174) having overlapping subbands, the subbands being at least a bandwidth of one of the sub-data packets (142) overlap. A data receiver (110) as claimed in any one of the preceding claims, wherein the second filter bank (172) is arranged to divide the wideband signal (120) into a plurality of subband signals (174) having overlapping subbands, wherein in dividing the wideband signal comprises a sum a bandwidth of a passband for one of the subband signals and a stopband bandwidth of a subband signal adjacent to the subband signal is not greater than a double sample rate of the plurality of subband signals. A data receiver (110) according to any one of the preceding claims, wherein a sampling rate f _IM (= M _IM * f _sym ) of the plurality of subband signals (174) provided by the second filter bank (172) for decoding the sub-data packets (142) is greater is a sample rate f _DET (= M _DET * f _sym ) of the plurality of subband signals (164) provided by the first filter bank (162) for the detection of the sub-data packets (142). A data receiver (110) according to any one of the preceding claims, wherein a number of subband signals N _IM of the subband signals (174) provided by the second filter bank (172) for decoding the sub data packets (142) is less than a number of subband signals N of subband signals (164) provided by the first filter bank (162) for the detection of the sub-data packets (142). The data receiver (110) of any one of the preceding claims, wherein the first filter bank (162) and the second filter bank (164) have different filter characteristics. The data receiver (110) of any one of the preceding claims, wherein the data receiver (110) comprises a detector (122) arranged to detect the at least two sub-data packets (142) in the different sub-bands of the plurality of sub-band signals (164) to provide detection parameters (126) for the detected sub-data packets. The data receiver (110) of any one of the preceding claims, wherein the data receiver (110) comprises a decoder (124) adapted to receive detected sub-data packets (142) using detection parameters (126) from the respective sub-band signals (174) extract. A method (210) for receiving a wideband signal, the wideband signal comprising at least two sub-data packets distributed over different frequencies Filtering (212) the received wideband signal with a first filter bank to divide the received wideband signal into a plurality of subband signals for detection of the sub data packets, the plurality of subband signals having different subbands of the wideband signal, wherein the first filter bank comprises a polyphase filter, Filtering the received wideband signal with a second filterbank to divide the received wideband signal into a plurality of subband signals for decoding the sub-data packets, the plurality of subband signals having different subbands of the wideband signal, wherein the second filter bank comprises a polyphase filter. Computer program for carrying out the method according to the preceding claim, when the computer program runs on a computer or microprocessor.

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