CN217085219U - Power output circuit of analog battery - Google Patents
Power output circuit of analog battery Download PDFInfo
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- CN217085219U CN217085219U CN202220578828.5U CN202220578828U CN217085219U CN 217085219 U CN217085219 U CN 217085219U CN 202220578828 U CN202220578828 U CN 202220578828U CN 217085219 U CN217085219 U CN 217085219U
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Abstract
The utility model relates to a simulation battery technical field leads to test quality and the technical problem of inefficiency because of there being burr interference in order to solve current simulation battery, the utility model discloses a power output circuit of simulation battery, including power output module and MCU, power output module includes discharge power adjusting tube and charge power adjusting tube, discharge power adjusting tube is linear power tube, and it has current detection resistance and current gear change over switch to establish ties on power output module's the output line, and the both ends of detecting current resistance are connected with the output current amplifier circuit who is used for feeding back current value to MCU, and MCU is connected with the current gear control circuit who is used for controlling current gear change over switch. The linear power tube is adopted to adjust the output, so that the burr interference generated by the output of the DC/DC switch of the analog battery can be effectively inhibited, the speed of dynamic response is improved, the clutter interference of output voltage is small, the voltage is pure and stable, and the quality and the efficiency of a test product of the analog battery are improved.
Description
Technical Field
The utility model relates to a simulation battery technical field especially relates to a power output circuit of simulation battery.
Background
With the use of a large number of lithium batteries and polymer batteries in consumer electronics, testing of the electronic products with real batteries affects testing efficiency, and simulated batteries are often used to replace the real batteries, which can also be referred to as battery simulators.
The existing analog battery DC/DC switch output generates burr interference, clutter exists, voltage is not pure enough, dynamic response speed is slow, and test quality and efficiency are low.
SUMMERY OF THE UTILITY MODEL
An object of the utility model is to provide a power output circuit of simulation battery to solve current simulation battery and lead to test quality and the technical problem of inefficiency because of there being burr interference.
In order to achieve the above object, the present invention provides a power output circuit of an analog battery, which comprises:
the utility model provides a power output circuit of simulation battery, includes power output module and the MCU that is used for control, power output module is including the discharge power adjusting tube that is used as external power supply and the power adjusting tube that charges that is used as load test, the discharge power adjusting tube is linear power pipe, and it has current detection resistance and current gear change over switch to establish ties on power output module's the output line, and the both ends of current detection resistance are connected with the output current amplifier circuit who is used for feeding back current value to MCU, and MCU is connected with the current gear control circuit who is used for controlling current gear change over switch. The power output circuit adopts the linear power tube to adjust the output, can effectively restrain the burr interference generated by the output of the DC/DC switch of the traditional analog battery, improves the speed of dynamic response, has small clutter interference of output voltage, has pure and stable voltage, and improves the quality and the efficiency of a test product of the analog battery.
Further, the discharge power adjusting tube comprises a switching tube Q15 and a switching tube Q16 controlled by the switching tube Q15, a controlled end of the switching tube Q16 is connected with an output end of a comparator U6, a non-inverting input end of the comparator U6 is connected with a second switching end of the switching tube Q15, a reference voltage is provided at an inverting input end of the comparator U6, the first switching ends of the switching tube Q15 and the switching tube Q16 are used for inputting voltage, and the second switching ends of the switching tube Q15 and the switching tube Q16 are used for outputting voltage. During discharging, the switch tube Q15 is firstly conducted, and then the switch tube Q16 is conducted, so that current impact caused by simultaneous conduction is avoided by time delay, and the quality of output voltage is improved.
Further, the charging power adjusting tube comprises a switching tube Q17 and a switching tube Q18 controlled by the switching tube Q17, a controlled end of the switching tube Q18 is connected with an output end of a comparator U7, a non-inverting input end of the comparator U7 is connected with a second switching end of the switching tube Q17, a reference voltage is provided at an inverting input end of the comparator U7, a first switching end of the switching tube Q17 and a first switching end of the switching tube Q18 are connected with a second switching end of the switching tube Q16, and a second switching end of the switching tube Q17 and the second switching end of the switching tube Q18 are grounded. During charging, the switch tube Q17 is turned on first, and the switch tube Q18 is turned on later, so that current impact caused by simultaneous conduction is avoided.
Furthermore, the current detection resistors comprise a first current detection resistor for detecting the magnitude of current in ampere level and a second current detection resistor for detecting current in milliampere level, a current gear selector switch is connected in parallel with the second current detection resistor, the current gear selector switch comprises a switch tube Q23 and a switch tube Q24, the source of the switch tube Q24 is the front stage of the current gear selector switch, the source of the switch tube Q23 is the rear stage of the current gear selector switch, the drain of the switch tube Q24 is connected with the source of the switch tube Q23, the source of the switch tube Q24 is connected with the drain of the switch tube Q23, and the gates of the switch tube Q23 and the switch tube Q24 are connected with the current gear control circuit.
Further, the output current amplifying circuit comprises an operational amplifier U9-A and an operational amplifier U9-B, the 1 st end of the first current detection resistor is respectively connected with the inverting input end of the operational amplifier U9-A and the non-inverting input end of the operational amplifier U9-B, and the 2 nd end of the first current detection resistor is respectively connected with the non-inverting input end of the operational amplifier U9-A and the inverting input end of the operational amplifier U9-B; the 1 st end of the second current detection resistor is respectively connected with the non-inverting input end of the operational amplifier U9-A and the inverting input end of the operational amplifier U9-B, and the 2 nd end of the second current detection resistor is connected with the non-inverting input end of the operational amplifier U9-A and the inverting input end of the operational amplifier U9-B through a diode D3 and a diode D4 which are connected in parallel in the reverse direction; therefore, current amplification is realized from different current directions, and the method can be applied to both discharge test and charge test.
Further, the sampling circuit further comprises a current signal ADC for improving the sampling precision, the current signal ADC is connected with the MCU, and the current signal ADC comprises a current safety gear ADC connected with the first current detection resistor and a current milliampere gear ADC connected with the second current detection resistor.
Furthermore, the sampling circuit further comprises a far-end sampling circuit, the problem of large current voltage drop on a line is solved, and the output end of the far-end sampling circuit is connected with a voltage signal ADC for improving sampling precision, so that the sampling precision is improved.
The output protection circuit is characterized in that the output protection switch comprises a switching tube Q19 and a switching tube Q20, the drain electrode of the switching tube Q19 is the front stage of the output protection switch, the source electrode of the switching tube Q19 is connected with the source electrode of the switching tube Q20, the drain electrode of the switching tube Q20 is the rear stage of the output protection switch, and the grid electrodes of the switching tube Q19 and the switching tube Q20 are connected with the output protection control circuit; the output protection control circuit comprises an optocoupler Q21 and an optocoupler Q22, an emitter of the optocoupler Q21 is connected with a source electrode of a switch tube Q19, a collector of the optocoupler Q21 is connected with a switch tube Q19 and a grid electrode of the switch tube Q20 respectively, an emitter of the optocoupler Q22 is connected with a collector of the optocoupler Q21 through a resistor R37, and a collector of the optocoupler Q22 is provided with a first voltage; the negative pole of opto-coupler Q22 ground connection, the negative pole of opto-coupler Q22 through two series connection resistance R35, resistance R36 and opto-coupler Q21 is connected, and opto-coupler Q21's positive pole is provided with the second voltage, and resistance R35 and resistance R36's middle node is connected with MCU. Thereby, output protection is formed.
Further, still include the voltage circuit of transferring files, the voltage circuit of transferring files is equipped with comparator U10, the homophase input end of comparator U10 obtains the partial pressure from the third direct current through resistance bleeder circuit, comparator U10's inverting input end is equipped with reference voltage, comparator U10's output is connected with opto-coupler Q33's positive pole through resistance R51, opto-coupler Q33's negative pole is ground even, opto-coupler Q33's collecting electrode is connected with the resonance control of the synchronous follow unit of output, opto-coupler Q33's emitter ground connection.
Further, the device also comprises a communication circuit for communicating with the outside.
The utility model provides a pair of power output circuit of simulation battery has following advantage:
the power output circuit adopts the linear power tube to adjust the output, can effectively restrain the burr interference generated by the output of the DC/DC switch of the traditional analog battery, improves the speed of dynamic response, has small clutter interference of output voltage, has pure and stable voltage, and improves the quality and the efficiency of a test product of the analog battery. In addition, the current impact caused by simultaneous conduction is avoided by adopting time delay, and the quality of output voltage is improved; the current amplification can be respectively carried out from different current directions, and the method can be applied to both discharge test and charge test; the ADC improves the sampling precision; the far-end sampling circuit solves the problem of large current drop on the line.
Drawings
Fig. 1 is a block diagram of a high-power analog battery system provided by the present invention;
fig. 2 is a functional block diagram of a power factor correction circuit provided by the present invention;
fig. 3 is a schematic diagram of a circuit structure of a power factor correction circuit provided by the present invention;
FIG. 4 is a functional diagram of an output synchronous follower circuit provided by the present invention;
FIG. 5 is a structural diagram of an output synchronous follower circuit provided by the present invention;
fig. 6 is a schematic structural diagram of a driving circuit of the resonant controller provided by the present invention;
fig. 7 is a circuit structure diagram of the resonant controller LCC provided by the present invention;
fig. 8 is a functional block diagram of a power output circuit provided by the present invention;
fig. 9 is a schematic structural diagram of a power output module provided by the present invention;
fig. 10 is a schematic diagram of the ADC, DAC and voltage measurement circuit structure provided by the present invention;
fig. 11 is a structural diagram of a charging and discharging power circuit provided by the present invention;
fig. 12 is a structural diagram of an output protection switch and an output protection control circuit provided by the present invention;
fig. 13 is a structural diagram of the current detecting circuit, the current gear selector switch and the current gear control circuit provided by the present invention;
fig. 14 is a schematic diagram of a differential pressure and optical coupling control circuit structure provided by the present invention;
fig. 15 is a schematic diagram of a voltage shift and optical coupling control circuit structure provided by the present invention.
In the figure: VCC1, first direct current; VCC2, second direct current; VCC3, third direct current; VCC4, fourth direct current; VCC5, fifth dc; VO, terminal direct current.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more clearly understood, the present invention is further described in detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and are not intended to limit the invention.
In the present application, the term "switching tube" refers to a general term for MOS, triode, IGBT, etc., and in the embodiments, the term "switching tube" is usually used to refer to an NMOS tube as an example, thereby defining a drain as its first switch terminal, a source as its second switch terminal, and a gate as its controlled terminal.
Referring to fig. 1 to 15, the present invention provides a high power analog battery, which includes a power factor correction circuit, an output synchronous follower circuit and a power output circuit. The power factor correction circuit is used for converting input commercial alternating current into high-voltage first direct current VCC1, correcting the power factor of the commercial alternating current, improving the power factor and reducing reactive current; the output synchronous following circuit acquires a first direct current VCC1 from the power factor correction circuit and outputs a third direct current VCC3 of 2-52V; the power output circuit acquires a third direct current VCC3, outputs a tail end direct current VO, and feeds back the tail end direct current VO to the output synchronous following circuit, so that the output synchronous following circuit adjusts the pressure difference of the adjusting tube in the power output circuit or fixes the voltage during operation, the constant voltage is always maintained, the power consumption of the power adjusting tube is reduced, the stability of the high-power simulation battery system is improved, the test requirement of current battery capacity increase is met, the heat productivity is reduced, the heat dissipation of elements and the optimization of a radiator are facilitated, the volume and the quality of the high-power simulation battery are reduced, and the high-power simulation battery is lighter and more portable.
Inductive load or capacitive load make the power factor of electric wire netting be less than 1, and the capacity of power supply unit has been wasted to the power factor of undersize, the utility model provides a power factor correction circuit corrects to power factor.
Referring to fig. 3, the power factor correction circuit includes a PFC module, where the PFC module includes a first common mode inductor for being electrically connected to a commercial ac, a second common mode inductor connected to the first common mode inductor, and a rectifier module connected to the second common mode inductor, a positive electrode of the rectifier module is connected to a coil L1A, an output end of the coil L1A is connected to a drain of a switching tube Q1, a source of the switching tube Q1 is grounded, a gate of the switching tube Q1 is connected to a driving end of a power factor controller, the switching tube Q1, the coil L1A, a capacitor C1, and the power factor controller constitute a power factor correction circuit, when the switching tube Q1 is turned on, a current flows through the coil L1A, the current linearly increases before the coil L1A is not saturated, electric energy is stored in the coil L1A in the form of magnetic energy, and at this time, the capacitor C1 discharges to provide energy for a load at a later stage; when the switching tube Q1 is turned off, a self-induced electromotive force is generated across the coil L1A to keep the current direction unchanged. Thus, the self-induced electromotive force is connected in series with the power supply output from the rectifier module to supply power to the capacitor C1 and the load.
Preferably, the switching tube Q1 is an NMOS tube.
The beneficial effects brought by the method are as follows: the input current is completely continuous and can be modulated in the sine period of the whole input voltage, so that a high power factor can be obtained; the current of the coil L1A is the input current, and is easy to adjust; the grid driving signal ground and the output of the switching tube Q1 are connected with the ground in common, and the driving is simple; the input current is continuous, the current peak value of the switching tube Q1 is small, the adaptability to the input voltage change is strong, and even the commercial power voltage change is large.
Referring to fig. 2, the pfc circuit includes an auxiliary power supply for generating a second dc voltage VCC2 at a low voltage to supply power to the pfc circuit.
In order to avoid surge current generated in the moment of starting up, a power type thermistor is connected in series in an alternating current circuit at the front stage of the rectifier module and is specifically arranged between a first common mode inductor and a second common mode inductor, the thermistor is a thermistor with a negative temperature coefficient, the resistance value of the thermistor is reduced along with the temperature increase, when the load is too heavy, the current flowing through the thermistor is increased, the temperature of the current is increased, in order to prevent the thermistor from being burnt out due to too high temperature, a first voltage feedback circuit is further arranged and is used for collecting the voltage of a first direct current VCC1, the output end of the first voltage feedback circuit is connected with a switching tube Q2 which is connected with the base of a switching tube Q2, the emitter of the switching tube Q2 is grounded, the thermistor is connected in parallel with a relay, two normally open contacts of the relay are connected with two ends of the thermistor, and two ends of a coil of the relay are respectively connected with a low-voltage direct current VCC2, The collector of switch tube Q2 is connected, goes to the opening and shutting of control relay through switch tube Q2, and when the electric current of output was too high, the switch in the relay was closed, with the thermistor short circuit, has avoided thermistor to be burnt out.
Preferably, the switching transistor Q2 is an NPN-type transistor.
In one embodiment, a typical value for high voltage dc VCC1 is 390V, and a typical value for low voltage dc VCC2 is 12V.
Referring to fig. 4, the output synchronous follower circuit includes an input port connected to an output port of the power factor correction circuit, and acquires a first dc VCC1 and a second dc VCC2 from the power factor correction circuit, and a control input port connected to the power output circuit, and is configured to provide a 12V power and a control signal, and finally output a third dc VCC3 to the power output circuit.
Referring to fig. 5, the output synchronous follower circuit includes a primary auxiliary power supply and a secondary auxiliary power supply, and the primary auxiliary power supply converts the second dc VCC2 into a fourth dc VCC4 to supply power to the resonant controller; the 12V of the control input port supplies power to the secondary auxiliary power supply, the secondary auxiliary power supply converts the voltage into fifth direct current VCC5 and 2.5V voltage to supply power to the voltage and current feedback circuit, and the control signal is used for the optical coupler control circuit.
Referring to fig. 6, the output synchronous follower circuit includes a resonant controller for outputting a 50% duty cycle, at the same time, high-side and low-side 180-degree phase inversion. The resonance controller is connected with a first direct current VCC1 and a fourth direct current VCC4, outputs a voltage driving signal SQH, and comprises a plurality of controlled ends controlled by an optical coupling control circuit, and the optical coupling control circuit is connected with the controlled ends; the high-end suspended gate driving output pin of the resonant controller is connected with the base electrode of a PNP type triode Q8, the low-end gate driving output pin of the resonant controller is connected with the base electrode of a PNP type triode Q7, the emitter electrode of the triode Q8 is connected with the gate electrode of a switching tube Q4, and the drain electrode of the switching tube Q4 is connected with a first direct current VCC 1; an emitter of the triode Q7 is connected with a gate of the switching tube Q6, a drain of the switching tube Q6 is connected with a source of the switching tube Q4, a source of the switching tube Q4 is grounded, and a collector of the triode Q7 is grounded; the floating ground pin of the high-side gate drive of the resonant controller is respectively connected with the collector of the triode Q8 and the source of the switching tube Q4, and the first direct current VCC1 is modulated by the circuit to generate a voltage drive signal SQH.
Referring to fig. 7, a voltage driving signal SQH is input to an LCC circuit, the LCC circuit includes a synchronous rectification controller U8, a voltage driving signal SQH is input to a transformer T3B, the transformer T3B has a primary side coil LR3, a secondary side coil T3D with a center tap, and a transformer T3E, one end of the primary side coil LR3 is connected to the voltage driving signal SQH, the other end of the primary side coil LR3 is grounded through an X capacitor CR3, and the X capacitor CR3 is used for eliminating differential mode interference; the two ends of the secondary side coil are respectively connected with the drain electrode of the switching tube Q13 and the drain electrode of the switching tube Q14, and the center tap is used for outputting third direct current VCC3 with the output of 2-52V.
A first drain end of the synchronous rectification controller U8 is connected with a drain electrode of the switching tube Q14, a first gate end is connected with a gate electrode of the switching tube Q14, and a first source end is connected with a source electrode of the switching tube Q14; the second drain terminal of the synchronous rectification controller U8 is connected to the drain of the switching transistor Q13, the second gate terminal is connected to the gate of the switching transistor Q13, and the second source terminal is connected to the source of the switching transistor Q13.
The LCC circuit also includes a primary side current sampling circuit that samples the current on the primary side of transformer T3B for feedback to the resonant controller. The primary side current sampling circuit comprises a resistor R68 connected with the other end of the primary side coil LR3, the resistor R68 is connected with the middle node of a switch diode D5 used for suppressing conducted interference through a series capacitor C6, a switch diode D5 comprises two end-to-end connected diodes, the anode of the switch diode D5 is grounded, and the cathode of the switch diode D5 is connected with a current detection signal input end of the resonance controller through a CS line.
Furthermore, the cathode of the switching diode D5 is also connected to a resistance-capacitance filter circuit, which is grounded through a resistor R75, a capacitor R79 and a capacitor C21, and the resistor R75, the capacitor R79 and the capacitor C21 connected in parallel form the resistance-capacitance filter circuit.
The LCC circuit comprises a plurality of same circuits, and the LCC circuits are connected in parallel, so that the output power and the output stability are increased.
Referring to fig. 5, voltage current feedback circuit includes voltage feedback circuit and current feedback circuit, the opto-coupler control circuit includes first opto-coupler, second opto-coupler and third opto-coupler, control input port passes through the first opto-coupler of PS _ ON line control, secondary auxiliary power supply provides the power supply of 2.5V for voltage feedback circuit, control input port passes through third direct current VCC3 and terminal direct current VO control second opto-coupler, the output of second opto-coupler and third opto-coupler is parallelly connected, the output of third opto-coupler respectively with resonant controller's intermittent type operating mode threshold pin, lowest oscillation frequency sets up the pin and connects.
The voltage feedback circuit detects the voltage value of the third direct current VCC3, the primary auxiliary power supply is controlled through the first optical coupler, the primary auxiliary power supply outputs or turns off the fourth direct current VCC4, and when the third direct current VCC3 is detected to be overvoltage, the primary auxiliary power supply turns off the output, so that the overvoltage protection effect is realized.
The current detection circuit detects the current value of the third direct current VCC3, and the current value is fed back to the resonance controller through the third optical coupler, so that the resonance controller can work or stand by, and intermittent work is realized.
Referring to fig. 8, the power output circuit includes a power output module, an MCU, an ADC, a DAC, a communication circuit, a power control interface, and a voltage measurement circuit, wherein the MCU is used for overall system control of the power output module; the ADC is used for converting analog signals into digital signals; DCA is used for digital to analog signal conversion; the communication circuit is used for the MCU to communicate with the outside; the power supply control interface is used for providing a control signal; the voltage measuring circuit is used for measuring the voltage output by the power output module; the control input port acts as a shared interface, is connected with the power output circuit and the output synchronous follower circuit, and is used for providing voltage and control signals, including control signals Ct1_ Up and Ct1_ Down and the like.
The power output module can be used for discharging and charging, wherein discharging refers to that the power output module supplies voltage to the outside to supply external electric equipment to work; the charging means that the power output circuit consumes electric energy as a load and is used for completing the charging function test of a tested product.
Referring to fig. 9, the power Output module includes a discharge power adjusting tube located at the upper portion and a charge power adjusting tube located at the lower portion, a power input end of the discharge power adjusting tube is used for connecting a third direct current VCC3 of the Output synchronous follower circuit, and is controlled by a Ct1_ Up signal line, so that the discharge power adjusting tube performs a switching operation according to a predetermined frequency, an Output _ V line obtains a voltage, and a final Output terminal direct current VO is provided to an external power consumption device.
When charging, external voltage is introduced into an Output _ V circuit of the power Output module and is controlled by a Ct1_ Down signal circuit, so that the charging power adjusting tube performs switching action according to a preset frequency, and the charging power adjusting tube consumes electric energy, thereby completing the charging test of a tested product.
Specifically, as shown in fig. 11, the discharge power adjusting transistor includes a switching transistor Q15, a drain of the switching transistor Q15 is used for inputting a third direct current VCC3, a source of the switching transistor Q15 is connected to an Output _ V line through a resistor R19, a gate of the switching transistor Q15 is connected to a Ct1_ Up signal line, when the Ct1_ Up signal line is at a high level, the switching transistor Q15 is turned on, and the third direct current VCC3 falls into the Output _ V line, so that the third direct current VCC3 is discharged to the outside.
Furthermore, in order to improve the Output power and the Output stability, the power converter further comprises a switching tube Q16 controlled by the switching tube Q15 after being turned on, a drain of the switching tube Q16 is used for inputting a third direct current VCC3, a source of the switching tube Q16 is connected with an Output _ V line through a resistor R32, a gate of the switching tube Q16 is connected with an Output end of a comparator U6, an inverting input end of the comparator U6 obtains a reference voltage from the line Clt _ VCC through a resistor R26, a non-inverting input end of the comparator U6 is connected with a source of the switching tube Q15, a positive electrode of the comparator U6 is connected with the line Clt _ VCC, and a negative electrode of the comparator U6 is connected with the Output _ V line. When the switching tube Q15 is turned on, the comparator U6 outputs a high level to turn on the switching tube Q16, and the path of the third dc VCC3 loaded to the Output _ V line is increased. The resistors R19 and R32 are extremely small in resistance and can carry a large current, and are preferably alloy resistors.
During discharging, the switching tube Q15 is firstly conducted, and the switching tube Q16 is then conducted, so that current impact caused by simultaneous conduction is avoided by time delay, and in addition, the switching tube Q16 can be independently controlled through Ctl _ VCC to control the number of the conducting switching tubes and control the output power; the switch tube Q15 and the switch tube Q16 are power tubes with linear adjustment, and output voltage quality is improved.
More combined circuits of the switching tube Q16 and the comparator U6 can be provided, and the path of the third direct current VCC3 loaded to the Output _ V line is further increased, so that the Output current is improved, the stability of the Output is enhanced, and the Output power is increased.
The charging power adjusting tube comprises a switch tube Q17, the drain of the switch tube Q17 is used for inputting the voltage of an Output _ V line, namely, when a tested product is tested and charged, the power supply voltage of the tested product is on the Output _ V line, the source of the switch tube Q17 is connected with a ground wire GND through a resistor R27, the gate of the switch tube Q17 is connected with a Ct1_ Down signal line, when the Ct1_ Down signal line is in a high level, the switch tube Q17 is conducted, the power supply of the tested product falls into the ground wire GND, and therefore electric energy is consumed.
Furthermore, in order to improve the load capacity, the load-tolerant power supply further comprises a switching tube Q18 controlled by the conducted switching tube Q17, the drain of the switching tube Q18 is used for inputting the voltage of an Output _ V line, the source of the switching tube Q18 is connected with a ground line GND through a resistor R33, the grid of the switching tube Q18 is connected with the Output end of a comparator U7, the inverting input end of the comparator U7 obtains a reference voltage from a 12V power supply through a resistor R31, the non-inverting input end of the comparator U7 is connected with the source of the switching tube Q17, the positive end of the comparator U7 is provided with the 12V voltage, and the negative end of the comparator U7 is connected with the ground line GND. When the switching tube Q17 is turned on, the comparator U7 outputs a high level to turn on the switching tube Q18, and the path for the voltage of the Output _ V line to be applied to the ground GND increases. The resistors R27 and R33 are extremely small in resistance and can carry a large current, and are preferably alloy resistors.
More combined circuits of the switching tube Q18 and the comparator U7 can be adopted, the voltage of the Output _ V line is loaded to the ground line GND, the load capacity is improved, the stability of the load is enhanced, and the load power is increased.
The switch tube Q15, the switch tube Q16, the switch tube Q17 and the switch tube Q18 are preferably linear power NMOS tubes, so that the glitch interference generated by the output of the conventional analog battery DC/DC switch can be effectively inhibited, the speed of dynamic response is improved, the output voltage clutter interference is small, the voltage is pure and stable, and the quality and the efficiency of a test product of the analog battery are improved; the average current is changed by changing the duty ratio through a Ct1_ Up signal line and a Ct1_ Down signal line so as to change the time length of the output current.
Referring to fig. 9, a current detection resistor is connected in series to the ground GND, and the output current amplification circuit collects the voltage across the current detection resistor and sends the voltage to the MCU. The current detection resistor comprises a first current detection resistor for detecting the magnitude of current in an ampere level and a second current detection resistor for detecting current in a milliampere level.
A current gear selector switch is further arranged on the ground wire GND and connected in parallel with a second current detection resistor, the MCU controls the current gear selector switch through a current gear control circuit, when the current gear selector switch is switched off, the current in the circuit is small, the second current detection resistor plays a main role, and the current detection is more accurate; when the current gear shifting switch is closed, a larger current can flow through the circuit, the second current detection resistor is short-circuited, and the second current detection resistor does not work; and selecting the current gear selector switch to be switched off or switched on according to different application scenes.
The current gear change-over switch can be switched automatically or manually, and is preferably automatically switched under the control of an MCU (microprogrammed control Unit), the current condition detected by the output current amplifying circuit is used as a judgment basis in automatic, and the current gear change is automatically switched to a small current gear when the current is reduced to a preset value, so that the voltage change of charging and discharging of a battery in a certain time period is simulated, the current measurement is more accurate, and the static current and the power consumption of a test product are very convenient; when manual, can go through control panel to set up, go to adjust according to user's demand.
Specifically, referring to fig. 13, a resistor R41 is a first current detection resistor, a resistor R40 is a second current detection resistor, a switching tube Q23 and a switching tube Q24 form a current step switching switch, and a transistor Q26 and a transistor Q27, a resistor R38 and a resistor R39 form a current step control circuit.
It can be understood that, in order to increase the output current in the circuit and increase the output power, a plurality of switching tubes may be arranged in parallel with the switching tube Q23 and the switching tube Q24, respectively.
Preferably, the switching tube Q23 and the switching tube Q24 are NMOS tubes.
Further, a capacitor C11 is connected in parallel between the drain and the source of the switching tube Q23 for reducing switching spikes and reducing electromagnetic radiation.
When the MCU generates a low level through the port A/mA, the triode Q26 is cut off, the base electrode of the triode Q27 obtains voltage through the pull-up resistor R38, the triode Q27 is conducted, the grid electrodes of the switch tube Q23 and the switch tube Q24 obtain starting voltage and are conducted, namely, the current gear change switch is closed, the second current detection resistor is short-circuited, large current can flow through the circuit, and ampere-level current in the first current detection resistor detection circuit is fed back to the MCU through the output current amplification circuit.
When the MCU generates a high level through the port A/mA, the triode Q26 is conducted, the base electrode of the triode Q27 is grounded, the triode Q27 is cut off, the grid electrodes of the switch tube Q23 and the switch tube Q24 lose opening voltage and are cut off, namely, the current gear change switch is switched off, the current flows through the second current detection resistor, a small current flows through the circuit, and the second current detection resistor detects a milliampere-level current in the circuit and feeds the milliampere-level current back to the MCU through the output current amplifying circuit.
In order to detect the current during charging and discharging respectively, the output current amplifying circuit comprises an operational amplifier U9-A and an operational amplifier U9-B, the 1 st end of a first current detection resistor (R41) is connected with the inverting input end of the operational amplifier U9-A and the non-inverting input end of the operational amplifier U9-B respectively, and the 2 nd end of a first current detection resistor (R41) is connected with the non-inverting input end of the operational amplifier U9-A and the inverting input end of the operational amplifier U9-B respectively; the 1 st end of a second current detection resistor (R40) is respectively connected with the non-inverting input end of the operational amplifier U9-A and the inverting input end of the operational amplifier U9-B, and the 2 nd end of the second current detection resistor (R40) is connected with the non-inverting input end of the operational amplifier U9-A and the inverting input end of the operational amplifier U9-B through a diode D3 and a diode D4 which are connected in parallel in an opposite direction; this allows current amplification from different current directions.
Referring to fig. 9, an output protection switch is further disposed on the ground GND, and the MCU controls the output protection switch through the output protection control circuit according to the current condition detected by the output current amplifying circuit, and turns off the output protection switch when the current exceeds a threshold.
Referring to fig. 12, the output protection switch includes a switching tube Q19 and a switching tube Q20, a drain of the switching tube Q19 is connected to a line at the front end of the protection, a source of the switching tube Q19 is connected to a source of the switching tube Q20, a drain of the switching tube Q20 is an output line at the rear end of the protection, and gates of the switching tube Q19 and the switching tube Q20 are connected to an output protection control circuit.
The output protection control circuit comprises an optocoupler Q21 and an optocoupler Q22, an emitter of the optocoupler Q21 is connected with a source electrode of a switching tube Q19, a collector of the optocoupler Q21 is connected with a switching tube Q19 and a grid electrode of the switching tube Q20 respectively, an emitter of the optocoupler Q22 is connected with a collector of the optocoupler Q21 through a resistor R37, and a collector of the optocoupler Q22 is provided with 12V voltage; the negative pole of the optical coupler Q22 is grounded, the negative pole of the optical coupler Q22 is connected with the negative pole of the optical coupler Q21 through the resistor R35 and the resistor R36 which are connected in series, the positive pole of the optical coupler Q21 is provided with 3.3V voltage, and the middle junction of the resistor R35 and the resistor R36 is connected with the port OUT of the MCU.
MCU produces high-low level through its port OUT, makes opto-coupler Q21 and opto-coupler Q22 work in turn, and when opto-coupler Q21 during operation, the inside triode of opto-coupler Q21 switches on for switch tube Q19 and switch tube Q20's V GS Is 0, V GS <V TH The switch tube Q19 and the switch tube Q20 are cut offNamely, the output protection switch is turned off, so that the protection function is realized; when the optocoupler Q22 works, the internal triode of the optocoupler Q22 is conducted, so that the grids of the switching tube Q19 and the switching tube Q20 acquire voltage V GS >V TH The switching tube Q19 and the switching tube Q20 are turned on, that is, the output protection switch is closed, so as to form a path.
Furthermore, a plurality of switching tubes may be respectively connected in parallel with the switching tube Q19 and the switching tube Q20 to increase the output current and the output power.
It is understood that the current detection resistor, the current step switch and the Output protection switch can also be arranged on the Output _ V line.
As shown in fig. 9, a conventional analog battery is directly connected to an output current amplifying circuit by using an MCU, and thus the MCU directly samples an analog signal, which has the advantage of high response speed, and is limited by the characteristics of the MCU itself, resulting in low display precision.
As shown in fig. 10, in order to provide the accuracy of current display, a current signal ADC for converting a current analog quantity into a digital quantity is provided, an input end of the current signal ADC is connected to both ends of a current detection resistor, an output end of the current signal ADC is connected to an MCU, and a sampling number is sent to the MCU via the separate high-accuracy current signal ADC, so that the sampling accuracy can be improved.
Further, the current signal ADC includes a current safety gear ADC and a current milliampere gear ADC, and input ends of the current safety gear ADC and the current milliampere gear ADC are respectively connected to two ends of the first current detection resistor and the second current detection resistor.
The voltage measuring circuit comprises a local output sampling circuit and a remote output sampling circuit, and the local output sampling circuit is used for adopting the output voltage of a local port; because the power transmission line has the overlength condition when the product to be measured uses, cause and have the pressure drop on the power transmission line, the voltage that shows does not represent the true voltage value that the product to be measured obtained, still is equipped with far-end output sampling circuit for this reason, uses the far-end sampling to solve the heavy current pressure drop problem.
Furthermore, in order to improve the accuracy of voltage measurement, the voltage measurement device also comprises a voltage signal ADC, so that the sampling is more accurate and the display is more accurate.
Parameters controlled by the display screen or data set by parameters of an external upper computer, an ATE test cabinet and the like are sent to the MCU by the communication circuit, processed by the MCU, converted by the DAC and sent to the power output module, and then output voltage is controlled.
Preferably, the communication circuit is an RS485 communication circuit.
Referring to fig. 14, in order to solve the problem of the voltage difference of the discharge power adjusting tube in the power output module, the optocoupler control circuit obtains a third direct current VCC3 and a terminal direct current VO from the power output circuit, respectively, because the discharge power adjusting tube has a voltage difference, the voltage of the terminal direct current VO will be lower than the third direct current VCC3, when the voltage difference between the two is lower than a threshold, the second optocoupler (Q30) works, the triode in the second optocoupler (Q30) is turned on to pull down the relevant power pin of the resonant controller, so as to cause the resonant controller to adjust the output frequency, and further change the third direct current VCC3 and the terminal direct current VO, that is, when the output synchronous follower circuit adjusts or works with a fixed voltage along with the voltage difference of the adjusting tube in the power output circuit, the output synchronous follower circuit is always maintained at a fixed voltage, thereby reducing the power consumption of the power adjusting tube itself, improving the working stability of the high-power analog battery system, and satisfying the current test requirement of increasing the battery capacity, the heat productivity is reduced, the heat dissipation of elements and the optimization of a radiator are facilitated, the size and the mass of the high-power simulation battery are reduced, and the high-power simulation battery is lighter and more convenient to carry.
In addition, referring to fig. 15, the voltage shift circuit obtains a third direct current VCC3 from the power output circuit, and the third direct current VCC is fed back to the resonant controller through the comparator U10 and the optocoupler Q33, so as to adjust the oscillation frequency of the resonant controller, thereby implementing voltage shift. The non-inverting input end of the comparator U10 obtains voltage division from a third direct current VCC3 through a resistor voltage division circuit formed by a resistor R49 and a resistor R50, the inverting input end of the comparator U10 is provided with reference voltage, the output end of the comparator U10 is connected with the anode of an optocoupler Q33 through the resistor R51, the cathode of the optocoupler Q33 is connected with the ground, the collector of the optocoupler Q33 is connected with the resonance control of the output synchronous following circuit, and the emitter of the optocoupler Q33 is grounded.
To sum up, the utility model provides a high-power simulation battery improves to prior art's shortcoming, and the synchronous follow circuit's of output resonance controller output voltage drive signal waveform gives the LCC circuit and is used for power conversion, through the LCC circuit transform, provides voltage for the output, and the voltage and the current signal of output give voltage current feedback circuit, and voltage current feedback signal passes through opto-coupler control circuit, transmits the feedback end to resonance controller to the voltage and the current output of control power; the output voltage signal of the power output circuit is input to the optical coupling control circuit to control the voltage of the output synchronous following circuit to follow the output voltage of the whole high-power analog battery. The front-stage power supply adopts an adjustable LCC switching power supply, so that the volume of a high-power instrument can be reduced in a large range, and the mass of the instrument can be reduced; the adjustable voltage range of the output of the analog battery can be enlarged through voltage following adjustment; the power output of the analog battery adopts a power tube with linear regulation, so that the quality of output voltage is improved.
The above description is only exemplary of the present invention and should not be taken as limiting the scope of the present invention, as any modifications, equivalents, improvements and the like made within the spirit and principles of the present invention are intended to be included within the scope of the present invention.
Claims (10)
1. The utility model provides a power output circuit of simulation battery, includes power output module and the MCU that is used for control, its characterized in that, power output module is including the discharge power adjusting tube that is used as external power supply and the charge power adjusting tube that is used as load test, the discharge power adjusting tube is linear power pipe, it has current detection resistance and current gear change over switch to establish ties on power output module's the output line, the both ends of detecting the current resistance are connected with the output current amplifier circuit who is used for feeding back current value to MCU, MCU is connected with the current gear control circuit who is used for controlling current gear change over switch.
2. The power output circuit simulating the battery as claimed in claim 1, wherein the discharging power adjusting tube comprises a switch tube Q15, and further comprises a switch tube Q16 controlled by a switch tube Q15, the controlled end of the switch tube Q16 is connected with the output end of a comparator U6, the non-inverting input end of the comparator U6 is connected with the second switch end of the switch tube Q15, the inverting input end of the comparator U6 is provided with a reference voltage, the first switch ends of the switch tube Q15 and the switch tube Q16 are used for inputting voltage, the second switch ends of the switch tube Q15 and the switch tube Q16 are used for outputting voltage, and the discharging power adjusting tube is a linear adjusting power tube.
3. The power output circuit of the analog battery as claimed in claim 2, wherein the charging power adjusting transistor comprises a switching transistor Q17, and further comprises a switching transistor Q18 controlled by a switching transistor Q17, the controlled terminal of the switching transistor Q18 is connected to the output terminal of a comparator U7, the non-inverting input terminal of the comparator U7 is connected to the second switching terminal of the switching transistor Q17, the inverting input terminal of the comparator U7 is provided with a reference voltage, the first switching terminals of the switching transistor Q17 and the switching transistor Q18 are connected to the second switching terminal of the switching transistor Q16, and the second switching terminals of the switching transistor Q17 and the switching transistor Q18 are grounded.
4. The power output circuit of the analog battery as claimed in claim 1, wherein the current detecting resistors include a first current detecting resistor for detecting the magnitude of current in ampere level, a second current detecting resistor for detecting current in milliampere level, the current step switch is connected in parallel with the second current detecting resistor, the current step switch includes a switch tube Q23 and a switch tube Q24, the source of the switch tube Q24 is the front stage of the current step switch, the source of the switch tube Q23 is the rear stage of the current step switch, the drain of the switch tube Q24 is connected with the source of the switch tube Q23, the source of the switch tube Q24 is connected with the drain of the switch tube Q23, and the gates of the switch tube Q23 and the switch tube Q24 are connected with the current step control circuit.
5. The power output circuit of the analog battery as claimed in claim 4, wherein the output current amplifying circuit comprises an operational amplifier U9-A and an operational amplifier U9-B, the 1 st end of the first current detecting resistor is connected with the inverting input terminal of the operational amplifier U9-A and the non-inverting input terminal of the operational amplifier U9-B, and the 2 nd end of the first current detecting resistor is connected with the non-inverting input terminal of the operational amplifier U9-A and the inverting input terminal of the operational amplifier U9-B; the 1 st end of the second current detection resistor is respectively connected with the non-inverting input end of the operational amplifier U9-A and the inverting input end of the operational amplifier U9-B, and the 2 nd end of the second current detection resistor is connected with the non-inverting input end of the operational amplifier U9-A and the inverting input end of the operational amplifier U9-B through a diode D3 and a diode D4 which are connected in parallel in an opposite direction.
6. The power output circuit of the analog battery according to claim 4, further comprising a current signal ADC for improving sampling accuracy, wherein the current signal ADC is connected with the MCU, and the current signal ADC comprises a current safety gear ADC connected with the first current detection resistor and a current milliampere gear ADC connected with the second current detection resistor.
7. The power output circuit of the analog battery as claimed in claim 4, further comprising a far-end sampling circuit, wherein the output end of the far-end sampling circuit is further connected with a voltage signal ADC for improving sampling precision.
8. The power output circuit simulating the battery according to claim 1, comprising an output protection switch disposed on the output line, the output protection switch being controlled to be connected with an output protection control circuit, wherein the output protection switch comprises a switching tube Q19 and a switching tube Q20, a drain of the switching tube Q19 is a front stage of the output protection switch, a source of the switching tube Q19 is connected with a source of the switching tube Q20, a drain of the switching tube Q20 is a rear stage of the output protection switch, and gates of the switching tube Q19 and the switching tube Q20 are connected with the output protection control circuit; the output protection control circuit comprises an optocoupler Q21 and an optocoupler Q22, an emitter of the optocoupler Q21 is connected with a source electrode of a switch tube Q19, a collector of the optocoupler Q21 is connected with a grid electrode of a switch tube Q19 and a grid electrode of the switch tube Q20 respectively, an emitter of the optocoupler Q22 is connected with a collector of the optocoupler Q21 through a resistor R37, and a collector of the optocoupler Q22 is provided with a first voltage; the negative pole of opto-coupler Q22 ground connection, the negative pole of opto-coupler Q22 through two series connection resistance R35, resistance R36 and opto-coupler Q21 is connected, and opto-coupler Q21's positive pole is provided with the second voltage, and resistance R35 and resistance R36's middle node is connected with MCU.
9. The power output circuit of the analog battery as claimed in claim 1, further comprising a voltage shift circuit, wherein the voltage shift circuit is provided with a comparator U10, a non-inverting input terminal of the comparator U10 obtains a voltage division from a third direct current (VCC3) through a resistance voltage division circuit, an inverting input terminal of the comparator U10 is provided with a reference voltage, an output terminal of the comparator U10 is connected with an anode of the optocoupler Q33 through a resistance R51, a cathode of the optocoupler Q33 is connected to ground, a collector of the optocoupler Q33 is connected with a resonance control of the output synchronous following unit, and an emitter of the optocoupler Q33 is connected to ground.
10. The power output circuit of an analog battery according to any of claims 1 to 9, further comprising a communication circuit for communicating with the outside.
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| Application Number | Priority Date | Filing Date | Title |
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| CN202220578828.5U CN217085219U (en) | 2022-03-16 | 2022-03-16 | Power output circuit of analog battery |
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| CN202220578828.5U CN217085219U (en) | 2022-03-16 | 2022-03-16 | Power output circuit of analog battery |
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN117559608A (en) * | 2024-01-09 | 2024-02-13 | 深圳市鼎阳科技股份有限公司 | Double-quadrant power supply capable of seamlessly switching charging and discharging and electronic equipment |
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN117559608A (en) * | 2024-01-09 | 2024-02-13 | 深圳市鼎阳科技股份有限公司 | Double-quadrant power supply capable of seamlessly switching charging and discharging and electronic equipment |
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Address after: 518,000 Room 410, Building 5, Shenzhen Software Industry Base, No. 11, 13, 15, Haitian 1st Road, Binhai Community, Yuehai Street, Nanshan District, Shenzhen, Guangdong Patentee after: Shenzhen Angshengda Electronics Co.,Ltd. Address before: 518000 No. 13, floor 3, building Y4, creative park, No. 5, Yayuan Road, Nankeng community, Bantian street, Longgang District, Shenzhen, Guangdong Province Patentee before: SHENZHEN ASUNDAR ELECTRONIC CO.,LTD. |
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