CN217036816U - Output synchronous following circuit of simulation battery - Google Patents
Output synchronous following circuit of simulation battery Download PDFInfo
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- CN217036816U CN217036816U CN202220578786.5U CN202220578786U CN217036816U CN 217036816 U CN217036816 U CN 217036816U CN 202220578786 U CN202220578786 U CN 202220578786U CN 217036816 U CN217036816 U CN 217036816U
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Abstract
The utility model relates to the technical field of analog batteries, and discloses an output synchronous following circuit of an analog battery, aiming at solving the technical problems of low test quality and low efficiency of the existing analog battery caused by burr interference. The output synchronous following circuit adopts an adjustable LCC switching power supply, so that the volume of a high-power instrument can be reduced in a large range, and the mass of the instrument can be reduced.
Description
Technical Field
The utility model relates to the technical field of analog batteries, in particular to an output synchronous following circuit of an analog battery.
Background
With the heavy use of lithium batteries and polymer batteries by various consumer electronics products, testing electronic products using real batteries affects testing efficiency, and simulated batteries, which may also be referred to as battery simulators, are often used to replace real batteries.
Along with the increase of the battery capacity, higher requirements are put on the power of an analog battery, the increase of the power is usually accompanied with the increase of the volume and the mass, and the existing analog battery has overlarge volume and mass, is heavy and is inconvenient to carry.
SUMMERY OF THE UTILITY MODEL
The utility model aims to provide an output synchronous follower circuit of an analog battery, which is used for solving the technical problem that the volume and the mass of the conventional analog battery are overlarge.
In order to achieve the above object, the present invention provides an output synchronous follower circuit of an analog battery, which comprises:
an output synchronous following circuit of an analog battery comprises a resonance controller used for modulating and generating a voltage driving signal, an LCC circuit used for carrying out power conversion according to the voltage driving signal and outputting a direct-current switching power supply, and a voltage and current feedback circuit used for feeding back parameters of the direct-current switching power supply to the resonance controller. The output synchronous following circuit adopts an adjustable LCC switching power supply, and compared with a pure linear conversion circuit, the volume of a high-power instrument can be reduced in a large range, and the mass of the instrument can be reduced.
Further, an optical coupling control circuit is arranged between the voltage and current feedback circuit and the resonance controller, and electric isolation is achieved.
Further, the LCC circuit includes a synchronous rectification controller and a transformer, a voltage driving signal is input to a primary side coil of the transformer, a secondary side coil of the transformer is provided with a center tap for outputting a dc switching power supply, and two ends of the secondary side coil are respectively connected with drains of a switching tube Q13 and a switching tube Q14; the gates of the switching tube Q13 and the switching tube Q14 are connected to the synchronous rectification controller, and the sources of the switching tube Q13 and the switching tube Q14 are connected to the ground GND.
Further, the primary side coil is grounded HGND through an X capacitor for eliminating differential mode interference.
Further, the resonant controller further comprises a primary side current sampling circuit used for feeding back to the resonant controller, the primary side current sampling circuit comprises a resistor R68 connected with the high potential end of the X capacitor, the resistor R68 is connected with an intermediate node of a switching diode D5 used for suppressing conducted interference through a series capacitor C6, the switching diode D5 comprises two diodes which are connected end to end, the anode of the switching diode D5 is connected to the ground HGND, and the cathode of the switching diode D5 outputs a current sampling signal.
Further, the switch diode D5 is connected in parallel with a resistor-capacitor filter circuit.
Further, the voltage and current feedback circuit comprises a voltage feedback circuit and a current feedback circuit, the optical coupler control circuit comprises a first optical coupler, a second optical coupler and a third optical coupler, the output synchronous following circuit comprises a primary auxiliary power supply for supplying power to the resonance controller, a secondary auxiliary power supply for supplying power to the voltage and current feedback circuit, and a control input port for providing an external input signal and an input power supply, the voltage feedback circuit samples the primary auxiliary power supply through the first optical coupler, the voltage feedback circuit samples the primary auxiliary power supply through the third optical coupler, and an external differential pressure signal passes through the second optical coupler to control the resonance controller. The voltage output of the simulation battery can be followed by adjusting the voltage, so that the voltage range of the output adjustable voltage of the simulation battery can be enlarged, the voltage output of the simulation battery can be followed, the voltage difference of the adjusting tube of the power output circuit in the simulation battery is always maintained at the fixed voltage in the voltage adjusting process or the fixed voltage working process, the power consumption of the power adjusting tube is reduced, the working stability of a simulation battery system is improved, the heat dissipation of elements and the optimization of a radiator are facilitated, and the volume and the quality of the simulation battery are further reduced.
Furthermore, a collector of the second optocoupler is connected with the resonance controller, an emitter of the second optocoupler is connected with a ground HGND, an anode of the second optocoupler is connected with a direct current switching power supply through a constant current circuit, a cathode of the second optocoupler is connected with an external power supply, and an external differential pressure signal is formed between the direct current switching power supply and the voltage of the external power supply.
Further, the constant current circuit comprises an NPN type triode Q31 and a triode Q32, the base of the triode Q31 is connected with the emitter of the triode Q32, the collector of the triode Q31 is connected with the base of the triode Q32, a resistor R46 for current sampling is arranged between the base and the emitter of the triode Q31, the emitter of the triode Q31 is connected with the anode of the second optocoupler, and the base of the triode Q32 is connected with a direct current switching power supply through a biasing resistor R47.
The output synchronous follower circuit of the analog battery provided by the utility model has the following advantages:
the output synchronous following circuit adopts an adjustable LCC switching power supply, so that the volume of a high-power instrument can be reduced in a large range, and the mass of the instrument can be reduced. In addition, the adjustable voltage range of the output of the analog battery can be enlarged through voltage following adjustment; the voltage output of the simulation battery can be followed, so that the voltage difference of the adjusting tube of the power output circuit in the simulation battery is always maintained at the fixed voltage in the voltage adjusting process or the fixed voltage working process, the power consumption of the power adjusting tube is reduced, the working stability of the simulation battery system is improved, convenience is brought to the heat dissipation of elements and the optimization of a radiator, and the size and the quality of the simulation battery are further reduced.
Drawings
FIG. 1 is a block diagram of a high power analog battery system provided by the present invention;
FIG. 2 is a functional block diagram of a power factor correction circuit according to the present invention;
FIG. 3 is a schematic diagram of a circuit structure of a power factor correction circuit according to the present invention;
FIG. 4 is a functional diagram of an output synchronous follower circuit according to the present invention;
FIG. 5 is a block diagram of an output synchronous follower circuit according to the present invention;
fig. 6 is a schematic structural diagram of a resonant controller driving circuit provided in the present invention;
fig. 7 is a circuit diagram of a resonant controller LCC provided by the present invention;
FIG. 8 is a functional block diagram of a power output circuit provided by the present invention;
FIG. 9 is a schematic diagram of a power output module according to the present invention;
FIG. 10 is a schematic diagram of the ADC, DAC and voltage measurement circuit provided by the present invention;
FIG. 11 is a block diagram of a charging and discharging power circuit provided by the present invention;
fig. 12 is a structural diagram of an output protection switch and an output protection control circuit provided by the present invention;
fig. 13 is a structural diagram of a current detection circuit, a current gear selector switch and a current gear control circuit provided by the utility model;
FIG. 14 is a schematic diagram of a differential pressure and optocoupler control circuit according to the present invention;
fig. 15 is a schematic diagram of a voltage shift and optocoupler control circuit according to the present invention.
In the figure: VCC1, first direct current; VCC2, second direct current; VCC3, third direct current; VCC4, fourth direct current; VCC5, fifth dc; VO, tail end direct current; q30 and a second optical coupler; T3B, transformer; u8, synchronous rectification controller; LR3, primary side coil; T3D and T3E, secondary side coil; SQH, voltage drive signal; CR3, X capacitance.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is further described in detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the utility model and do not limit the utility model.
Referring to fig. 1 to 15, the present invention provides a high power analog battery, which includes a power factor correction circuit, an output synchronous follower circuit and a power output circuit. The power factor correction circuit is used for converting input commercial alternating current into high-voltage first direct current VCC1, correcting the power factor of the power factor, improving the power factor and reducing reactive current; the output synchronous following circuit acquires a first direct current VCC1 from the power factor correction circuit and outputs a third direct current VCC3 of 2-52V; the power output circuit acquires a third direct current VCC3, outputs a tail end direct current VO, and feeds back the tail end direct current VO to the output synchronous following circuit, so that the output synchronous following circuit adjusts the pressure difference of the adjusting tube in the power output circuit or fixes the voltage during operation, the constant voltage is always maintained, the power consumption of the power adjusting tube is reduced, the stability of the high-power simulation battery system is improved, the test requirement of current battery capacity increase is met, the heat productivity is reduced, the heat dissipation of elements and the optimization of a radiator are facilitated, the volume and the quality of the high-power simulation battery are reduced, and the high-power simulation battery is lighter and more portable.
The inductive load or the capacitive load enables the power factor of the power grid to be smaller than 1, the too small power factor wastes the capacity of the power supply equipment, and the power factor correction circuit corrects the power factor.
Referring to fig. 3, the power factor correction circuit includes a PFC module, the PFC module includes a first common mode inductor electrically connected to a commercial ac, a second common mode inductor connected to the first common mode inductor, and a rectifier module connected to the second common mode inductor, a positive electrode of the rectifier module is connected to a coil L1A, an output end of the coil L1A is connected to a drain of a switching tube Q1, a source of the switching tube Q1 is grounded, a gate of the switching tube Q1 is connected to a driving end of the power factor controller, the switching tube Q1, the coil L1A, a capacitor C1, and the power factor controller constitute the power factor correction circuit, when the switching tube Q1 is turned on, a current flows through the coil L1A, before the coil L1A is not saturated, the current linearly increases, electric energy is stored in the coil L1A in the form of magnetic energy, and at this time, the capacitor C1 discharges to provide energy for a load at a later stage; when the switching tube Q1 is turned off, a self-induced electromotive force is generated across the coil L1A to keep the current direction unchanged. Thus, the self-induced electromotive force is connected in series with the power supply output from the rectifier module to supply power to the capacitor C1 and the load.
Preferably, the switching tube Q1 is an NMOS tube.
The beneficial effects brought by the method are as follows: the input current is completely continuous and can be modulated in the sine period of the whole input voltage, so that a high power factor can be obtained; the current of the coil L1A is the input current, and is easy to adjust; the grid electrode driving signal ground and the output of the switching tube Q1 are connected with the ground, and the driving is simple; the input current is continuous, the current peak value of the switching tube Q1 is small, the adaptability to the input voltage change is strong, and even the commercial power voltage change is large.
Referring to fig. 2, the pfc circuit includes an auxiliary power supply for generating a second dc voltage VCC2 at a low voltage to supply power to the pfc circuit.
In order to avoid surge current generated in the instant of starting up, a power type thermistor is connected in series in an alternating current circuit at the front stage of the rectifier module, and is specifically arranged between a first common mode inductor and a second common mode inductor, the thermistor is a thermistor with a negative temperature coefficient, the resistance value of the thermistor is reduced along with the temperature increase, when the load is too heavy, the current flowing through the thermistor is increased, the temperature of the thermistor is increased, in order to prevent the thermistor from being burnt out due to too high temperature, a first voltage feedback circuit is further arranged and used for collecting the voltage of first direct current VCC1, the output end of the first voltage feedback circuit is connected with a switching tube Q2 which is connected with the base of a switching tube Q2, the emitter of the switching tube Q2 is grounded, the thermistor is connected in parallel with a relay, two normally open contacts of the relay are connected with two ends of the thermistor, and two ends of a coil of the relay are respectively connected with a low-voltage direct current VCC2, a low-voltage direct current switch Q2, a high-voltage switch is connected with the output of the relay, and a high-voltage switch is connected with the high-voltage switch, The collector of switch tube Q2 is connected, goes to the opening and shutting of control relay through switch tube Q2, and when the electric current of output was too high, the switch in the relay was closed, with the thermistor short circuit, has avoided thermistor to be burnt out.
Preferably, the switching transistor Q2 is an NPN-type transistor.
In one embodiment, a typical value for high voltage dc VCC1 is 390V, and a typical value for low voltage dc VCC2 is 12V.
Referring to fig. 4, the output synchronous follower circuit includes an input port connected to an output port of the power factor correction circuit, and acquires a first direct current VCC1 and a second direct current VCC2 from the power factor correction circuit, and further includes a control input port connected to the power output circuit, and is configured to provide a 12V power supply and a control signal, and finally output a third direct current VCC3 to the power output circuit.
Referring to fig. 5, the output synchronous follower circuit includes a primary auxiliary power supply and a secondary auxiliary power supply, the primary auxiliary power supply converts the second dc VCC2 into a fourth dc VCC4 to supply power to the resonant controller; the 12V of the control input port supplies power to the secondary auxiliary power supply, the secondary auxiliary power supply converts the voltage into fifth direct current VCC5 and 2.5V voltage to supply power to the voltage and current feedback circuit, and the control signal is used for the optocoupler control circuit.
Referring to fig. 6, the output synchronous follower circuit includes a resonant controller for outputting a 50% duty cycle, at the same time, high-side and low-side 180-degree phase inversion. The resonance controller is connected with a first direct current VCC1 and a fourth direct current VCC4, outputs a voltage driving signal SQH, and comprises a plurality of controlled ends controlled by an optical coupling control circuit, and the optical coupling control circuit is connected with the controlled ends; the high-end suspended gate driving output pin of the resonant controller is connected with the base electrode of a PNP type triode Q8, the low-end gate driving output pin of the resonant controller is connected with the base electrode of a PNP type triode Q7, the emitter electrode of the triode Q8 is connected with the gate electrode of a switching tube Q4, and the drain electrode of the switching tube Q4 is connected with a first direct current VCC 1; an emitter of the triode Q7 is connected with a gate of the switching tube Q6, a drain of the switching tube Q6 is connected with a source of the switching tube Q4, a source of the switching tube Q4 is grounded, and a collector of the triode Q7 is grounded; the floating ground pin of the high-side gate drive of the resonant controller is respectively connected with the collector of the triode Q8 and the source of the switching tube Q4, and the first direct current VCC1 is modulated by the circuit to generate a voltage drive signal SQH.
Referring to fig. 7, a voltage driving signal SQH is input to an LCC circuit, the LCC circuit includes a synchronous rectification controller U8, a voltage driving signal SQH is input to a transformer T3B, the transformer T3B has a primary side coil LR3, a secondary side coil T3D with a center tap, and a transformer T3E, one end of the primary side coil LR3 is connected to the voltage driving signal SQH, the other end of the primary side coil LR3 is grounded through an X capacitor CR3, and the X capacitor CR3 is used to eliminate differential mode interference; the two ends of the secondary side coil are respectively connected with the drain electrode of the switching tube Q13 and the drain electrode of the switching tube Q14, and the center tap is used for outputting third direct current VCC3 with the output of 2-52V.
A first drain end of the synchronous rectification controller U8 is connected with a drain electrode of the switching tube Q14, a first gate end is connected with a gate electrode of the switching tube Q14, and a first source end is connected with a source electrode of the switching tube Q14; a second drain terminal of the synchronous rectification controller U8 is connected to the drain of the switching tube Q13, a second gate terminal is connected to the gate of the switching tube Q13, a second source terminal is connected to the source of the switching tube Q13, and the sources of the switching tube Q13 and the switching tube Q14 are grounded.
The LCC circuit also includes a primary side current sampling circuit that samples the current on the primary side of transformer T3B for feedback to the resonant controller. The primary side current sampling circuit comprises a resistor R68 connected with the other end of the primary side coil LR3, the resistor R68 is connected with the middle junction of a switch diode D5 used for suppressing conducted interference through a series capacitor C6, the switch diode D5 comprises two end-to-end connected diodes, the anode of the switch diode D5 is grounded HGND, and the cathode of the switch diode D5 is connected with a current sampling signal input end of the resonant controller through a CS line.
Furthermore, the cathode of the switching diode D5 is connected in parallel with a resistance-capacitance filter circuit, which is grounded through a resistor R75, a capacitor R79 and a capacitor C21, respectively, and the resistor R75, the capacitor R79 and the capacitor C21 connected in parallel form the resistance-capacitance filter circuit.
The LCC circuit comprises a plurality of same circuits, and the LCC circuits are connected in parallel, so that the output power and the output stability are increased.
Referring to fig. 5, the voltage and current feedback circuit comprises a voltage feedback circuit and a current feedback circuit, the optical coupler control circuit comprises a first optical coupler, a second optical coupler and a third optical coupler, the control input port controls the first optical coupler through a PS _ ON circuit, a secondary auxiliary power supply provides 2.5V power for the voltage feedback circuit, the control input port controls the second optical coupler through a third direct current VCC3 and a terminal direct current VO, the output ends of the second optical coupler and the third optical coupler are connected in parallel, the output end of the third optical coupler is respectively connected with an intermittent working mode threshold pin of the resonant controller, and the lowest oscillation frequency setting pin is connected.
The voltage feedback circuit detects the voltage value of the third direct current VCC3, the primary auxiliary power supply is controlled through the first optical coupler, the primary auxiliary power supply outputs or turns off the fourth direct current VCC4, and when the third direct current VCC3 is detected to be overvoltage, the primary auxiliary power supply turns off the output, so that the overvoltage protection effect is realized.
The current detection circuit detects the current value of the third direct current VCC3, and the current value is fed back to the resonance controller through the third optical coupler, so that the resonance controller can work or stand by, and intermittent work is realized.
Referring to fig. 8, the power output circuit includes a power output module, an MCU, an ADC, a DAC, a communication circuit, a power control interface, and a voltage measurement circuit, wherein the MCU is used for overall system control of the power output module; the ADC is used for converting analog signals into digital signals; DCA is used for digital to analog signal conversion; the communication circuit is used for the MCU to communicate with the outside; the power supply control interface is used for providing a control signal; the voltage measuring circuit is used for measuring the voltage output by the power output module; the control input port is used as a shared interface, is connected with the power output circuit and the output synchronous follower circuit and is used for providing voltage and control signals, including control signals such as Ct1_ Up and Ct1_ Down.
The power output module can be used for discharging and charging, wherein discharging refers to that the power output module provides voltage for external electric equipment to work; the charging means that the power output circuit consumes electric energy as a load and is used for completing the charging function test of a tested product.
Referring to fig. 9, the power Output module includes a discharge power adjusting tube located at the upper portion and a charge power adjusting tube located at the lower portion, a power input end of the discharge power adjusting tube is used for connecting a third direct current VCC3 of the Output synchronous follower circuit, and is controlled by a Ct1_ Up signal line, so that the discharge power adjusting tube performs a switching operation according to a predetermined frequency, an Output _ V line obtains a voltage, and a final Output terminal direct current VO is provided to an external power consumption device.
When charging, external voltage is introduced into an Output _ V circuit of the power Output module and is controlled by a Ct1_ Down signal circuit, so that the charging power adjusting tube performs switching action according to a preset frequency, and the charging power adjusting tube consumes electric energy, thereby completing the charging test of a tested product.
Specifically, as shown in fig. 11, the discharge power adjusting tube includes a switching tube Q15, a drain of the switching tube Q15 is used for inputting a third direct current VCC3, a source of the switching tube Q15 is connected to an Output _ V line through a resistor R19, a gate of the switching tube Q15 is connected to a Ct1_ Up signal line, when the Ct1_ Up signal line is at a high level, the switching tube Q15 is turned on, and the third direct current VCC3 falls into the Output _ V line, thereby discharging to the outside.
Furthermore, in order to improve the Output power and the Output stability, the power converter further comprises a switching tube Q16 controlled by the switching tube Q15 after being turned on, a drain of the switching tube Q16 is used for inputting a third direct current VCC3, a source of the switching tube Q16 is connected with an Output _ V line through a resistor R32, a gate of the switching tube Q16 is connected with an Output end of a comparator U6, an inverting input end of the comparator U6 obtains a reference voltage from the line Clt _ VCC through a resistor R26, a non-inverting input end of the comparator U6 is connected with a source of the switching tube Q15, a positive electrode of the comparator U6 is connected with the line Clt _ VCC, and a negative electrode of the comparator U6 is connected with the Output _ V line. When the switching tube Q15 is turned on, the comparator U6 outputs a high level to turn on the switching tube Q16, and a path of the third direct current VCC3 loaded to the Output _ V line is increased. The resistors R19 and R32 are extremely low in resistance and can carry a large current, and alloy resistance is preferable.
During discharging, the switching tube Q15 is firstly conducted, and the switching tube Q16 is then conducted, so that current impact caused by simultaneous conduction is avoided in time delay, and in addition, the switching tube Q16 can be independently controlled through Ctl _ VCC to control the number of the conducted switching tubes and control the output power; the switch tube Q15 and the switch tube Q16 are power tubes with linear regulation, and the quality of output voltage is improved.
More combined circuits of the switching tube Q16 and the comparator U6 can be provided, and the path of the third direct current VCC3 loaded to the Output _ V line is further increased, so that the Output current is improved, the stability of Output is enhanced, and the Output power is increased.
The charging power adjusting tube comprises a switch tube Q17, the drain of the switch tube Q17 is used for inputting the voltage of an Output _ V line, namely, when a tested product is tested and charged, the power supply voltage of the tested product is on the Output _ V line, the source of the switch tube Q17 is connected with a ground wire GND through a resistor R27, the gate of the switch tube Q17 is connected with a Ct1_ Down signal line, when the Ct1_ Down signal line is in a high level, the switch tube Q17 is conducted, the power supply of the tested product falls into the ground wire GND, and therefore electric energy is consumed.
Furthermore, in order to improve the load capacity, the load-tolerant power supply further comprises a switching tube Q18 controlled by the conducted switching tube Q17, the drain of the switching tube Q18 is used for inputting the voltage of an Output _ V line, the source of the switching tube Q18 is connected with a ground line GND through a resistor R33, the grid of the switching tube Q18 is connected with the Output end of a comparator U7, the inverting input end of the comparator U7 obtains a reference voltage from a 12V power supply through a resistor R31, the non-inverting input end of the comparator U7 is connected with the source of the switching tube Q17, the positive end of the comparator U7 is provided with the 12V voltage, and the negative end of the comparator U7 is connected with the ground line GND. When the switching tube Q17 is turned on, the comparator U7 outputs a high level to turn on the switching tube Q18, and a path for loading the voltage of the Output _ V line to the ground GND increases. The resistors R27 and R33 are extremely low in resistance and can carry a large current, and alloy resistance is preferable.
More combined circuits of the switching tube Q18 and the comparator U7 can be adopted, the voltage of the Output _ V line is loaded to the ground line GND, the load capacity is improved, the stability of the load is enhanced, and the load power is increased.
The switch tube Q15, the switch tube Q16, the switch tube Q17 and the switch tube Q18 are preferably linear power NMOS tubes, so that the glitch interference generated by the output of the traditional analog battery DC/DC switch can be effectively inhibited, the dynamic response speed is improved, the output voltage clutter interference is small, the voltage is pure and stable, and the quality and the efficiency of a test product of the analog battery are improved; the Ct1_ Up signal line and the Ct1_ Down signal line change the duty ratio to change the time length of the output current, so as to change the average current.
Referring to fig. 9, a current detection resistor is connected in series to the ground GND, and a voltage across the current detection resistor is collected by an output current amplifying circuit and sent to the MCU. The current detection resistor comprises a first current detection resistor used for detecting the magnitude of current in an ampere level and a second current detection resistor used for detecting current in a milliampere level.
A current gear selector switch is further arranged on the ground wire GND and connected in parallel with a second current detection resistor, the MCU controls the current gear selector switch through a current gear control circuit, when the current gear selector switch is switched off, the current in the circuit is small, the second current detection resistor plays a main role, and the current detection is more accurate; when the current gear shifting switch is closed, a larger current can flow through the circuit, the second current detection resistor is short-circuited, and the second current detection resistor does not work; and selecting the current gear selector switch to be switched on or switched off according to different application scenes.
The current gear selector switch can be switched automatically or manually, preferably, the current gear selector switch is automatically switched under the control of an MCU (micro control unit), the current condition detected by the output current amplifying circuit is used as a judgment basis automatically, and the current gear selector switch is automatically switched to a low-current gear when the current is reduced to a preset value, so that the voltage change of charging and discharging of a battery in a certain time period is simulated, the current measurement is more accurate, and the static current and the power consumption of a test product are very convenient; when manual, can go through control panel to set up, go to adjust according to the user's demand.
Specifically, referring to fig. 13, a resistor R41 is a first current detection resistor, a resistor R40 is a second current detection resistor, a switch Q23 and a switch Q24 form a current step switch, and a transistor Q26 and a transistor Q27, a resistor R38 and a resistor R39 form a current step control circuit.
It can be understood that, in order to increase the output current in the circuit and increase the output power, a plurality of switching tubes may be arranged in parallel with the switching tube Q23 and the switching tube Q24, respectively.
Preferably, the switching tube Q23 and the switching tube Q24 are NMOS tubes.
Further, a capacitor C11 is connected in parallel between the drain and the source of the switching tube Q23 for reducing switching spikes and reducing electromagnetic radiation.
When the MCU generates a low level through the port A/mA, the triode Q26 is cut off, the base electrode of the triode Q27 obtains voltage through the pull-up resistor R38, the triode Q27 is conducted, the grid electrodes of the switch tube Q23 and the switch tube Q24 obtain starting voltage to be conducted, namely, the current gear change-over switch is closed, the second current detection resistor is short-circuited, large current can flow through the circuit, and ampere-level current in the first current detection resistor detection circuit is fed back to the MCU through the output current amplification circuit.
When the MCU generates a high level through the a/mA port, the transistor Q26 is turned on, so that the base of the transistor Q27 is grounded, the transistor Q27 is turned off, and the gates of the switching tube Q23 and the switching tube Q24 lose their turn-on voltages and turn off, that is, the current gear selector switch is turned off, the current flows through the second current detection resistor, a small current flows through the circuit, and the second current detection resistor detects a milliamp-level current in the circuit and feeds it back to the MCU through the output current amplifier circuit.
In order to detect the current during charging and discharging respectively, the output current amplifying circuit comprises an operational amplifier U9-A and an operational amplifier U9-B, the 1 st end of a first current detection resistor (R41) is connected with the inverting input end of the operational amplifier U9-A and the non-inverting input end of the operational amplifier U9-B respectively, and the 2 nd end of a first current detection resistor (R41) is connected with the non-inverting input end of the operational amplifier U9-A and the inverting input end of the operational amplifier U9-B respectively; the 1 st end of a second current detection resistor (R40) is respectively connected with the non-inverting input end of the operational amplifier U9-A and the inverting input end of the operational amplifier U9-B, and the 2 nd end of the second current detection resistor (R40) is connected with the non-inverting input end of the operational amplifier U9-A and the inverting input end of the operational amplifier U9-B through a diode D3 and a diode D4 which are connected in parallel in an opposite direction; this allows current amplification from different current directions.
Referring to fig. 9, an output protection switch is further disposed on the ground GND, the MCU controls the output protection switch through the output protection control circuit according to the current condition detected by the output current amplifying circuit, and turns off the output protection switch when the current exceeds a threshold.
Referring to fig. 12, the output protection switch includes a switching tube Q19 and a switching tube Q20, a drain of the switching tube Q19 is connected to a line at the front end of the protection, a source of the switching tube Q19 is connected to a source of the switching tube Q20, a drain of the switching tube Q20 is an output line at the rear end of the protection, and gates of the switching tube Q19 and the switching tube Q20 are connected to an output protection control circuit.
The output protection control circuit comprises an optocoupler Q21 and an optocoupler Q22, an emitter of the optocoupler Q21 is connected with a source electrode of a switching tube Q19, a collector of the optocoupler Q21 is connected with a switching tube Q19 and a grid electrode of the switching tube Q20 respectively, an emitter of the optocoupler Q22 is connected with a collector of the optocoupler Q21 through a resistor R37, and a collector of the optocoupler Q22 is provided with 12V voltage; the negative pole ground connection of opto-coupler Q22, the negative pole that passes through two series connections of opto-coupler Q22 resistance R35, resistance R36 and opto-coupler Q21 is connected, and opto-coupler Q21's positive pole is provided with 3.3V voltage, and resistance R35 and resistance R36's middle node is connected with MCU's port OUT.
MCU produces the high-low level through its port OUT, makes opto-coupler Q21 and opto-coupler Q22 work in turn, and when opto-coupler Q21 during operation, the inside triode of opto-coupler Q21 switches on for switch tube Q19 and switch tube Q20's VGSIs 0, VGS<VTHThe switch tube Q19 and the switch tube Q20 are cut off, namely the output protection switch is switched off, so that the protection function is realized; when the optocoupler Q22 works, the internal triode of the optocoupler Q22 is conducted, so that the grids of the switching tube Q19 and the switching tube Q20 acquire voltage VGS>VTHThe switching tube Q19 and the switching tube Q20 are turned on, that is, the output protection switch is closed, so as to form a path.
Furthermore, a plurality of switching tubes may be respectively connected in parallel with the switching tube Q19 and the switching tube Q20 to increase the output current and the output power.
It is understood that the current detecting resistor, the current step switch and the Output protection switch can also be arranged on the Output _ V line.
As shown in fig. 9, the conventional analog battery is directly connected to the output current amplifying circuit by using the MCU, so that the MCU directly samples the analog signal, and the analog battery has the advantage of high response speed, is limited by the characteristics of the MCU itself, and thus has low display accuracy.
As shown in fig. 10, in order to provide the accuracy of current display, a current signal ADC for converting an analog current into a digital current is provided, an input end of the current signal ADC is connected to two ends of a current detection resistor, an output end of the current signal ADC is connected to an MCU, and a sampling number is sent to the MCU through the single high-accuracy current signal ADC, so that the sampling accuracy can be improved.
Further, the current signal ADC includes a current safety gear ADC and a current milliampere gear ADC, and input ends of the current safety gear ADC and the current milliampere gear ADC are respectively connected to two ends of the first current detection resistor and the second current detection resistor.
The voltage measuring circuit comprises a local output sampling circuit and a remote output sampling circuit, and the local output sampling circuit is used for adopting the output voltage of a local port; because the power transmission line has the overlength condition when the product to be measured uses, cause and have the pressure drop on the power transmission line, the voltage that shows does not represent the true voltage value that the product to be measured obtained, still is equipped with far-end output sampling circuit for this reason, uses the far-end sampling to solve the heavy current pressure drop problem.
Furthermore, in order to improve the accuracy of voltage measurement, the voltage measurement device also comprises a voltage signal ADC, so that the sampling is more accurate and the display is more accurate.
Parameters controlled by the display screen or data set by parameters of an external upper computer, an ATE test cabinet and the like are sent to the MCU by the communication circuit, processed by the MCU, converted by the DAC and sent to the power output module, and then output voltage is controlled.
Preferably, the communication circuit is an RS485 communication circuit.
Referring to fig. 14, in order to solve the problem of the voltage difference of the discharge power regulating tube in the power output module, the optocoupler control circuit respectively obtains a third direct current VCC3 and a terminal direct current VO from the power output circuit, because the discharge power regulating tube has a voltage difference, the voltage of the terminal direct current VO is lower than the third direct current VCC3, when the voltage difference between the two is lower than a threshold, the second optocoupler Q30 operates, the triode in the second optocoupler Q30 is turned on to pull down the relevant power pin of the resonant controller, so as to enable the resonant controller to regulate the output frequency, further change the third direct current VCC3 and the terminal direct current VO, that is, when the output synchronous following circuit follows the voltage difference of the regulating tube in the power output circuit to regulate or work with a fixed voltage, the output synchronous following circuit is always maintained at a fixed voltage, the power consumption of the power regulating tube itself is reduced, the working stability of the high-power analog battery system is improved, and the current test requirement of increasing the battery capacity is satisfied, the heat productivity is reduced, the heat dissipation of elements and the optimization of a radiator are facilitated, the size and the mass of the high-power simulation battery are reduced, and the high-power simulation battery is lighter and more convenient to carry.
Specifically, a collector of the second optocoupler Q30 is connected with the resonance controller, an emitter of the second optocoupler Q30 is connected to the ground HGND, an anode of the second optocoupler Q30 is connected with a third direct current VCC3 through a constant current circuit, a cathode of the second optocoupler Q30 is connected with a terminal direct current VO, an external voltage difference signal is formed between the voltage of the third direct current VCC3 and the voltage of the terminal direct current VO, and the constant current circuit performs current limiting, so that the control precision is improved. The constant current circuit comprises an NPN type triode Q31 and a triode Q32, the base electrode of the triode Q31 is connected with the emitting electrode of the triode Q32, the collector electrode of the triode Q31 is connected with the base electrode of the triode Q32, a resistor R46 used for current sampling is arranged between the base electrode of the triode Q31 and the emitting electrode, the emitting electrode of the triode Q31 is connected with the anode of a second optocoupler Q30, and the base electrode of the triode Q32 is connected with the direct current switching power supply through a bias resistor R47.
In addition, referring to fig. 15, the voltage shift circuit obtains a third direct current VCC3 from the power output circuit, and the third direct current VCC is fed back to the resonant controller through the comparator U10 and the optocoupler Q33, so as to adjust the oscillation frequency of the resonant controller, thereby implementing voltage shift. The non-inverting input end of the comparator U10 obtains voltage division from a third direct current VCC3 through a resistor voltage division circuit composed of a resistor R49 and a resistor R50, the inverting input end of the comparator U10 is provided with reference voltage, the output end of the comparator U10 is connected with the anode of an optocoupler Q33 through the resistor R51, the cathode of the optocoupler Q33 is connected with the ground, the collector of the optocoupler Q33 is connected with the resonance control of the output synchronous following circuit, and the emitter of the optocoupler Q33 is grounded.
In summary, the high-power analog battery provided by the utility model is improved aiming at the defects of the prior art, the resonant controller of the output synchronous following circuit outputs a voltage driving signal waveform to the LCC circuit for power conversion, the voltage and current signals at the output end are provided to the voltage and current feedback circuit after being converted by the LCC circuit, and the voltage and current feedback signals are transmitted to the feedback end of the resonant controller through the optocoupler control circuit, so as to control the voltage and current output of the power supply; and an output voltage signal of the power output circuit is input into the optical coupling control circuit to control the voltage of the output synchronous following circuit to follow the output voltage of the whole high-power analog battery. The power supply of the front stage adopts an adjustable LCC switching power supply, so that the volume of a high-power instrument can be reduced in a large range, and the mass of the instrument can be reduced; the adjustable voltage range of the output of the analog battery can be enlarged through voltage following adjustment; the power output of the analog battery adopts a power tube with linear adjustment, so that the quality of output voltage is improved.
The above description is intended to be illustrative of the preferred embodiment of the present invention and should not be taken as limiting the utility model, but rather, the intention is to cover all modifications, equivalents, and alternatives falling within the spirit and scope of the utility model.
Claims (9)
1. The output synchronous following circuit of the analog battery is characterized by comprising a resonance controller used for modulating and generating a voltage driving signal, an LCC circuit used for carrying out power conversion according to the voltage driving signal and outputting a direct-current switching power supply, and a voltage and current feedback circuit used for feeding back parameters of the direct-current switching power supply to the resonance controller.
2. The output synchronous follower circuit of the analog battery as claimed in claim 1, wherein an optical coupling control circuit is further provided between the voltage current feedback circuit and the resonant controller.
3. The output synchronous follow circuit of the analog battery according to claim 2, characterized in that, the LCC circuit comprises a synchronous rectification controller (U8) and a transformer (T3B), the voltage driving Signal (SQH) is inputted to a primary side coil (LR3) of the transformer (T3B), a secondary side coil (T3D, T3E) of the transformer (T3B) is provided with a center tap for outputting a dc switching power supply, and two ends of the secondary side coil (T3D, T3E) are respectively connected with a drain of a switching tube Q13 and a drain of a switching tube Q14; the gates of the switching tube Q13 and the switching tube Q14 are connected to a synchronous rectification controller (U8), and the sources of the switching tube Q13 and the switching tube Q14 are connected to the ground GND.
4. The output synchronous follower circuit of an analog battery according to claim 3, characterized in that the primary side coil (LR3) is connected to ground HGND through an X capacitor (CR3) for eliminating differential mode interference.
5. The output synchronous follower circuit of the analog battery as claimed in claim 4, further comprising a primary side current sampling circuit for feeding back to the resonant controller, wherein the primary side current sampling circuit comprises a resistor R68 connected to the high potential side of the X capacitor (CR3), the resistor R68 is connected to the middle node of a switch diode D5 for suppressing conducted interference through a series capacitor C6, the switch diode D5 comprises two end-to-end connected diodes, the anode of the switch diode D5 is connected to the ground HGND, and the cathode of the switch diode D5 outputs a current sampling signal.
6. The output synchronous follower circuit of the analog battery as claimed in claim 5, wherein the switch diode D5 is further connected in parallel with a resistance-capacitance filter circuit.
7. The output synchronous follower circuit of the analog battery as claimed in claim 2, wherein the voltage and current feedback circuit comprises a voltage feedback circuit and a current feedback circuit, the optical coupler control circuit comprises a first optical coupler, a second optical coupler (Q30) and a third optical coupler, the output synchronous follower circuit comprises a primary auxiliary power supply for supplying power to the resonant controller, a secondary auxiliary power supply for supplying power to the voltage and current feedback circuit, and a control input port for providing an external input signal and an input power supply, the voltage feedback circuit samples the dc switching power supply to control the primary auxiliary power supply through the first optical coupler, the voltage feedback circuit samples the dc switching power supply to control the resonant controller through the third optical coupler, and an external differential voltage signal controls the resonant controller through the second optical coupler (Q30).
8. The output synchronous follow circuit of the analog battery according to claim 7, wherein a collector of the second optical coupler (Q30) is connected with a resonance controller, an emitter of the second optical coupler (Q30) is connected with a ground HGND, an anode of the second optical coupler (Q30) is connected with the direct current switching power supply through a constant current circuit, a cathode of the second optical coupler (Q30) is connected with an external power supply, and an external voltage difference signal is formed between the direct current switching power supply and the voltage of the external power supply.
9. The output synchronous follower circuit of the analog battery as claimed in claim 8, wherein the constant current circuit comprises an NPN-type transistor Q31 and a transistor Q32, a base of the transistor Q31 is connected to an emitter of the transistor Q32, a collector of the transistor Q31 is connected to a base of the transistor Q32, a resistor R46 for sampling current is arranged between the base and the emitter of the transistor Q31, the emitter of the transistor Q31 is connected to an anode of a second optocoupler (Q30), and the base of the transistor Q32 is connected to the dc switching power supply through a biasing resistor R47.
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| CN202220578786.5U CN217036816U (en) | 2022-03-16 | 2022-03-16 | Output synchronous following circuit of simulation battery |
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| CN202220578786.5U CN217036816U (en) | 2022-03-16 | 2022-03-16 | Output synchronous following circuit of simulation battery |
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN115681263A (en) * | 2022-12-29 | 2023-02-03 | 江苏恒立液压科技有限公司 | Circuit structure of electro-hydraulic proportional movement controller and use method thereof |
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2022
- 2022-03-16 CN CN202220578786.5U patent/CN217036816U/en active Active
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN115681263A (en) * | 2022-12-29 | 2023-02-03 | 江苏恒立液压科技有限公司 | Circuit structure of electro-hydraulic proportional movement controller and use method thereof |
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