CN214756073U - High-gain non-isolated DC-DC conversion circuit - Google Patents

High-gain non-isolated DC-DC conversion circuit Download PDF

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CN214756073U
CN214756073U CN202121331898.2U CN202121331898U CN214756073U CN 214756073 U CN214756073 U CN 214756073U CN 202121331898 U CN202121331898 U CN 202121331898U CN 214756073 U CN214756073 U CN 214756073U
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diode
capacitor
inductor
power supply
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邓元果
曹太强
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Xihua University
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Abstract

The utility model discloses a non-isolation DC-DC converting circuit of high gain connects power, include: the first capacitor is connected with the first diode, the second capacitor is connected with the second diode, the third capacitor is connected with the second capacitor, the fourth capacitor is connected with the third diode, the second capacitor is connected with the eighth capacitor, the third inductor is connected with the fourth inductor, the first switch tube is connected with the second switch tube, the resistor and the booster circuit; the power supply, the booster circuit, the fifth diode, the sixth diode, the resistor, the seventh diode and the eighth diode are sequentially connected in series to form a loop; the power supply, the third diode, the fourth inductor and the first switching tube are sequentially connected in series to form a loop. The utility model discloses utilize the parallelly connected nature of charging, series discharge of inductance-capacitance to form a pressure Boost unit, adopt staggered structure again, make voltage gain can reach 8 times of traditional Boost transformer gain, switching stress only has output voltage's 1/4 to have characteristics such as input current ripple is little, the output voltage ripple is little.

Description

High-gain non-isolated DC-DC conversion circuit
Technical Field
The utility model relates to a DC-DC (direct current-direct current) converting circuit.
Background
In a photovoltaic power generation system, because the output voltage of a photovoltaic cell is low, even if the photovoltaic cell is connected in series and in parallel, the grid-connected requirement is difficult to meet, and meanwhile, the photovoltaic cell has the P-V output characteristic, a DC-DC converter is required to realize direct-current voltage boosting and MPPT (maximum power point tracking), so that the maximum stable and reliable electric energy is output to a power grid for a rear-stage inverter. Because the voltage stress of the switching tube of the Boost (Boost chopper) converter is output voltage, the voltage stress of the switching tube is larger when the output voltage is higher. The traditional Boost converter has lower voltage gain, increases the loss of a switching tube, has larger ripple factor and generates higher peak voltage by increasing the duty ratio when realizing high gain, and can seriously influence the reverse recovery performance of a diode.
SUMMERY OF THE UTILITY MODEL
An object of the utility model is to provide a high-gain non-isolation DC-DC converting circuit increases voltage gain, reduces the switch stress to have the characteristics that the input current ripple is little and the output voltage ripple is little.
The technical scheme for realizing the purpose is as follows:
a high-gain non-isolated DC-DC conversion circuit connected with a power supply comprises: the first capacitor is connected with the first diode, the second capacitor is connected with the second diode, the third capacitor is connected with the second capacitor, the fourth capacitor is connected with the third diode, the second capacitor is connected with the eighth capacitor, the third inductor is connected with the fourth inductor, the first switch tube is connected with the second switch tube, the resistor and the booster circuit;
the power supply, the booster circuit, the fifth diode, the sixth diode, the resistor, the seventh diode and the eighth diode are sequentially connected in series to form a loop;
the power supply, the third diode, the fourth inductor and the first switching tube are connected in series in sequence to form a loop;
the power supply, the third inductor, the fourth diode and the first switching tube are sequentially connected in series to form a loop, and the fourth diode and the fourth inductor are connected with the same end of the first switching tube;
one end of the second capacitor is connected with the connection end of the third diode and the fourth inductor, and the other end of the second capacitor is connected with the connection end of the third inductor and the fourth diode;
two ends of the series branch of the third capacitor and the fourth capacitor are respectively connected with the connection end of the fifth diode and the sixth diode and the connection end of the seventh diode and the eighth diode;
a series branch of the fifth capacitor and the sixth capacitor is connected with the resistor in parallel;
two ends of the second switch tube are respectively connected with the connection end of the boosting unit and the fifth diode, and the connection end of the eighth diode and the power supply;
the connection end of the boosting unit and the fifth diode is connected with the connection ends of the fifth capacitor and the sixth capacitor;
and the connection end of the fourth inductor and the fourth diode is connected with the connection end of the third capacitor and the fourth capacitor.
Preferably, the positive electrode of the power supply is connected to the voltage boost circuit, the cathode of the fifth diode is connected to the anode of the sixth diode, and the cathode of the seventh diode is connected to the anode of the eighth diode;
the anode of the power supply is connected with the anode of the third diode;
one end of the third inductor is connected with the positive electrode of the power supply, and the other end of the third inductor is connected with the anode of the fourth diode.
Preferably, the boosting circuit includes: a first capacitor, a first inductor, a second inductor, a first diode and a second diode,
the anode of the first diode is connected with the positive electrode of the power supply, and the cathode of the first diode is connected with the fifth diode through the second inductor;
the anode of the second diode is connected with the anode of the power supply through the first inductor, and the cathode of the second diode is connected with the fifth diode;
one end of the first capacitor is connected with the connection end of the first diode and the second inductor, and the other end of the first capacitor is connected with the connection end of the first inductor and the second diode.
Preferably, the first switch tube and the second switch tube are both NMOS tubes, and the respective source electrodes of the first switch tube and the second switch tube are both connected to the negative electrode of the power supply; the drain electrode of the first switching tube is connected with the fourth diode and the fourth inductor; and the drain electrode of the second switching tube is connected with the connection end of the boosting unit and the fifth diode.
The utility model has the advantages that: the utility model discloses utilize parallelly connected the nature of charging of inductance and capacitance, series discharge to form a pressure Boost unit, adopt staggered structure again, make voltage gain can reach 8 times of traditional Boost transformer gain, avoided the use of limit duty cycle, reduced switching loss, be applicable to photovoltaic power generation very much. Meanwhile, the voltage stress of the switching tube and the voltage stress of the diode are greatly reduced. The voltage stress of the switching tube is only 1/4 of the output voltage, the voltage stress of the diode is only 1/2 of the output voltage at most, and the voltage stress of the diode is only 1/10 of the output voltage at least under the condition that the duty ratio D is 0.6. The low switching stress can adopt a low-voltage-resistant switching tube and a diode, thereby effectively reducing the switching loss and the cost. And the ripple of the input current is low and the ripple of the output voltage is also low.
Drawings
Fig. 1 is a circuit diagram of a high-gain non-isolated DC-DC converter circuit of the present invention;
FIG. 2 is a waveform diagram of the main operation of the DC-DC converter circuit of the present invention;
fig. 3 is a first operation mode diagram of the DC-DC converter circuit according to the present invention;
fig. 4 is a second operation mode diagram of the DC-DC converter circuit of the present invention;
fig. 5 is a third operation mode diagram of the DC-DC converter circuit according to the present invention.
Detailed Description
The present invention will be further explained with reference to the accompanying drawings.
Referring to fig. 1, the high-gain non-isolated DC-DC converter circuit of the present invention, connected to a power source Uin, includes: the circuit comprises first to eighth diodes D1-D8, first to eighth capacitors C1-D8, a first inductor L11, a second inductor L12, a third inductor L21, a fourth inductor L22, a first switch tube S1, a second switch tube S2, a resistor R and a boosting circuit 100. The boosting circuit 100 includes: a first capacitor C1, a first inductor L11, a second inductor L12, a first diode D1 and a second diode D2.
The power supply Uin, the boosting circuit 100, the fifth diode D5, the sixth diode D6, the resistor R, the seventh diode D7 and the eighth diode D8 are sequentially connected in series to form a loop. The power source Uin, the third diode D3, the fourth inductor L22 and the first switch tube S1 are connected in series in sequence to form a loop. The power source Uin, the third inductor L21, the fourth diode D4 and the first switch S1 are sequentially connected in series to form a loop, and the fourth diode D4 and the fourth inductor L22 are connected to the same end of the first switch S1.
One end of the second capacitor C2 is connected to the connection end of the third diode D3 and the fourth inductor L22, and the other end is connected to the connection end of the third inductor L21 and the fourth diode D4. Two ends of the series branch of the third capacitor C3 and the fourth capacitor C4 are respectively connected to the connection terminals of the fifth diode D5 and the sixth diode D6, and to the connection terminals of the seventh diode D7 and the eighth diode D8. The series branch of the fifth capacitor C5 and the sixth capacitor C6 is connected in parallel with the resistor R.
Two ends of the second switch tube S2 are respectively connected to the connection end of the voltage boost unit 100 and the fifth diode D5, and the connection end of the eighth diode D8 and the power source Uin. The voltage boost unit 100 is connected with the connection end of the fifth diode D5 and the connection ends of the fifth capacitor C5 and the sixth capacitor C6. The connection end of the fourth inductor L22 and the fourth diode D4 is connected with the connection end of the third capacitor C3 and the fourth capacitor C4.
The anode of the power source Uin is connected to the voltage boost circuit 100, the cathode of the fifth diode D5 is connected to the anode of the sixth diode D6, and the cathode of the seventh diode D7 is connected to the anode of the eighth diode D8. The anode of the power source Uin is connected to the anode of the third diode D3. One end of the third inductor L21 is connected to the anode of the power source Uin, and the other end is connected to the anode of the fourth diode D4.
The anode of the first diode D1 is connected to the anode of the power source Uin, and the cathode is connected to the fifth diode D5 through the second inductor L12. The anode of the second diode D2 is connected to the anode of the power source Uin through the first inductor L11, and the cathode is connected to the fifth diode D5. One end of a first capacitor C1 is connected to the connection end of the first diode D1 and the second inductor L12, and the other end is connected to the connection end of the first inductor L11 and the second diode D2.
The first switch tube S1 and the second switch tube S2 are both NMOS tubes, and the respective sources of the first switch tube S1 and the second switch tube S2 are both connected to the negative electrode of the power source Uin; the drain of the first switch tube S1 is connected to the fourth diode D4 and the fourth inductor L22; the drain of the second switch tube S2 is connected to the connection end of the voltage boost unit 100 and the fifth diode D5.
Suppose that: the conduction voltage drop of the switch tube and each diode is zero, and the influence of parasitic resistance and capacitance of the switch tube and the diode is ignored. The capacitance is large enough, the four capacitance values are the same, the circuit operates in a continuous mode (CCM), the period of the first switch tube S1 and the second switch tube S2 is set to T, the duty ratio is D, the circuit mainly has three operating modes when the parasitic parameters of the switch tubes are not considered, and the main operating waveforms are shown in fig. 2. In fig. 2, US1 and US2 are voltages to which the switching tubes S1 and S2 are subjected when they are turned off. The iL11, iL12, iL21 and iL22 are currents in four inductors respectively. t1-t4 are time points.
The working principle is as follows:
in an operating mode 1[ t1-t2], the switching tubes S1 and S2 are simultaneously turned on, at the time, the diodes D1, D2, D3 and D4 are in a forward conducting state, and the diodes D5, D6, D7 and D8 are in a reverse blocking state. Under the action of an input voltage Uin, six loops of inductors L11, L12, L21 and L22 and capacitors C1 and C2 are charged in parallel. The current of the inductors L11, L12, L21, and L22 rises linearly, and the voltage of the capacitors C1 and C2 rises linearly. The voltages of the capacitors C3 and C4 are unchanged, the capacitors C5 and C6 supply power to the load R, the output voltage U0 at this time drops, and the operation mode is ended until the turn-off signal of S1 arrives, that is, at time t 2. The operation circuit of the operation mode 1 is shown in fig. 3.
Since the inductance L11 is the same as the inductance L12 is the same as the inductance L21 is the same as the inductance L22, when the switching tube S1 and the switching tube S2 are simultaneously turned on, the current changes in the inductances L11, L12, L21, and L22 are the same, and thus, the equations (1) and (2) can be obtained.
Figure BDA0003115282200000041
UC1＝UC2＝Uin (2)
Wherein di11/dt represents the current change of the inductor L11, di12/dt represents the current change of the inductor L12, di21/dt represents the current change of the inductor L21, and di22/dt represents the current change of the inductor L2.
In the working mode 2[ t2-t3], the switching tube S1 is turned off, and the switching tube S2 is turned on. At this time, the diodes D1, D2, D6, and D8 are in a forward conducting state, and the diodes D3, D4, D5, and D7 are in a reverse blocking state. Under the action of an input voltage Uin, three loops of inductors L11 and L12 and a capacitor C1 are charged in parallel. The current of the inductors L11 and L12 rises linearly, the voltage of the capacitor C1 rises linearly, Uin, L21, C2, L22, C4 and D8 form a loop, Uin, L21, C2, L22, C3, D6, C5 and S2 form a loop, and Uin, L21, C2, L22, C3, D6, C5, R, C6 and S2 form a loop. The inductors L11 and L12 release energy in this working mode, the current of the inductors L11 and L12 decreases, the capacitors C2, C3 and C6 are in a discharging state, the voltages of the capacitors C2, C3 and C6 decrease, the capacitors C4 and C5 are in a charging state, and the voltages of the capacitors C4 and C5 increase. The output voltage U0 rises at this time, and continues until the S2 shutdown signal arrives, that is, at time t3, and this operation mode ends. The operating circuit of the operating mode 2 is shown in fig. 4.
When L11 is equal to L12 is equal to L21 is equal to L22, switching tube S1 is turned off, and S2 is turned on. The following equations can be derived for the same current changes in the inductors L11 and L12 and the same current changes in the inductors L21 and L22.
Figure BDA0003115282200000051
Figure BDA0003115282200000052
Figure BDA0003115282200000053
Wherein, Uc3, Uc4 and Uc5 are the voltages of capacitors C3, C4 and C5 respectively.
In the working mode 3 t3-t4, the switching tube S1 is turned on, and the switching tube S2 is turned off. At this time, the diodes D3, D4, D5, and D7 are in a forward conducting state, and the diodes D1, D2, D6, and D8 are in a reverse blocking state. Under the action of an input voltage Uin, three loops of inductors L21 and L22 and a capacitor C2 are charged in parallel. The current of the inductors L21 and L22 rises linearly, the voltage of the capacitor C2 rises linearly, Uin, L11, C1, L12, D5, C3 and S1 form a loop, Uin, L11, C1, L12, C5, C6, D7, C4 and S1 form a loop, and Uin, L11, C1, L12, C5, R, D7, C4 and S1 form a loop. The inductors L21 and L22 release energy in the working mode, the currents of the inductors L21 and L22 drop, the capacitors C1, C4 and C5 are in a discharging state, the voltages of the capacitors C1, C4 and C5 drop, the capacitors C3 and C6 are in a charging state, and the voltages of the capacitors C3 and C6 rise. The output voltage U0 rises at this time, continues until time t4, and the operation mode ends, and then returns to operation mode 1. The operating circuit of the operating mode 3 is shown in fig. 5.
When L11 is equal to L12 is equal to L21 is equal to L22, switching tube S1 is turned off, and S2 is turned on. The following equations can be derived for the same current changes in the inductors L11 and L12 and the same current changes in the inductors L21 and L22.
Figure BDA0003115282200000061
Figure BDA0003115282200000062
Figure BDA0003115282200000063
Obtaining:
2UinD＝(UC3-2Uin)(1-D) (9)
2UinD＝(UC6-UC4-2Uin)(1-D) (10)
according to the voltage-second balance principle of the L21 and L22 inductors in the steady state, the method comprises the following steps:
2UinD＝(UC4-2Uin)(1-D) (11)
2UinD＝(UC5-UC3-2Uin)(1-D) (12)
the following equations (1) to (4) can be obtained:
Figure BDA0003115282200000064
Figure BDA0003115282200000065
Figure BDA0003115282200000066
the voltage gain is therefore:
Figure BDA0003115282200000067
therefore, higher gain can be realized under the condition of small duty ratio, the switching loss is effectively reduced, the generation of higher peak voltage is effectively inhibited, and the reverse recovery performance of the diode is effectively enhanced.
When the switch tube is turned off, the voltage stress of the switch device is as follows:
Figure BDA0003115282200000068
Figure BDA0003115282200000069
Figure BDA00031152822000000610
Figure BDA00031152822000000611
Figure BDA00031152822000000612
Figure BDA0003115282200000071
wherein, UL11 is inductor L11 voltage, UL12 is inductor L12 voltage, UL21 is inductor L21 voltage, and UL22 is inductor L22 voltage.
When one of the switch tubes S1 or S2 is turned off and the other is turned on, the voltage stress of the diode is:
Figure BDA0003115282200000072
Figure BDA0003115282200000073
Figure BDA0003115282200000074
Figure BDA0003115282200000075
when the switch tube S1 or S2 is turned on simultaneously, the voltage stress of the diode is:
Figure BDA0003115282200000076
Figure BDA0003115282200000077
Figure BDA0003115282200000078
Figure BDA0003115282200000079
the voltage stress of diodes D5-D8 takes on the larger value, namely:
Figure BDA00031152822000000710
Figure BDA00031152822000000711
US1 and US2 in equations (17) and (18) are voltages borne by the switching tubes S1 and S2 when the switching tubes are turned off, UD1-UD4 in equations (19) and (22) are reverse bearing voltages of the diodes D1-D4, and UD5-UD8 in equations (31) and (32) are reverse bearing voltages of the diodes D5-D8.
Therefore, under the condition that the duty ratio is the same, compared with the traditional Boos, the converter has the advantages that the voltage gain is high, the voltage stress of the switching tube and the voltage stress of the diode are lower, the switching loss is effectively reduced, and the transmission efficiency of the converter is improved.
According to the formulas (1), (3) and (6), the ripple of the inductive current is related to the input voltage, the duty ratio and the frequency of the switching tube, the four inductance values have the same value, the structure is symmetrical, and the ripples of the four inductance values are consistent.
Figure BDA00031152822000000712
Where Uin is the input voltage, D is the duty cycle, L is the inductance value, and f is the switching tube frequency.
In the application, the voltage gain is 8 times of that of a traditional Boost converter, so that the required voltage can be boosted only by low duty ratio, meanwhile, the frequency of a switching tube of the converter designed in the application is 100kHz, the frequency of the switching tube is high, and according to the formula (33), the lower the duty ratio is, the higher the frequency of the switching tube is, and the smaller the ripple of the inductive current is. The inductor current ripple of the present application is small relative to the inductor current ripple of a typical non-isolated high gain DC-DC converter.
To sum up, the utility model overcomes the shortcoming that traditional Boost converter voltage gain is low and switching stress is big. The voltage gain is 8 times of that of the traditional Boost converter, the use of limit duty ratio is avoided, the switching loss is reduced, and the photovoltaic power generation device is very suitable for photovoltaic power generation. Compared with the topological structure of most high-gain DC-DC converters, the voltage stress of the switching tube and the voltage stress of the diode are greatly reduced. The voltage stress of the switching tube is only 1/4 of the output voltage, the voltage stress of the diode is only 1/2 of the output voltage at most, and in the case that the duty ratio D is 0.6, the voltage stress of the diode is only 1/10 of the output voltage at least. The low switching stress can adopt a low-voltage-resistant switching tube and a diode, thereby effectively reducing the switching loss and the cost. And the ripple of the input current is low and the ripple of the output voltage is also low.
The above embodiments are provided only for the purpose of illustration, not for the limitation of the present invention, and those skilled in the relevant art can make various changes or modifications without departing from the spirit and scope of the present invention, therefore, all equivalent technical solutions should also belong to the scope of the present invention, and should be defined by the claims.

Claims (4)

1. A high-gain non-isolated DC-DC conversion circuit connected to a power supply, comprising: the first capacitor is connected with the first diode, the second capacitor is connected with the second diode, the third capacitor is connected with the second capacitor, the fourth capacitor is connected with the third diode, the second capacitor is connected with the eighth capacitor, the third inductor is connected with the fourth inductor, the first switch tube is connected with the second switch tube, the resistor and the booster circuit;
the power supply, the booster circuit, the fifth diode, the sixth diode, the resistor, the seventh diode and the eighth diode are sequentially connected in series to form a loop;
the power supply, the third diode, the fourth inductor and the first switching tube are connected in series in sequence to form a loop;
the power supply, the third inductor, the fourth diode and the first switching tube are sequentially connected in series to form a loop, and the fourth diode and the fourth inductor are connected with the same end of the first switching tube;
one end of the second capacitor is connected with the connection end of the third diode and the fourth inductor, and the other end of the second capacitor is connected with the connection end of the third inductor and the fourth diode;
two ends of the series branch of the third capacitor and the fourth capacitor are respectively connected with the connection end of the fifth diode and the sixth diode and the connection end of the seventh diode and the eighth diode;
a series branch of the fifth capacitor and the sixth capacitor is connected with the resistor in parallel;
two ends of the second switch tube are respectively connected with the connection end of the booster circuit and the fifth diode, and the connection end of the eighth diode and the power supply;
the connection end of the boosting circuit and the fifth diode is connected with the connection ends of the fifth capacitor and the sixth capacitor;
and the connection end of the fourth inductor and the fourth diode is connected with the connection end of the third capacitor and the fourth capacitor.
2. The high-gain non-isolated DC-DC converter circuit according to claim 1, wherein the positive terminal of the power supply is connected to the voltage boosting circuit, the cathode of the fifth diode is connected to the anode of the sixth diode, and the cathode of the seventh diode is connected to the anode of the eighth diode;
the anode of the power supply is connected with the anode of the third diode;
one end of the third inductor is connected with the positive electrode of the power supply, and the other end of the third inductor is connected with the anode of the fourth diode.
3. The high-gain non-isolated DC-DC converter circuit according to claim 1 or 2, wherein the voltage boosting circuit comprises: a first capacitor, a first inductor, a second inductor, a first diode and a second diode,
the anode of the first diode is connected with the positive electrode of the power supply, and the cathode of the first diode is connected with the fifth diode through the second inductor;
the anode of the second diode is connected with the anode of the power supply through the first inductor, and the cathode of the second diode is connected with the fifth diode;
one end of the first capacitor is connected with the connection end of the first diode and the second inductor, and the other end of the first capacitor is connected with the connection end of the first inductor and the second diode.
4. The high-gain non-isolated DC-DC conversion circuit according to claim 1 or 2, wherein the first switch tube and the second switch tube are NMOS tubes, and the sources of the first switch tube and the second switch tube are connected to the negative electrode of the power supply; the drain electrode of the first switching tube is connected with the fourth diode and the fourth inductor; and the drain electrode of the second switching tube is connected with the connection end of the boosting circuit and the fifth diode.
CN202121331898.2U 2021-06-15 2021-06-15 High-gain non-isolated DC-DC conversion circuit Expired - Fee Related CN214756073U (en)

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