CN213152009U - Self-adaptive phase difference driving circuit applied to ultrasonic transducer - Google Patents
Self-adaptive phase difference driving circuit applied to ultrasonic transducer Download PDFInfo
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- CN213152009U CN213152009U CN202022580613.0U CN202022580613U CN213152009U CN 213152009 U CN213152009 U CN 213152009U CN 202022580613 U CN202022580613 U CN 202022580613U CN 213152009 U CN213152009 U CN 213152009U
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Abstract
The utility model relates to a be applied to ultrasonic transducer's self-adaptation phase difference drive circuit. The power conversion module in the utility model is used for providing driving voltage and current for the ultrasonic transducer, and comprises a rectifier bridge circuit, a voltage reduction circuit, a full bridge circuit and an LC resonance matching circuit; the voltage and current sampling and converting module is used for collecting the voltage and the current of the transducer and converting the voltage and the current analog quantity into digital quantity; the phase difference conversion circuit module is used for converting the digital quantity into a phase difference, namely a pulse signal; the MOS drive circuit receives the output from the phase difference conversion circuit and is used for controlling the conduction and the disconnection of the field effect transistor in the full bridge circuit so as to realize the control of the output frequency of the power conversion module. The utility model discloses the phase difference signal direct conversion of the transducer voltage signal and the current signal of sampling is drive circuit's input signal, has reduced the control time delay of system.
Description
Technical Field
The utility model belongs to the technical field of electronic equipment, in particular to be applied to ultrasonic transducer's self-adaptation phase difference drive circuit.
Background
With the development of manufacturing industry, ultrasonic precision machining becomes an important technology in the current industrial machining field. The most central part of the ultrasonic precision machining technology is an ultrasonic generator, namely an ultrasonic transducer driving power supply. An ultrasonic transducer is also called an ultrasonic sensor and is a device capable of realizing energy form conversion. An ultrasonic transducer driving power supply is a device for generating an excitation signal and supplying ultrasonic energy to the transducer. According to the requirements of the transducer and the characteristic that the impedance of the transducer at the resonant frequency is the lowest, the transducer driving power supply needs to control the phase difference between the voltage and the current output by the power supply according to the actual resonant frequency of the transducer, and when the phase difference between the voltage and the current is zero, the transducer can obtain the maximum output power.
In the field of industrial automation, ultrasonic cleaning machines, ultrasonic welding machines, ultrasonic atomizers, ultrasonic range finders, ultrasonic flaw detectors and other instruments are continuously invented, and meanwhile, the development of ultrasonic technology is greatly promoted, so that the application of the ultrasonic technology to the field of finish machining becomes possible. But compared with equipment such as an ultrasonic cleaning machine and an ultrasonic welding machine, the ultrasonic transducer driving power supply required by the ultrasonic processing machine tool is higher in power and higher in requirements on stability and reliability.
The ultrasonic driving power supply mainly comprises two driving modes of self-excitation and independent excitation. Self-excitation is a driving mode which leads the circuit to tend to be stable by utilizing continuous oscillation under the condition that a positive feedback network keeps the amplitude and the phase of the circuit balanced according to the principle of self-excitation oscillation of the circuit under the action of signals in the circuit; the independent excitation means that an independent oscillator is arranged in the power supply, and the output frequency of the power supply is determined by adopting a frequency tracking or frequency scanning mode.
Because the self-excitation mode has no control unit, under the action of environmental noise, the stability of the output frequency is poor, the ultrasonic drive power supply in the current industrial automation field is driven by adopting the independent excitation mode, but when the ultrasonic drive power supply is driven by the independent excitation mode, the control module needs to adjust the output frequency of the power supply by acquiring and processing the voltage and the current of the transducer in real time, the control module needs to spend time on processing the sampled voltage and current data, and the adjustment of the output frequency of the power supply has a part of time delay relative to the change of the actual working frequency of the transducer.
Disclosure of Invention
The to-be-solved technical problem of the utility model is: aiming at the defects in the prior art, the self-excitation driving mode and the independent excitation driving mode are combined, and the self-adaptive phase difference driving circuit applied to the ultrasonic transducer is provided.
The utility model adopts the technical proposal that:
the utility model comprises a power conversion module, a voltage and current sampling conversion module, a phase difference conversion circuit module, a MOS drive circuit module and an AC-DC module;
the power conversion module is used for providing driving voltage and current for the ultrasonic transducer and comprises a rectifier bridge circuit, a voltage reduction circuit, a full bridge circuit and an LC resonance matching circuit;
the voltage and current sampling and converting module is used for collecting the voltage and the current of the transducer and converting the voltage and the current analog quantity into digital quantity;
the phase difference conversion circuit module is used for converting the digital quantity into a phase difference, namely a pulse signal;
the MOS driving circuit receives the output from the phase difference conversion circuit and is used for controlling the conduction and the disconnection of the field effect transistor in the full-bridge circuit so as to realize the control of the output frequency of the power conversion module;
the AC-DC module is used for supplying power to the MOS drive circuit module.
Furthermore, the MOS drive circuit is provided with a peripheral IGBT, the peripheral IGBT is connected with an oscillation resistor in the MOS drive circuit in parallel, and the on-resistance of the peripheral IGBT is changed through an input pulse signal, so that the resistance value of the oscillation resistor is changed, and the pulse width modulation of an output signal of the MOS drive circuit is realized.
The utility model has the advantages that:
1) the utility model directly converts the phase difference signal of the sampled voltage signal and the current signal of the transducer into the input signal of the driving circuit, and compared with the traditional singlechip which processes the sampled voltage signal and the sampled current signal of the transducer and then outputs the pulse width modulation signal to control the driving circuit, the control time delay of the system is reduced;
2) the utility model innovatively adjusts the external oscillation resistance value of the driving circuit by changing the on-state internal resistance of the IGBT, and has higher precision compared with the mode of directly adjusting the external oscillation resistance value by using a potentiometer;
3) the utility model discloses innovatively adopt analog switch to realize the drive control to the field effect transistor in the full-bridge circuit with voltage signal and current signal conversion for the phase difference signal.
Drawings
Fig. 1 is a schematic diagram of the system structure of the present invention;
fig. 2 is a schematic diagram of a power conversion module of the present invention;
fig. 3 is a schematic diagram of a voltage current sampling circuit module according to the present invention;
fig. 4 is a schematic diagram of an a/D conversion circuit module of the present invention;
fig. 5 is a schematic diagram of a MOS driver module of the present invention;
fig. 6 is a schematic diagram of an AC-DC module of the present invention.
Detailed Description
The working principle of the present invention is further explained by the following specific embodiments, and the parameters marked in the drawings are preferred parameters selected by the embodiments, not limitations to the protection scope of the present invention.
The utility model discloses general concept: the utility model discloses pass through the analog quantity of the voltage of the transducer and the electric current of gathering circuit conversion to the digital quantity, then obtain its phase difference, pulse signal through analog switch with the digital quantity of the voltage that the conversion obtained and electric current. The pulse signal is used as a control signal of the IGBT to adjust the conduction degree of the IGBT, and the conduction internal resistance of the IGBT can change linearly along with the width of the pulse signal, so that the resistance value of the oscillation resistor of the MOS drive circuit is adjusted, the output signal of the MOS drive circuit is changed, the on and off of the field effect transistor of the power conversion module of the driving power supply of the ultrasonic transducer are controlled, and the control of the output frequency of the power supply is realized.
The utility model discloses an overall structure is as shown in fig. 1, mainly includes power conversion module 1, voltage current sampling conversion module 2, phase difference converting circuit module 3, MOS drive circuit module 4 and AC-DC module 5. In order to provide reliable and stable driving voltage and current for an ultrasonic transducer applied to the field of ultrasonic precision machining, the utility model designs a circuit structure as shown in figure 1, a power conversion module 1 mainly realizes the function of electric energy conversion, firstly, 220V/50Hz alternating current is converted into direct current voltage through a rectifier bridge circuit, the direct current voltage obtained by rectification is too high and can not be directly converted into alternating current voltage with the same working frequency of the transducer, so voltage reduction is needed through a voltage reduction circuit, then, the direct current voltage after voltage reduction is converted into high-frequency alternating current voltage through a full bridge circuit consisting of four field effect transistors, the high-frequency alternating current voltage is provided for the ultrasonic transducer through an LC resonance matching circuit, because the impedance characteristic of the transducer can be changed under the loading state, the LC resonance matching circuit is used for matching the transducer and an ultrasonic driving power supply, so that the impedance of the transducer becomes optimally loaded. The voltage and current sampling conversion module 2 is used for sampling the real-time working voltage and current of the transducer, and the phase difference conversion circuit module 3 is used for converting the voltage and current analog quantity sampled by the voltage and current sampling conversion module 2 into digital quantity and obtaining a phase difference signal; the MOS driving circuit module 4 takes the phase difference signal output by the phase difference conversion circuit module 3 as an input signal, the peripheral IGBT is connected with the oscillation resistor of the MOS driving circuit in parallel, the conduction internal resistance of the peripheral IGBT is changed through the input phase difference signal, so that the resistance value of the oscillation resistor is changed, the pulse width modulation of the MOS driving signal is realized, and a proper control signal is provided for the conduction and the turn-off of a field effect transistor (MOS tube); the AC-DC module 5 is used for converting the output 220V/50Hz alternating current into 12V direct current to supply power for the driving chip.
As shown in fig. 2, a schematic circuit diagram of the power conversion module 1 is that 220V/50Hz alternating current is connected to the power conversion module 1 through an alternating current connection socket AC-PWR, an L, N pin of the AC-PWR socket is connected to an alternating current input terminal of a rectifier bridge B1, and a positive electrode of a direct current output terminal of the rectifier bridge B1 is connected to one end of a capacitor C26, one end of a capacitor C27, one end of a resistor R59 and a drain D of a field effect transistor Q3; the cathode of the direct-current output end of the rectifier bridge B1 is connected with the other end of the capacitor C26, the other end of the capacitor C27, the anode of the diode D10, one end of the capacitor C25, the source S of the field-effect transistor Q4, one end of the capacitor C31, the source S of the field-effect transistor Q5 and one end of the capacitor C32; the other end of the resistor R59 is connected with one end of a capacitor C24; the other end of the capacitor C24 is connected with the source S of the field effect transistor Q3, one end of the inductor L2 and the cathode of the diode D10; the other end of the inductor L2 is connected with the other end of the capacitor C25, the drain D of the field effect transistor Q1, one end of the resistor R60, the drain D of the field effect transistor Q2 and one end of the R61; the other end of the resistor R60 is connected with one end of the capacitor C28; the other end of the resistor R61 is connected with a capacitor C29; the other end of the capacitor C32 is connected with a resistor R63; the other end of the capacitor C31 is connected with one end of a resistor R62, and the other end of the resistor R62 is connected with the drain D of the field effect transistor Q4, the source S of the field effect transistor Q1, the other end of the capacitor C28 and one end of the capacitor C30; the drain D of the field effect transistor Q5 is connected with the other end of the resistor R63, the different name input end of the isolation transformer T4, the source S of the field effect transistor Q2 and the other end of the capacitor C29; the other end of the capacitor C30 is connected with the homonymous input end of an isolation transformer T4; the output same-name end of the isolation transformer is connected with one end of an inductor L3, and the other end of the inductor L3 is connected with a pin 1 of a transducer wiring terminal H1; the output alias terminal of isolation transformer T4 is connected to pin 2 of transducer terminal H1.
The utility model discloses a voltage current sampling module 2 constitutes full wave rectifier circuit through operational amplifier and triode, converts the transducer voltage and the current signal of sampling into transducer voltage full wave rectification signal V _ AS and current full wave rectification signal I _ AS.
A voltage-current sampling conversion module 2 is shown in a schematic circuit diagram of fig. 3, wherein V-TL + and I-TL + represent analog quantities of sampled transducer voltage and current signals, V-TL1+ is connected with one end of a resistor R10, the other end of the resistor R10 is connected with one end of a resistor R16 and a pin 1 of a PNP triode QP2, and the other end of the resistor R16 and a pin 3 of the PNP triode QP2 are grounded; a pin 2 of the PNP triode QP2 is connected to one end of the resistor R6 and a pin 1 of the NPN triode QN2, the other end of the resistor R6 is connected to the positive electrode VCC12V of the 12V dc power supply and a pin 3 of the NPN triode QN2, a pin 2 of the NPN triode QN2 is connected to one end of the resistor R15, one end of the resistor R9 and one end of the resistor R12, and the other end of the resistor R15 is grounded; one end of the resistor R14 is connected with the other end of the resistor R9, the other end of the resistor R12 and one end of the resistor R8, and the other end of the resistor R14 is grounded; the other end of the resistor R8 is connected with one end of a resistor R13 and a pin 1 of the PNP triode QP1, and the other end of the resistor R13 and a pin 3 of the PNP triode QP1 are grounded; a pin 2 of the PNP triode QP1 is connected with a pin 14 of the output end of the operational amplifier LM239DRG3, one end of a resistor R1 and one end of a resistor R2; the other end of the resistor R1 is connected with the positive electrode of VCC 12V; the other end of the resistor R2 is connected with a pin 1 of an NPN triode QN1, a pin 3 of an NPN triode QN1 is connected with the anode of a VCC12V, a pin 2 of the NPN triode QN1 OUTPUTs a full-wave rectification signal V _ AS of the voltage of the transducer, a pin 8 of an inverting input end of an operational amplifier LM239DRG3 is connected with one end of a resistor R64 and a pin 6 of an inverting input end of the operational amplifier, and the other end of the resistor R64 is connected with a pin 4 oscillation OUTPUT signal OSC _ OUTPUT of a transistor driver SG2525AP103TR and used for full-wave rectification of the voltage and the current of the feedback control transducer; a pin 9 at the non-inverting input end of the operational amplifier LM239DRG3 is connected with one end of a resistor R65, one end of a resistor R66 and a pin 7 at the non-inverting input end of the operational amplifier LM239DRG3, and the other end of the resistor R65 is connected with the positive electrode of a VCC5V direct-current power supply; the other end of the resistor R66 is grounded; a pin 1 at the output end of the operational amplifier LM239DRG3 is connected with one end of a resistor R25, one end of a resistor R29 and a pin 2 of a PNP triode QP3, the other end of the resistor R29 is connected with a pin 1 of an NPN triode QN3, the other end of the resistor R25 and a pin 3 of the NPN triode QN3 are connected with VCC12V, and a pin 2 of an NPN triode QN3 is connected with one end of the resistor R34 and outputs a full-wave rectification signal I _ AS of the transducer current; a pin 1 of the NP triode QP3 is connected with one end of a resistor R33 and one end of a resistor R32; the other end of the resistor R32 inputs a sampled transducer current signal I-T _ O2 +; the other end of the resistor R33 and the other end of the resistor R34 are grounded.
The utility model discloses a phase difference converting circuit module 3, the transducer voltage full wave rectification signal V _ AS and the current full wave rectification signal I _ AS who outputs voltage current sampling module 2 convert transducer voltage current phase difference signal output into through analog switch CD4016 BM.
AS shown in fig. 4, the phase difference conversion circuit module 3 is a schematic circuit diagram, wherein a transducer voltage full-wave rectification signal V _ AS is connected to one end of a resistor R3, the other end of the resistor R3 is connected to the anode of a diode D1, the cathode of a diode D2 and one end of a resistor R20, the cathode of a diode D1 is connected to VCC12V, and the anode of a diode D2 is grounded; the other end of the resistor R20 is connected with pin 1 of the analog switch chip CD4016 BM; the transducer current full-wave rectification signal I _ AS is connected with one end of a resistor R21, the other end of a resistor R21 is connected with the anode of a diode D3, the cathode of a diode D4 and one end of a resistor R22, the cathode of a diode D3 is connected with VCC12V, and the anode of a diode D4 is grounded; the other end of the resistor R22 is connected with the pin 8 of the analog switch chip CD4016 BM; VCC5V is connected with one end of a resistor R27, and the other end of the resistor R27 is connected with a pin 11 of an analog switch chip CD4016 BM; VCC12V is connected with one end of a resistor R30, and the other end of the resistor R30 is connected with pins 12, 6 and 13 of an analog switch chip CD4016 BM; a pin 14 of the analog switch chip CD4016BM is connected with one end of a resistor R18 and one end of a capacitor C2, the other end of the capacitor C2 is grounded, and the other end of the resistor R18 is connected with the positive electrode of a VCC12V direct-current power supply; VCC5V is connected with one end of a resistor R7, the other end of the resistor R7 is connected with a pin 5 at the non-inverting input end of the operational amplifier LM224DR and the resistor R17, and the other end of the resistor R17 is grounded; the inverting input end 6 pin of the operational amplifier LM224DR is connected with one end of a resistor R4, the other end of the resistor R4 is connected with the output end 7 pin of the LM224DR, one end of a capacitor C1 and one end of a resistor R11, the other end of the capacitor C1 is grounded, the other end of the resistor R11 is connected with one end of a resistor R5 and the inverting input end 9 pin of the LM224DR, the other end of the resistor R5 is connected with the output end 8 pin of the LM224DR and one end of the resistor R19 to serve as phase difference of voltage signals and current signals and record as Control; the other end of the resistor R19 is grounded; the pin 10 of the non-inverting input end of the LM224DR is connected with one end of a resistor R24 and one end of a resistor R26, the other end of the resistor R26 is grounded, the other end of the resistor R24 is connected with one end of a capacitor C3, one end of a resistor R23, one end of a resistor R28 and one end of a resistor R31, and the other end of the capacitor C3 is grounded; the other end of the resistor R23 is connected with a pin 2 of an analog switch chip CD4016 BM; the other end of the resistor R28 is connected with a pin 10 of an analog switch chip CD4016 BM; the other end of the resistor R31 is connected with a pin 9 of an analog switch chip CD4016 BM; pins 3, 4, 5 and 7 of the analog switch chip CD4016BM are connected and grounded.
The utility model discloses a MOS drive circuit module 4, with input signal Control as IGBT's Control signal, along with input signal's change, IGBT (QM 2) switch on internal resistance linear variation, QM2 and transistor driver SG2525AP103TR external resistance R50, R51 constitute oscillating resistance RT in parallel. RT changes linearly with the on-resistance of the IGBT (QM 2), thereby changing the MOS drive signal output by the drive circuit.
As shown in fig. 5, the circuit schematic diagram of the MOS drive circuit module 4 is that a transducer voltage-current phase difference signal Control output by the phase difference conversion circuit module 3 is connected to one end of a resistor R54, the other end of the resistor R54 is connected to one end of a capacitor C23 and one end of a resistor R55, and the other end of the capacitor C23 is grounded; the other end of the resistor R55 is connected with pin 1 of the IGBT QM2, pin 2 of the IGBT QM2 is connected with one end of the resistor R58, and the other end of the resistor R58 is grounded; the 3 pins of the IGBT QM2 are connected with one end of a resistor R50, one end of a resistor R51, the 3 pins of the IGBT QM1 and the 6 pins of a transistor driving chip SG2525AP013 TR; the other end of the resistor R50 is connected with pin 3 of the variable resistor RP1, and pin 2 of the variable resistor RP1 is connected with pin 1 and is grounded; the other end of the resistor R51 is connected with the resistor R57, and the other end of the resistor R57 is grounded; a pin 9 of the transistor driving chip SG2525AP013TR is connected with one end of a capacitor C16, and the other end of the capacitor C16 is grounded; a pin 10 of the transistor driving chip SG2525AP013TR is connected to one end of the capacitor C13 and one end of the resistor R48, and the other end of the capacitor C13 is grounded to the other end of the resistor R48; a pin 11 of the transistor driving chip SG2525AP013TR outputs a MOS transistor driving signal U2_ output; the 12 pin of the transistor driving chip SG2525AP013TR is grounded; a pin 13 of the transistor driving chip SG2525AP013TR is connected to a pin 15 of the transistor driving chip SG2525AP013TR, one end of the resistor R36, one end of the resistor R37 and one end of the capacitor C4; the other end of the capacitor C4 is connected with a pin 3 of the voltage reference chip IC1 and one end of the resistor R39 and is grounded; the other end of the resistor R36 is connected with the other end of the resistor R37 and the positive electrode of the VCC12V power supply; a pin 14 of the transistor driving chip SG2525AP013TR is connected to one end of a resistor R45, one end of a resistor R44 and one end of a resistor R42, the other end of the resistor R45 is connected to one end of a resistor R46, the other end of the resistor R46 is connected to the other end of the resistor R44 and to ground (not shown), and the other end of the resistor R42 is connected to the positive terminal of the VCC12V power supply; the 16 pins of the transistor driving chip SG2525AP013TR are connected with one end of the resistor R35, one end of the resistor R38 and one end of the resistor R43; the other end of the resistor R35 is connected with a pin 2 of the voltage reference chip IC1 and a pin 1 of the IGBT QM 1; pin 1 of the voltage reference chip IC1, pin 2 of the IGBT QM1 and the other end of the resistor R39 are connected; the 3 pins of the IGBT QM1 are connected with the 6 pins of a transistor driving chip SG2525AP013 TR; the other end of the resistor R38 is connected with one end of a resistor R41, one end of a capacitor C7 and a pin 1 of a transistor driving chip SG2525AP013 TR; the other end of the capacitor C7 and the other end of the resistor R41 are grounded; the other end of the resistor R43 is connected with a pin 2 of the transistor driving chip SG2525AP013 TR; the 4 OUTPUT oscillation signal OSC _ OUTPUT of the transistor driving chip SG2525AP013 TR; a pin 5 of the transistor driving chip SG2525AP013TR is connected to one end of a capacitor C9 and one end of a resistor R47, the other end of the capacitor C9 is grounded, and the other end of the resistor R47 is connected to a pin 7 of the transistor driving chip SG2525AP013 TR; the pin 8 of the transistor driving chip SG2525AP013TR is connected to one end of the capacitor C17 and one end of the capacitor C18, and the other end of the capacitor C17 is connected to the other end of the capacitor C18 and is grounded.
The utility model discloses a AC-DC module 5, the mode through switching power supply is the operational amplifier in the system, analog switch and driver chip power supply, its circuit structure is shown in FIG. 6, reference numeral L, N represents live wire and the zero line of 220V alternating current respectively, as the input of AC-DC module 5, reference numeral L links to each other with thermistor NTC1 one end, the thermistor NTC1 other end links to each other with 4 feet of common mode inductance TL1, 3 feet and X electric capacity Cx1 one end of common mode inductance TL1, 1 foot of rectifier bridge D6 link to each other; the reference number N is connected with pin 1 of the common-mode inductor TL1, and pin 2 of the common-mode inductor TL1 is connected with the other end of the X capacitor Cx1 and pin 2 of the rectifier bridge D6; a pin 3 of the rectifier bridge D6 is connected with one end of a filter capacitor C12, the anode of a transient suppression diode TVS1 and a pin 1 of a high-frequency transformer T1; a pin 4 of the common-mode inductor TL1 is connected with the other end of the filter capacitor C12, pins 5, 6, 7 and 8 of the switching tube power supply chip U3, one end of the capacitor C21 and a pin 3 of the optical coupler U4 and connected with a simulated ground PGND; the other end of the capacitor C21 is connected with a pin 2 of a switching tube power supply chip U3; a pin 1 of the switching tube power supply chip U3 is connected with a pin 4 of the optocoupler U4; the cathode of the transient suppression diode TVS1 is connected with the cathode of the diode D8; the anode of the diode D8 is connected with the 4 pin of the switching tube power chip U3 and the 2 pin of the high-frequency transformer T1; a pin 6 of the high-frequency transformer T1 is connected with the anode of a diode D5, the cathode of a diode D5 is connected with the anode of an electrolytic capacitor C5, one end of the capacitor C6 and one end of a resistor R40 to serve as the anode of a 12V power supply output and to be recorded as VCC12V, a pin 7 of the high-frequency transformer T1 is connected with the cathode of the electrolytic capacitor C5, the other end of the capacitor C6 and the other end of the resistor R40 to serve as the cathode of the 12V power supply output and to be grounded; a pin 9 of the high-frequency transformer T1 is connected with the anode of a diode D7; the cathode of the diode D7 is connected with the anode of the electrolytic capacitor C8, one end of the capacitor C10 and the 1 pin of the 5V voltage-stabilizing chip IC2, the 3 pin of the 5V voltage-stabilizing chip IC2 is connected with one end of the capacitor C11, and the anode is used as the 5V power supply and is marked as VCC 5V; a pin 10 of the high-frequency transformer T1 is connected with the negative electrode of the electrolytic capacitor C8, the other end of the capacitor C10, a pin 2 of the 5V voltage-stabilizing chip IC2 and the other end of the capacitor C11 and is grounded; the 4 feet of the high-frequency transformer T1 are connected with the anode of a diode D9; one end of a resistor R52 and the cathode of a diode D9 are connected with the anode of an electrolytic capacitor C14, one end of a capacitor C19 and one end of an inductor L1, the other end of an inductor L1 is connected with the anode of an electrolytic capacitor C15, one end of a resistor R49 and one end of a capacitor C20, and the resistor R52 and the anode of the capacitor C15 are used as the anode of a digital power supply 5V and are marked as VDD + 5V; the pin 5 of the high-frequency transformer T1 is connected with the negative electrode of the electrolytic capacitor C14, the other end of the capacitor C19, the negative electrode of the electrolytic capacitor C15 and the other end of the capacitor C20 and is grounded; one end of the resistor R53 is connected with the cathode of the electrolytic capacitor C15 and the pin 3 of the 2.5V voltage reference chip U5; the other end of the resistor R53 is connected with the other end of the resistor R49, one end of the capacitor C22 and a pin 1 of the 2.5V voltage reference chip U5; the other end of the capacitor C22 is connected with one end of a resistor R56, a pin 2 of the optocoupler U4 and a pin 2 of a 2.5V voltage reference chip U5; the other end of the resistor R56 is connected with the other end of the resistor R52 and a pin 1 of the optocoupler U4.
Claims (2)
1. The utility model provides a be applied to ultrasonic transducer's self-adaptation phase difference drive circuit, includes power conversion module, voltage current sampling conversion module, phase difference conversion circuit module, MOS drive circuit module and AC-DC module, its characterized in that:
the power conversion module is used for providing driving voltage and current for the ultrasonic transducer and comprises a rectifier bridge circuit, a voltage reduction circuit, a full bridge circuit and an LC resonance matching circuit;
the voltage and current sampling and converting module is used for collecting the voltage and the current of the transducer and converting the voltage and the current analog quantity into digital quantity;
the phase difference conversion circuit module is used for converting the digital quantity into a phase difference, namely a pulse signal;
the MOS driving circuit receives the output from the phase difference conversion circuit and is used for controlling the conduction and the disconnection of the field effect transistor in the full-bridge circuit so as to realize the control of the output frequency of the power conversion module;
the AC-DC module is used for supplying power to the MOS drive circuit module.
2. The adaptive phase difference driving circuit applied to the ultrasonic transducer is characterized in that the MOS driving circuit is provided with a peripheral IGBT, the peripheral IGBT is connected with an oscillating resistor in the MOS driving circuit in parallel, and the on-state internal resistance of the peripheral IGBT is changed through an input pulse signal, so that the resistance value of the oscillating resistor is changed, and the pulse width modulation of an output signal of the MOS driving circuit is realized.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202022580613.0U CN213152009U (en) | 2020-11-10 | 2020-11-10 | Self-adaptive phase difference driving circuit applied to ultrasonic transducer |
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202022580613.0U CN213152009U (en) | 2020-11-10 | 2020-11-10 | Self-adaptive phase difference driving circuit applied to ultrasonic transducer |
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| CN213152009U true CN213152009U (en) | 2021-05-07 |
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN113904569A (en) * | 2021-10-20 | 2022-01-07 | 杭州茂葳科技有限公司 | Ultrasonic drive circuit |
| CN116351686A (en) * | 2023-04-04 | 2023-06-30 | 重庆科技学院 | Variable-pressure variable-frequency ultrasonic cleaning machine generator and control method |
-
2020
- 2020-11-10 CN CN202022580613.0U patent/CN213152009U/en active Active
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN113904569A (en) * | 2021-10-20 | 2022-01-07 | 杭州茂葳科技有限公司 | Ultrasonic drive circuit |
| CN116351686A (en) * | 2023-04-04 | 2023-06-30 | 重庆科技学院 | Variable-pressure variable-frequency ultrasonic cleaning machine generator and control method |
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