CN209860803U - Non-contact single-tube resonant converter - Google Patents
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Abstract
The utility model discloses a non-contact single-tube resonant converter, which comprises a primary side and a secondary side; wherein: the primary side comprises a resonance inversion module; the resonance inversion module comprises a primary side inductor, a switching tube, a resonant capacitor and a capacitor, wherein the primary side inductor and the switching tube are connected in series and then connected in parallel at two ends of an input voltage; the secondary side comprises a secondary side inductor, a high-order compensation network and a rectification module which are connected in sequence. The utility model provides a different parallel connection method of primary resonance electric capacity and secondary adopt high-order compensation network, not only can realize accurate constant current output, provide good closed loop regulation characteristic for wireless charging, have realized the soft opening of switch tube moreover, have reduced switch tube voltage stress and current stress, have increased the parameter design degree of freedom; the secondary side rectifier bridge can adopt a controllable rectifier bridge structure, and the load of the rectifier bridge is adjusted to be pure resistance under the given control method, so that the power transmission capability of the proposed topology is improved.
Description
Technical Field
The utility model relates to a non-contact single tube resonant converter belongs to the wireless technical field that charges.
Background
Wireless Power Transmission (WPT) has been applied to the fields of electric vehicles, Automated Guided Vehicles (AGVs), unmanned aerial vehicles, automatic driving, and the like, especially in situations where automatic charging and manual charging are required. Compared with contact power supply, wireless power supply has the advantages of safety, flexibility, no spark, less maintenance, mobility, easiness in automation realization and the like.
The WPT mainly realizes non-contact energy Transmission by inductive coupling energy Transmission (ICPT), electromagnetic-coupling resonance energy Transmission (ERPT), Radio Frequency energy Transmission (RFPT), Microwave energy Transmission (MPT), Laser energy Transmission (LPT), and the like. Among them, ICPT is the most widely used WPT system.
Inversion is one of the essential links of ICPT, and the most common inversion topologies are all of multi-tube structures. However, for medium and small power occasions, the multi-tube inversion has high cost, complex driving and low cost performance, so that the single-tube inversion with low cost and simple driving becomes a more preferable choice for the medium and small power occasions. The particularity of single-tube inversion lies in that the conversion of DC/AC is realized by means of a resonance process, so that the voltage stress of a switching tube is high, and the analysis is difficult.
The existing research shows that the non-contact single tube circuit has two types, namely Class-E and resonant flyback, wherein the Class-E has low application value due to the voltage stress of a switching tube which is more than 4 times of the input voltage. The existing non-contact resonant flyback circuit (hereinafter referred to as a non-contact single-tube resonant converter) has two compensation modes of series compensation and parallel compensation on the secondary side. The series compensation and the parallel compensation have no parameter design freedom degree, which is not in accordance with the actual application requirement; the parallel compensation presents capacitive secondary side folded impedance, so that the voltage stress and the current stress of the switching tube are both larger, wherein the voltage stress is more than 3 times of the input voltage. The bus voltage of the product PFC module is about 400V generally, and the voltage stress of more than 3 times of the input voltage greatly reduces the model selection range of the switch tube. Therefore, in order to improve the application value of the non-contact single-tube circuit, it is necessary to achieve good output characteristics, appropriately reduce the voltage stress and the current stress of the switching tube, and increase the degree of freedom in parameter design.
Disclosure of Invention
The purpose of the invention is as follows: aiming at the prior art, the non-contact single-tube resonant converter is provided, the output quasi-constant current characteristic is realized, the voltage stress of a switching tube is improved, and the parameter design freedom degree is increased.
The technical scheme is as follows: a non-contact single-tube resonant converter comprises a primary side and a secondary side; wherein: the primary side comprises a resonance inversion module; the resonance inversion module comprises a primary side inductor LpA switching tube S, the primary side inductor LpIs connected in series with the switching tube S and then connected in parallel with the input voltage VinTwo ends, and a primary side inductor LpAnd/or the switch tube S is respectively connected with a resonance capacitor in parallel; the secondary side comprises secondary side inductors L connected in sequencesThe high-order compensation network and the rectification module.
Further, the high-order compensation network is composed of a compensation capacitor C1And a compensation capacitor C2Resonant inductor L2The secondary side inductor LsAnd a compensation capacitor C1After being connected in series, the compensating capacitor C2Connected in parallel and then with the resonant inductor L2Are connected in series.
Further, the high-order compensation network is composed of a compensation capacitor C and a resonance inductor L2The secondary side inductor LsConnected in parallel with the compensation capacitor C and then connected with the resonance inductor L2Are connected in series.
Further, the rectifier module comprises a rectifier and a filter, the rectifier is full-bridge rectification or current-doubling rectification or voltage-doubling rectification, and the filter is LC filtering or C filtering.
Further, the rectifier is a controllable rectifier bridge, and both bridge arms are formed by connecting a diode and a MOSFET in series, wherein the MOSFET is a lower tube.
Further, the resonant capacitor in the resonant inverter module, the compensation capacitor in the high-order compensation network, and the filter capacitor in the rectifier module are composed of a plurality of capacitors connected in series and/or in parallel; the resonance inductor in the high-order compensation network and the filter inductor in the rectifying module are composed of a plurality of inductors which are connected in series and/or in parallel.
Has the advantages that: compared with the prior art, the utility model has the following advantages:
(1) the utility model discloses a novel non-contact single-tube resonant converter, through the design of a primary side resonant capacitor and a high-order compensation network, a switching tube in a primary side inversion module can realize zero voltage opening under light load, and realize zero voltage and zero current opening simultaneously under heavy load, and the primary side inductive current of the converter presents a quasi-constant current characteristic, and the output presents a quasi-constant current characteristic;
(2) the utility model utilizes the high-order compensation network to adjust the folded impedance property of the secondary side into the resistance or the inductance resistance, thereby reducing the voltage stress and the current stress of the switching tube in the primary side inversion module;
(3) the utility model utilizes the high-order compensation network to increase the freedom of parameter design, and can be designed to adapt to different output indexes under the condition of ensuring the soft switching on of a switch tube in the primary side inversion module, and the series or parallel compensation has no design capability;
(4) the utility model utilizes the controllable rectifier bridge to adjust the equivalent impedance property of the rectifier bridge load into pure resistance, thereby improving the power transmission capability of the novel non-contact single-tube resonant converter;
(5) the utility model discloses a novel non-contact single tube resonant converter has circuit and drive simply, and reliable operation, advantage with low costs.
Drawings
Fig. 1 is an equivalent circuit in which the secondary side of the non-contact single-tube resonant converter of the present invention is folded into the primary side;
fig. 2 is a schematic diagram of a working waveform of a primary side circuit of the non-contact single-tube resonant converter of the present invention;
FIG. 3 is an exploded view of the fundamental wave of the voltage across the resonant capacitor;
FIG. 4 is a schematic diagram of a conventional converter with parallel compensation of secondary side;
fig. 5 is a schematic structural diagram of a first embodiment of the present invention;
fig. 6 is a simulation waveform of the first embodiment of the present invention;
fig. 7 is a simulation result of output characteristics according to the first embodiment of the present invention;
fig. 8 shows the comparison result of the voltage stress of the switching tube of the first embodiment of the present invention and the secondary side parallel compensation structure;
fig. 9 is a comparison result of current stress of the switching tube of the first compensation structure connected in parallel with the secondary side according to the embodiment of the present invention;
fig. 10 is a schematic structural view of a second embodiment of the present invention;
fig. 11 is a schematic structural diagram of a third embodiment of the present invention;
fig. 12 is an input-side voltage current simulation diagram of the uncontrolled rectifier bridge of the rectifier module of the present invention;
fig. 13 is a schematic diagram of a control logic of a rectifier module according to a second embodiment of the present invention;
fig. 14 is a simulation diagram of a second embodiment of the present invention;
fig. 15 is a schematic structural diagram of a fourth embodiment of the present invention;
fig. 16 is a schematic structural diagram of a fifth embodiment of the present invention;
in the figure: vinSupply voltage, S-switch tube, Cds1～Cds3Parasitic capacitance, D01～D03Body diode, LpPrimary inductance of the contactless transformer, LsSecondary inductance of the non-contact transformer, M-mutual inductance of the primary and secondary inductances, Cr1、Cr2、CrPrimary side resonant capacitance, iLPrimary inductor current of non-contact transformer, uc-resonant capacitor voltage us-switching tube drain-source voltage, ReMinor edge fold resistance, C, C1、C2-compensation capacitance in secondary side higher order compensation network, L2Resonant inductance in secondary side high order compensation network, D1～D4-a rectifier diode, S3、S4-a controllable rectifier tube, CoFilter capacitor, RL-load, Vo-output voltage, vrec-a rectifier bridge front voltage, irec-a rectifier bridge input current uacFundamental voltage of primary side resonance capacitor iacPrimary inductor current fundamental current of non-contact transformer, VgsDriving signal of switching tube S, IoOutput current, VsVoltage stress of the switching tube S, IsCurrent stress of the switching tube S, vS3-S3Voltage between source and drain, vS4-S4Voltage between the source and drain.
Detailed Description
The present invention will be further explained with reference to the accompanying drawings.
The utility model discloses a novel non-contact single tube resonant converter utilizes the vice limit of high order compensation network adjustment to convert into impedance nature, under the parameter design method that gives, has realized the soft of switch tube and has opened, and the primary coil current has accurate constant current characteristic, has realized the accurate constant current characteristic of output, has improved switch tube voltage stress, has increased the parametric design degree of freedom, has solved existing non-contact single tube circuit because of output characteristic is poor, high switch tube stress and lack the problem that the parametric design degree of freedom is not high.
FIG. 1(a) shows the equivalent circuit of the non-contact single-tube resonant converter of the present invention, in which the secondary folded impedance is temporarily approximated to the pure resistance ReFig. 2 is a schematic diagram of a circuit waveform based on an equivalent circuit. At time t0, S is in a conducting state, and primary inductance L of the non-contact transformerpEnd of energy release, primary side inductor current iLTo zero; primary side inductance L during period t 0-t 1pStored energy, iLIncreasing; at time t1, S is turned off, and the primary side resonant capacitor CrStart and LpCarrying out resonance; time t2, iLResonant to zero, CrMaximum reverse voltage of S, drain-source voltage u of SsMaximum; during the period t 2-t 3, CrCharging is carried out; time t3, ucIs equal to VinBody diode D of S01Conducting, and meanwhile, S is switched on, so that ZVS is realized; during the period t 3-t 4, LpReleasing energy to the power source.
Example one
Fig. 5 is a schematic structural diagram of a non-contact single-tube resonant converter according to a first embodiment of the present invention. As shown in FIG. 5, LpAnd CrAfter parallel connection, one end is connected with the positive electrode of the power supply, the other end is connected with the drain electrode of S, the source electrode of S is connected with the negative electrode of the power supply, and LsAnd C1After being connected in series, is then connected with C2Connected in parallel and then with L2Connected in series and finally connected to the middle points of two bridge arms of an uncontrolled rectifier bridge, CoAnd RLAfter being connected in parallel, the output end of the uncontrolled rectifier bridge is connected in parallel.
Equation (1) gives a time-domain differential expression of the resonance process during S-off:
the S off period i can be derived and calculated by the formula (1)LAnd ucThe time domain expression of (2), wherein,I0＝iL(t1)，wrfor the resonant angular frequency during the off-time of the switching tube S,is the phase shift angle of the primary side inductor current, I0The primary inductor current at time t 1. It can be seen that, during S off,is the rate of decay of the circuit energy at time t.
Therefore, the condition for realizing ZVS by S is as shown in formula (3), wherein t1 is time CrAnd LpTotal energy stored
At time t1, the primary side inductor current can be calculated by equation (4):
as can be seen from FIG. 2, at time t2, when iLWhen the resonance reaches 0, the voltage at the two ends of the switching tube S is the highest,Tris the resonance period during which the switching tube S is turned off. At this time, the energy in the resonant elements is transferred to CrAbove, as shown in formula (5):
is composed of(5) The voltage stress of the switching tube S can be solved, as shown in formula (6), T is the switching period of S, TrIs the S off period Lp、CrAnd ReThe resonance period of (c).
The voltage stress of the switching tube S is subjected to Taylor series decomposition and certain approximation, as shown in formula (7):
FIG. 3 shows a pair CrThe voltage at two ends is subjected to fundamental wave decomposition, and the amplitude U of the fundamental wave voltage is shownacIs about CrHalf of the peak value of the voltage at both ends, i.e. half of the voltage stress of the switching tube S, i.e.Therefore CrThe fundamental voltage at both ends has a quasi-constant voltage characteristic. FIG. 1(b) shows the AC equivalent circuit of the non-contact single-tube resonant converter of the present invention, the primary side inductive current fundamental wave current of the original non-contact transformer is as shown in formula (8), IacThe amplitude of the primary side inductance current fundamental wave current of the non-contact transformer is shown, and w is the switching angular frequency of S.
Therefore, the fundamental wave current of the primary coil of the non-contact single-tube resonant converter has the characteristic of quasi-constant current.
The non-contact single-tube resonant converter of the embodiment needs to be designed according to the following design flow:
first, given Po，Vin，Lp，f，ReIn which P isoF is the switching frequency of S for the output power;
in the second step, C is resolved from the formula (3)rA range of (d);
third stepStep two, when the equal number is taken in the second step, the I can be calculated by the formula (6) and the formula (8)ac；
Fourth, the current output powerIf Po' if the output power requirement is not satisfied, then R is adjustedeTurning to the second step;
fifthly, calculating the voltage stress of the switching tube by the formula (6), and if the voltage stress does not meet the requirement, adjusting ReTurning to the second step;
the sixth step, from Re＝Re(Zeq) Performing high-order compensation network parameter design, wherein ZeqThe impedance is reduced for the secondary side.
The higher-order compensation network prefers the parameter relationship:obviously, there is one degree of freedom in the design of the parameters.
On the premise that the load of the rectifier bridge is pure resistance, the secondary side is reduced into impedanceThe S-shaped switch tube is pure resistive, and compared with the parallel compensation of the secondary side, the S-shaped switch tube has relatively small voltage stress and current stress.
Under the condition of the parameter design, the output current expression of the novel non-contact single-tube resonant converter is shown as a formula (9), and the output current expression is combined with a formula (8), so that the converter has the output quasi-constant current characteristic.
According to the parameter design process, a group of saber simulation parameters of the novel non-contact single-tube resonant converter with the secondary side adopting the high-order compensation network are given as follows: vin＝400V，f＝40kHz，Lp＝95.9μH，Cr＝106.4nF，Ls＝97.8μH，M＝29μH，C1＝378.7nF，C2＝282.7nF，L2＝56μH，Co＝650μF。
If the secondary side of the non-contact single-tube resonant converter adopts parallel compensation, as shown in fig. 4, the compensation capacitor and the secondary side inductance of the non-contact transformer satisfy the relationshipWherein C ispThe secondary side is connected with a compensation capacitor in parallel. The load fundamental wave of the rectifier bridge is equivalent to pure resistance, and the reduced impedance of the secondary side is shown as the formula (10):
apparently capacitive, so V is shown in the voltage stress expression of the switching tubesIncrease of IacThe increase, and correspondingly, the switching tube current stress increases. A set of sabe simulation parameters when the secondary side adopts parallel compensation are given below: vin＝400V，f＝40kHz，Lp＝95.9μH，Cr＝106.4nF，Ls＝97.8μH，M＝29μH，Cp＝161nF，Co＝650μF。
Fig. 6 shows a simulation waveform of S simultaneously implementing zero-voltage and zero-current switching under the parameter design of the novel non-contact single-tube resonant converter adopting the high-order compensation network on the secondary side; fig. 7 shows the output current VS load resistance, which exhibits an output quasi-constant current characteristic. Fig. 8 and 9 show a comparison between the voltage stress and the current stress of the switching tube under the above two sets of parameters, and it is obvious that the secondary side has lower voltage stress and current stress of the switching tube than the parallel compensation by using a high-order compensation network.
Example two
Fig. 10 is a schematic structural diagram of a second embodiment of the non-contact single-tube resonant converter according to the present invention. Primary side circuit configuration same as in the first embodiment, LsAfter being connected with C in parallel, the three-phase bridge is connected to the middle points of two bridge arms of an uncontrolled rectifier bridge, CoAnd RLAfter being connected in parallel, the output end of the uncontrolled rectifier bridge is connected in parallel.
Design of primary side resonant capacitor is same as that of embodiment I, and preferable parameter of high-order resonant networkNumerical relationshipObviously, the design freedom of parameters is not available at this time, but L can be adjusted2And enabling the high-order resonant network to work in a detuning state so as to meet the output index.
EXAMPLE III
Fig. 11 is a schematic structural diagram of a third embodiment of the non-contact single-tube resonant converter of the present invention. As shown in fig. 11, the resonant inverter module and the high-order compensation module have the same structure as the first embodiment, the parameter design process is the same as the first embodiment, the rectifier module is a controllable rectifier bridge, and both bridge arms are formed by connecting a diode and a MOSFET in series, wherein the MOSFET is a lower tube, and C isoAnd RLAfter being connected in parallel, the output end of the controllable rectifier bridge is connected in parallel. The load equivalent impedance of the uncontrolled rectifier bridge is approximately pure resistive in the above, but due to the influence of the higher harmonic current, the equivalent impedance is resistive, fig. 12 shows the input side voltage and current waveform of the uncontrolled rectifier bridge, and obviously the fundamental current lags behind the fundamental voltage. Ignoring parasitic parameters in the circuit, equation (11) gives an expression of equivalent impedance of a rectifier bridge load and an expression of power transmission capability:
in the formula, ZrecFor a bridge loaded with an equivalent impedance, PcapIn order to control the power transmission capability of the novel non-contact single-tube resonant converter under the condition of rectification, theta is a load equivalent impedance angle of the rectifier bridge. In the embodiment, the phase relation between the fundamental wave voltage and the fundamental wave current at the input side of the rectifier bridge is adjusted by controlling the on-off of the bridge arm of the rectifier bridge, so that the aim of adjusting the equivalent impedance of the rectifier bridge to be pure resistance is fulfilled. FIG. 13 shows the control logic of the controllable rectifier bridge when irecWhen changing from positive to negative, S3Body diode D of02On, and off after a period of time4At D02Conducting S during conduction3(ii) a When i isrecFrom negative to positive, S4Body diode D of03On, and off after a period of time3At D03Conducting S during conduction4(ii) a Let D02The conduction time is the starting time ta，S4Turn-off time tbOr D is03The conduction time is the starting time ta，S3Turn-off time tbDefinition of Dctr＝1-2(tb-ta) T, then when DctrWhen equation (12) is satisfied, the bridge load equivalent impedance can be adjusted to be pure resistive, as shown in fig. 14, i.e. cos θ is 1, the inductance of the secondary side reduced impedance disappears, according to the above IacIs shown by the expression (8) of (A), in which case IacAnd also increased. Therefore, as shown in the combination formula (11), the power transmission capability of the non-contact single-tube resonant converter can be improved by adopting the controllable rectifier bridge.
Example four
Fig. 15 is a schematic structural diagram of a fourth embodiment of the non-contact single-tube resonant converter of the present invention. As shown in FIG. 15, LpAnd Cr1After parallel connection, one end is connected with the positive pole of the power supply, the other end is connected with the drain electrode of S, the source electrode of S is connected with the negative pole of the power supply, Cr2Connected in parallel across S, LsAnd C1After being connected in series, is then connected with C2Connected in parallel and then with L2Connected in series and finally connected to the middle points of two bridge arms of an uncontrolled rectifier bridge, CoAnd RLAfter being connected in parallel, the output end of the uncontrolled rectifier bridge is connected in parallel. The parameter design method of this embodiment is the same as that of the first embodiment, wherein Cr＝Cr1+Cr2，Cr1And Cr2The size relationship of (a) can be arbitrarily configured.
EXAMPLE five
Fig. 16 is a schematic structural diagram of a fourth embodiment of the non-contact single-tube resonant converter of the present invention. As shown in FIG. 16, LpOne end connected to the positive electrode of the power supply, the other end connected to the drain of S, the source of S connected to the negative electrode of the power supply, Cr2In parallelAt both ends S, LsAnd C1After being connected in series, is then connected with C2Connected in parallel and then with L2Connected in series and finally connected to the middle points of two bridge arms of an uncontrolled rectifier bridge, CoAnd RLAfter being connected in parallel, the output end of the uncontrolled rectifier bridge is connected in parallel. The parameter design method of this embodiment is the same as that of the first embodiment, wherein Cr＝Cr2。
The utility model provides a vice limit adopts the high order compensation network, cooperates reasonable parameter design, not only can realize accurate constant current output, provides good closed loop regulation characteristic for wireless charging, has realized the soft of switch tube moreover and has opened, has reduced switch tube voltage stress and current stress, has increased parameter design degree of freedom, adaptable different output index. The utility model discloses still provide the secondary limit and adopt controllable rectifier bridge, adjustment rectifier bridge load nature has improved novel non-contact single tube resonant converter's power transmission ability, has improved non-contact single tube circuit's using value greatly.
The foregoing is only a preferred embodiment of the present invention, and it should be noted that, for those skilled in the art, a plurality of modifications and decorations can be made without departing from the principle of the present invention, and these modifications and decorations should also be regarded as the protection scope of the present invention.
Claims (7)
1. A non-contact single tube resonant converter is characterized in that: comprises a primary side and a secondary side; wherein: the primary side comprises a resonance inversion module; the resonance inversion module comprises a primary side inductor LpA switching tube S, the primary side inductor LpIs connected in series with the switching tube S and then connected in parallel with the input voltage VinTwo ends, and a primary side inductor LpAnd/or the switch tube S is respectively connected with a resonance capacitor in parallel; the secondary side comprises secondary side inductors L connected in sequencesThe high-order compensation network and the rectification module.
2. The non-contact single-tube resonant converter according to claim 1, wherein: the high-order compensation network is composed of a compensation capacitor C1And a compensation capacitor C2Resonant inductor L2The secondary side inductor LsAnd a compensation capacitor C1After being connected in series, the compensating capacitor C2Connected in parallel and then with the resonant inductor L2Are connected in series.
3. The non-contact single-tube resonant converter according to claim 1, wherein: the high-order compensation network consists of a compensation capacitor C and a resonance inductor L2The secondary side inductor LsConnected in parallel with the compensation capacitor C and then connected with the resonance inductor L2Are connected in series.
4. The non-contact single-tube resonant converter according to claim 2 or 3, characterized in that: the rectifier module comprises a rectifier and a filter, the rectifier is full-bridge rectification or current-doubling rectification or voltage-doubling rectification, and the filter is LC filtering or C filtering.
5. The non-contact single-tube resonant converter according to claim 4, wherein the rectifier is a controllable rectifier bridge, and both bridge arms are composed of a diode and a MOSFET connected in series, wherein the MOSFET is a down tube.
6. The non-contact single-tube resonant converter according to claim 4, wherein: the resonance capacitor in the resonance inversion module, the compensation capacitor in the high-order compensation network and the filter capacitor in the rectification module are composed of a plurality of capacitors which are connected in series and/or in parallel; the resonance inductor in the high-order compensation network and the filter inductor in the rectifying module are composed of a plurality of inductors which are connected in series and/or in parallel.
7. The non-contact single-tube resonant converter according to claim 5, wherein: the resonance capacitor in the resonance inversion module, the compensation capacitor in the high-order compensation network and the filter capacitor in the rectification module are composed of a plurality of capacitors which are connected in series and/or in parallel; the resonance inductor in the high-order compensation network and the filter inductor in the rectifying module are composed of a plurality of inductors which are connected in series and/or in parallel.
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110212778A (en) * | 2019-06-28 | 2019-09-06 | 南京航空航天大学 | A kind of non-contact single tube controlled resonant converter |
| CN112202252A (en) * | 2020-12-04 | 2021-01-08 | 南京航空航天大学 | Non-contact single-tube resonant converter with primary impedance conversion network |
| CN114785156A (en) * | 2022-06-13 | 2022-07-22 | 南京航空航天大学 | Single-tube resonant converter with low voltage stress |
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2019
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Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110212778A (en) * | 2019-06-28 | 2019-09-06 | 南京航空航天大学 | A kind of non-contact single tube controlled resonant converter |
| CN110212778B (en) * | 2019-06-28 | 2024-03-22 | 南京航空航天大学 | Non-contact single-tube resonant converter |
| CN112202252A (en) * | 2020-12-04 | 2021-01-08 | 南京航空航天大学 | Non-contact single-tube resonant converter with primary impedance conversion network |
| CN114785156A (en) * | 2022-06-13 | 2022-07-22 | 南京航空航天大学 | Single-tube resonant converter with low voltage stress |
| CN114785156B (en) * | 2022-06-13 | 2022-09-02 | 南京航空航天大学 | Single-tube resonant converter with low voltage stress |
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Address after: No. 29, Qinhuai District, Qinhuai District, Nanjing, Jiangsu Patentee after: Nanjing University of Aeronautics and Astronautics Patentee after: Jiangsu Zhanxin Semiconductor Technology Co.,Ltd. Address before: No. 29, Qinhuai District, Qinhuai District, Nanjing, Jiangsu Patentee before: Nanjing University of Aeronautics and Astronautics Patentee before: JIANGSU ZHANXIN SEMICONDUCTOR TECHNOLOGY Co.,Ltd. |