CN110212778B - Non-contact single-tube resonant converter - Google Patents
Non-contact single-tube resonant converter Download PDFInfo
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- CN110212778B CN110212778B CN201910575234.1A CN201910575234A CN110212778B CN 110212778 B CN110212778 B CN 110212778B CN 201910575234 A CN201910575234 A CN 201910575234A CN 110212778 B CN110212778 B CN 110212778B
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
- H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
- H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Computer Networks & Wireless Communication (AREA)
- Dc-Dc Converters (AREA)
- Rectifiers (AREA)
Abstract
The invention discloses a non-contact single-tube resonant converter, which comprises a primary side and a secondary side; wherein: the primary side comprises a resonance inversion module; the resonance inversion module comprises a primary inductor and a switching tube, wherein the primary inductor and the switching tube are connected in series and then connected in parallel at two ends of input voltage, and the resonance inversion module further comprises a resonance capacitor which is respectively connected in parallel with the primary inductor and/or the switching tube; the secondary side comprises a secondary side inductor, a high-order compensation network and a rectifying module which are sequentially connected. The invention provides a parallel connection method of different primary side resonance capacitors and a secondary side of the transformer adopts a high-order compensation network, and is matched with reasonable parameter design, so that the transformer not only can realize quasi-constant current output and provide good closed-loop regulation characteristic for wireless charging, but also realizes soft switching on of a switching tube, reduces voltage stress and current stress of the switching tube and increases the degree of freedom of parameter design; the secondary side rectifier bridge can adopt a controllable rectifier bridge structure, and under the given control method, the load of the rectifier bridge is adjusted to be pure resistance, so that the power transmission capacity of the proposed topology is improved.
Description
Technical Field
The invention relates to a non-contact single-tube resonant converter, and belongs to the technical field of wireless charging.
Background
Wireless energy transfer technology (WPT, wireless PowerTransmission) has been applied to the fields of electric vehicles, automated guided vehicles (AGV, automated GuidedVehicle), unmanned aerial vehicles, automatic driving, etc., especially where automatic charging is required and manual charging is not possible. Compared with contact power supply, wireless power supply has the advantages of safety, flexibility, no spark, less maintenance, portability, easy realization of automation and the like.
WPT achieves non-contact energy transfer mainly through inductive coupling energy transfer (ICPT, inductively CoupledPowerTransmission), electromagnetic coupling resonance energy transfer (ERPT, electro-magnetic ResonantPower Transmission), radio frequency energy transfer (RFPT, radio Frequency PowerTransmission), microwave energy transfer (MPT, microwave PowerTransmission), laser energy transfer (LPT, laser PowerTransmission), and the like. Among them, ICPT is the most widely used WPT mode.
Inversion is one of the essential links of ICPT, and the most commonly used inversion topology is a multi-tube structure. However, for the middle and small power occasions, the multi-tube inversion is relatively high in cost, complicated in driving and low in cost performance, so that the single-tube inversion with low cost and simple driving becomes a better choice for the middle and small power occasions. The single-tube inversion is special in that DC/AC conversion is realized by means of a resonance process, so that the voltage stress of a switching tube is high, and analysis is difficult.
The existing researches show that the non-contact single-tube circuit has two types of Class-E and resonance flyback, wherein the Class-E has little application value due to the voltage stress of the switching tube with the input voltage being more than 4 times. The existing non-contact resonant flyback circuit (hereinafter referred to as a non-contact single-tube resonant converter) has two compensation modes of series compensation and parallel compensation on the secondary side. The series compensation and the parallel compensation have no parameter design freedom, which is not in accordance with the actual application requirements; the parallel compensation is capacitive, and the secondary folding impedance enables the voltage stress and the current stress of the switching tube to be larger, wherein the voltage stress is more than 3 times of the input voltage. The bus voltage of the PFC module is usually about 400V, and the voltage stress above 3 times of the input voltage greatly reduces the type selection range of the switching tube. Therefore, in order to improve the application value of the non-contact single-tube circuit, good output characteristics are required to be realized, the voltage stress and the current stress of the switching tube are properly reduced, and the degree of freedom of parameter design is increased.
Disclosure of Invention
The invention aims to: aiming at the prior art, the non-contact single-tube resonant converter is provided, the quasi-constant current output characteristic is realized, the voltage stress of a switching tube is improved, the degree of freedom of parameter design is increased, and the problem that the application value of the existing non-contact single-tube circuit is low due to poor output characteristic, high switching tube stress and lack of degree of freedom of parameter design is solved.
The technical scheme is as follows: a non-contact single-tube resonant converter comprises a primary side and a secondary side; wherein: the primary side comprises a resonance inversion module; the resonance inversion module comprises a primary inductor L p A switch tube S, the primary side inductance L p Is connected in series with a switching tube S and then is connected in parallel with an input voltage V in Both ends also include the inductance L at the primary side p And/or the switch tubes S are respectively connected with the resonant capacitors in parallel; the secondary side comprises secondary side inductors L which are connected in sequence s The system comprises a high-order compensation network and a rectification module.
Furthermore, the resonance capacitor meets the following requirements, so that the switching tube S in the resonance inversion module can realize zero voltage switching-on under light load and realize zero voltage and zero current switching-on under heavy load;
when the primary inductance L p And the switch tube S are respectively connected with the resonant capacitor C in parallel r1 And a resonance capacitor C r2 When (1):
when the primary inductance L p Or on the switching tube S and resonance capacitor C r When (1):
wherein R is e For the secondary side folding-in resistor, △ t is the turn-off time of the switching tube S in the primary side resonance inversion module, and W is the resonance capacitance and the primary side inductance L when the switching tube S in the primary side resonance inversion module is turned off p The sum of the stored energies.
Further, the high-order compensation networkCompensation capacitor C 1 Compensating capacitor C 2 Resonant inductance L 2 Composition of the secondary inductance L s And compensating capacitor C 1 After being connected in series, the capacitor is connected with a compensation capacitor C 2 Connected in parallel and then with resonant inductance L 2 Are connected in series; the high-order compensation network parameters meet the following requirements, so that the non-contact single-tube resonant converter has quasi-constant current output characteristics:
wherein w is the switching angular frequency of the switching tube S.
Further, the high-order compensation network consists of a compensation capacitor C and a resonance inductance L 2 Composition of the secondary inductance L s Is connected in parallel with the compensation capacitor C and then is connected with the resonant inductor L 2 Are connected in series; the parameters of the high-order compensation network are required to meet the following requirements, so that the non-contact single-tube resonant converter has quasi-constant current output characteristics:
wherein w is the switching angular frequency of the switching tube S.
Further, the rectifying module comprises a rectifier and a filter, wherein the rectifier is full-bridge rectification or double-current rectification or double-voltage rectification, and the filter is LC filtering or C filtering.
Further, the rectifier is a controllable rectifier bridge, two bridge arms are respectively formed by connecting a diode and a MOSFET in series, wherein the MOSFET is a lower tube, and the control characteristic quantity D of the MOSFET ctr The method meets the following requirements, and the equivalent impedance of the load of the rectifier bridge is adjusted to be pure resistance;
wherein R is L Is the load resistance.
Further, the resonance capacitor in the resonance inversion module, the compensation capacitor in the high-order compensation network and the filter capacitor in the rectification module are composed of a plurality of capacitors connected in series and/or in parallel; the resonant inductance in the high-order compensation network and the filter inductance in the rectification module are composed of a plurality of inductances which are connected in series and/or in parallel.
The beneficial effects are that: compared with the prior art, the invention has the following advantages:
(1) The invention discloses a novel non-contact single-tube resonant converter, which is characterized in that through the parameter design of a primary side resonant capacitor and a high-order compensation network, a switching tube in a primary side inversion module can realize zero voltage switching-on under light load and realize zero voltage and zero current switching-on under heavy load simultaneously, and the primary side inductance current of the converter presents quasi-constant current characteristics, and the output presents quasi-constant current characteristics;
(2) The secondary side folding impedance property is adjusted to be resistive or resistive-inductive by utilizing the high-order compensation network, so that the voltage stress and the current stress of a switching tube in the primary side inversion module are reduced;
(3) The invention increases the degree of freedom of parameter design by using a high-order compensation network, and can design and adapt to different output indexes under the condition of ensuring that a switching tube in a primary side inversion module is soft-opened, and serial or parallel compensation does not have design capability;
(4) The invention can adjust the load equivalent impedance property of the rectifier bridge to be pure resistance by utilizing the controllable rectifier bridge, thereby improving the power transmission capacity of the novel non-contact single-tube resonant converter;
(5) The novel non-contact single-tube resonant converter disclosed by the invention has the advantages of simple circuit and driving, reliable work and low cost.
Drawings
FIG. 1 is an equivalent circuit of a non-contact single-tube resonant converter of the present invention with the secondary side folded to the primary side;
FIG. 2 is a schematic diagram of the operational waveforms of the primary circuit of the non-contact single-tube resonant converter of the present invention;
FIG. 3 is an exploded view of the fundamental wave of the voltage across the resonant capacitor;
FIG. 4 is a schematic diagram of a conventional converter with secondary side parallel compensation;
FIG. 5 is a schematic diagram of a first embodiment of the present invention;
FIG. 6 is a simulation waveform of a first embodiment of the present invention;
FIG. 7 is a simulation result of the output characteristics according to the first embodiment of the present invention;
FIG. 8 shows the comparison of the voltage stress of the switching tube of the parallel compensation structure of the first embodiment of the invention and the secondary side;
FIG. 9 is a comparison result of current stress of a switching tube of a parallel compensation structure with a secondary side according to an embodiment of the present invention;
FIG. 10 is a schematic diagram of a second embodiment of the present invention;
FIG. 11 is a schematic diagram of a third embodiment of the present invention;
FIG. 12 is a schematic diagram of a voltage-current simulation of the input side of the rectifier module of the present invention as an uncontrolled rectifier bridge;
FIG. 13 is a schematic diagram of a control logic of a rectifier module according to a second embodiment of the invention;
FIG. 14 is a simulation diagram of a second embodiment of the present invention;
FIG. 15 is a schematic diagram of a fourth embodiment of the present invention;
FIG. 16 is a schematic diagram of a fifth embodiment of the present invention;
in the figure: v (V) in Supply voltage, S-switch tube, C ds1 ～C ds3 Parasitic capacitance, D 01 ～D 03 Body diode, L p -primary inductance of non-contact transformer, L s -non-contact transformer secondary inductance, M-primary inductance and mutual inductance of secondary inductance, C r1 、C r2 、C r Primary side resonance capacitance, i L -non-contact transformer primary inductor current, u c -resonant capacitor voltage, u s -switching tube drain-source voltage, R e Secondary fold resistance C, C 1 、C 2 -compensation capacitance, L in secondary higher order compensation network 2 -resonant inductance in secondary high order compensation network, D 1 ～D 4 -rectifier diode, S 3 、S 4 -a controllable rectifier tube, C o Filter capacitor R L The load is a load that is set up in the vehicle,V o -output voltage, v rec -rectifier bridge front voltage, i rec -rectifier bridge input current, u ac Fundamental voltage of primary side resonance capacitor, i ac Primary inductor current fundamental current of non-contact transformer, V gs Drive signal of switching tube S, I o -output current, V s Voltage stress of switching tube S, I s Current stress of switching tube S, v S3 -S 3 Voltage between source and drain, v S4 -S 4 Source-drain voltage of (a) is provided.
Detailed Description
The invention is further explained below with reference to the drawings.
According to the novel non-contact single-tube resonant converter, the secondary folding impedance property is adjusted by utilizing the high-order compensation network, soft switching-on of a switching tube is realized under the given parameter design method, the primary coil current has the quasi-constant current characteristic, the output quasi-constant current characteristic is realized, the voltage stress of the switching tube is improved, the degree of freedom of parameter design is increased, and the problem that the application value of the existing non-contact single-tube circuit is low due to poor output characteristic, high switching tube stress and lack of parameter design freedom is solved.
In FIG. 1 (a), an equivalent circuit of the novel non-contact single-tube resonant converter of the invention is shown, and the secondary folded impedance is temporarily approximated to the pure R e Fig. 2 is a schematic diagram of a circuit waveform based on an equivalent circuit. At time t0, S is in a conducting state, and the primary inductance L of the non-contact transformer p The energy release is finished, and the primary side inductance current i L To zero; during t 0-t 1, primary inductance L p Store energy, i L Increasing; at time t1, S is turned off, primary side resonance capacitor C r Start and L p Resonating; time t2, i L Resonance to zero, C r The reverse voltage of S is the largest, drain-source voltage u s Maximum; during the period t 2-t 3, C r Charging; at time t3, u c Equal to V in Body diode D of S 01 Conducting, and meanwhile, switching on S to realize ZVS; during t3 to t4, L p Releasing energy to the power supply.
Example 1
Fig. 5 is a schematic structural diagram of a first embodiment of a non-contact single-tube resonant converter according to the present invention. As shown in FIG. 5, L p And C r After being connected in parallel, one end is connected with the positive electrode of the power supply, the other end is connected with the drain electrode of the S, the source electrode of the S is connected with the negative electrode of the power supply, L s And C 1 After being connected in series, is connected with C 2 Connected in parallel and then with L 2 Connected in series and finally connected to the midpoints of two bridge arms of the uncontrolled rectifier bridge, C o And R is R L And after being connected in parallel, the output terminals of the uncontrolled rectifier bridge are connected in parallel.
Equation (1) gives the time-differential expression of the resonance process during S-off:
from equation (1), the S-off period i can be calculated by derivation L And u c As shown in the formula (2), wherein,w r for the resonance angular frequency during the switching tube S off, < >>I is the phase shift angle of primary inductor current 0 The primary inductor current at time t 1. It can be seen that during S-off, +.>Is the rate of decay of the circuit energy at time t.
Thus, the condition for achieving ZVS by S is as shown in formula (3), wherein time C is t1 r And L p Total energy stored
At time t1, the primary inductor current can be calculated by equation (4):
as can be seen from FIG. 2, at time t2, when i L When resonance reaches 0, the voltage across the switching tube S is highest,T r is the resonance period during which the switching tube S is turned off. At this time, the energy in the resonant element is transferred to C r As shown in formula (5):
the voltage stress of the switching tube S can be solved by the formula (5), as shown in the formula (6), T is the switching period of S, T r For the S off period L p 、C r And R is e Is a resonant period of (a).
The voltage stress of the switching tube S is subjected to Taylor series decomposition and certain approximation, as shown in a formula (7):
FIG. 3 shows pair C r Fundamental wave decomposition is carried out on the voltages at two ends, and it can be seen that the amplitude U of the fundamental wave voltage ac About C r Half of the peak-to-peak voltage of the two ends is half of the voltage stress of the switch tube S, namelyTherefore C r The two-terminal fundamental wave voltage has a quasi-constant voltage characteristic. The present invention is shown in FIG. 1 (b)AC equivalent circuit of open type non-contact single tube resonant converter, primary side inductance current fundamental wave current of original non-contact transformer is shown as formula (8), I ac The primary side inductance current fundamental current amplitude of the non-contact transformer is the switching angular frequency of S.
Therefore, the primary coil fundamental current of the non-contact single-tube resonant converter has the characteristic of quasi-constant current.
The non-contact single-tube resonant converter of the embodiment needs to be designed according to the following design flow:
first step, give P o ，V in ，L p ，f，R e Wherein P is o F is the switching frequency of S for output power;
second, solve C from formula (3) r Is defined by the range of (2);
third, when the equal sign is taken in the second step, I can be calculated according to the formulas (6) and (8) ac ；
Fourth step, current output powerIf P o ' do not meet the output power requirement, R is adjusted e Turning to the second step;
fifth step, calculate the voltage stress of the switch tube according to formula (6), if not meeting the requirement, adjust R e Turning to the second step;
sixth step, R is e ＝Re(Z eq ) Performing high-order compensation network parameter design, wherein Z eq The impedance is folded for the secondary side.
Higher order compensation network preference parameter relationship:obviously, there is one degree of freedom in parameter design.
On the premise that the rectifier bridge load is purely resistive, the secondary side folding impedanceThe switching tube S is purely resistive, and the voltage stress and the current stress of the switching tube S are relatively small compared with the parallel compensation of the secondary side.
Under the above parameter design condition, the output current expression of the novel non-contact single-tube resonant converter is shown as formula (9), and in combination with formula (8), the converter can be seen to have the output quasi-constant current characteristic.
According to the parameter design flow, a set of saber simulation parameters of the novel non-contact single-tube resonant converter with the secondary side adopting the high-order compensation network are given below: v (V) in ＝400V，f＝40kHz，L p ＝95.9μH，C r ＝106.4nF，L s ＝97.8μH，M＝29μH，C 1 ＝378.7nF，C 2 ＝282.7nF，L 2 ＝56μH，C o ＝650μF。
If the secondary side of the non-contact single-tube resonant converter adopts parallel compensation, as shown in fig. 4, the compensation capacitance and the inductance of the secondary side of the non-contact transformer satisfy the relationWherein C is p And compensating capacitors are connected in parallel for the secondary sides. The fundamental wave of the rectifier bridge load is equivalent to pure resistance, and the secondary folding impedance is shown as formula (10):
is obviously capacitive, so that V can be seen from the expression of the voltage stress of the switching tube s Enlargement, I ac The increase, and correspondingly, the switch tube current stress increases. A set of sabe simulation parameters for the secondary side using parallel compensation is given below: v (V) in ＝400V，f＝40kHz，L p ＝95.9μH，C r ＝106.4nF，L s ＝97.8μH，M＝29μH，C p ＝161nF，C o ＝650μF。
FIG. 6 shows simulation waveforms for realizing zero voltage and zero current switching on simultaneously under the parameter design of the novel non-contact single-tube resonant converter with the secondary side adopting a high-order compensation network; fig. 7 shows an output current VS load resistor, which exhibits an output quasi-constant current characteristic. Fig. 8 and 9 show comparison of the voltage stress and the current stress of the switching tube under the two groups of parameters, and it is obvious that the secondary side has lower voltage stress and current stress of the switching tube compared with the parallel compensation by adopting a higher-order compensation network.
Example two
Fig. 10 is a schematic structural diagram of a second embodiment of the novel non-contact single-tube resonant converter of the present invention. The primary side circuit structure is the same as that of the first embodiment, L s Connected in parallel with C, connected to the midpoint of two bridge arms of the uncontrolled rectifier bridge, C o And R is R L And after being connected in parallel, the output terminals of the uncontrolled rectifier bridge are connected in parallel.
The design of the primary resonance capacitor is the same as that of the first embodiment, and the preferred parameter relation of the higher-order resonance networkObviously, the degree of freedom of parameter design is not provided at this time, but L can be adjusted 2 The high-order resonant network is enabled to work in a detuned state so as to meet the output index.
Example III
Fig. 11 is a schematic structural diagram of a third embodiment of the novel non-contact single-tube resonant converter of the present invention. As shown in fig. 11, the resonant inversion module and the high-order compensation module have the same structure as the first embodiment, the parameter design flow is the same as the first embodiment, the rectification module is a controllable rectification bridge, the two bridge arms are each formed by connecting a diode and a MOSFET in series, wherein the MOSFET is a lower tube, and C o And R is R L And after being connected in parallel, the two ends of the controllable rectifier bridge are connected in parallel with the output terminal of the controllable rectifier bridge. The equivalent impedance of the load of the uncontrolled rectifier bridge is approximately pure resistive in the above, but due to the influence of higher harmonic currents, the equivalent impedance is resistive, and fig. 12 shows the input side voltage and current waveforms of the uncontrolled rectifier bridge, and it is obvious that the fundamental current lags behind the fundamental voltage. Neglecting parasitic parameters in the circuit, equation (11) gives the equivalent impedance expression of the rectifier bridge load and the power transmission energyForce expression:
wherein Z is rec For the equivalent impedance of the load of the rectifier bridge, P cap And theta is the equivalent impedance angle of the load of the rectifier bridge, which is the power transmission capacity of the novel non-contact single-tube resonant converter under the uncontrolled rectification. According to the embodiment, the phase relation between the input side fundamental wave voltage and the fundamental wave current of the rectifier bridge is adjusted by controlling the on-off of the bridge arm of the rectifier bridge, so that the aim of adjusting the equivalent impedance of the rectifier bridge to be pure resistance is achieved. FIG. 13 shows the control logic of the controllable rectifier bridge, when i rec When changing from positive to negative, S 3 Body diode D of (2) 02 Turn on and off after a period of time S 4 At D 02 On period of on S 3 The method comprises the steps of carrying out a first treatment on the surface of the When i rec From negative to positive, S 4 Body diode D of (2) 03 Turn on and off after a period of time S 3 At D 03 On period of on S 4 The method comprises the steps of carrying out a first treatment on the surface of the Order D 02 The conduction time is the starting time t a ，S 4 The turn-off time is t b Or D 03 The conduction time is the starting time t a ，S 3 The turn-off time is t b Definition D ctr ＝1-2(t b -t a ) T, when D ctr When the equation (12) is satisfied, the equivalent impedance of the rectifier bridge load can be adjusted to be pure impedance, as shown in fig. 14, i.e. cosθ=1, the inductance of the secondary folding impedance disappears, according to the above I ac As can be seen from the expression (8) of (C), I ac And also increases. Thus, in combination with formula (11), the use of a controllable rectifier bridge can improve the power transfer capability of the non-contact single-tube resonant converter.
Example IV
Fig. 15 is a schematic structural diagram of a fourth embodiment of the novel non-contact single-tube resonant converter of the present invention. As shown in fig. 15, L p And C r1 Connected in parallelThen one end is connected with the positive electrode of the power supply, the other end is connected with the drain electrode of the S, the source electrode of the S is connected with the negative electrode of the power supply, C r2 Connected in parallel at two ends S, L s And C 1 After being connected in series, is connected with C 2 Connected in parallel and then with L 2 Connected in series and finally connected to the midpoints of two bridge arms of the uncontrolled rectifier bridge, C o And R is R L And after being connected in parallel, the output terminals of the uncontrolled rectifier bridge are connected in parallel. The parameter design method of this embodiment is the same as that of embodiment one, wherein C r ＝C r1 +C r2 ，C r1 And C r2 The size relation of (2) may be arbitrarily configured.
Example five
Fig. 16 is a schematic structural diagram of a fourth embodiment of the novel non-contact single-tube resonant converter of the present invention. As shown in fig. 16, L p One end of the capacitor is connected with the positive electrode of the power supply, the other end of the capacitor is connected with the drain electrode of the S, the source electrode of the S is connected with the negative electrode of the power supply, C r2 Connected in parallel at two ends S, L s And C 1 After being connected in series, is connected with C 2 Connected in parallel and then with L 2 Connected in series and finally connected to the midpoints of two bridge arms of the uncontrolled rectifier bridge, C o And R is R L And after being connected in parallel, the output terminals of the uncontrolled rectifier bridge are connected in parallel. The parameter design method of this embodiment is the same as that of embodiment one, wherein C r ＝C r2 。
The secondary side adopts a high-order compensation network and is matched with reasonable parameter design, so that the quasi-constant current output can be realized, good closed-loop regulation characteristic is provided for wireless charging, soft switching on of a switching tube is realized, voltage stress and current stress of the switching tube are reduced, the degree of freedom of parameter design is increased, and the method can be suitable for different output indexes. The invention also provides a secondary side which adopts the controllable rectifier bridge, adjusts the load property of the rectifier bridge, improves the power transmission capacity of the novel non-contact single-tube resonant converter, and greatly improves the application value of the non-contact single-tube circuit.
The foregoing is merely a preferred embodiment of the present invention and it should be noted that modifications and adaptations to those skilled in the art may be made without departing from the principles of the present invention, which are intended to be comprehended within the scope of the present invention.
Claims (7)
1. A non-contact single tube resonant converter, characterized by: comprises a primary side and a secondary side; wherein: the primary side comprises a resonance inversion module; the resonance inversion module comprises a primary inductor L p A switch tube S, the primary side inductance L p Is connected in series with a switching tube S and then is connected in parallel with an input voltage V in Both ends also include the inductance L at the primary side p And/or the switch tubes S are respectively connected with the resonant capacitors in parallel; the secondary side comprises secondary side inductors L which are connected in sequence s A high-order compensation network and a rectification module; primary inductance L p And secondary inductance L s Coupling;
the resonance capacitor meets the following requirements, so that primary side inductance current in the resonance inversion module has quasi-constant current characteristics, zero voltage switching on is realized under light load of the switching tube S, and zero voltage and zero current switching on are simultaneously realized under heavy load;
when the primary inductance L p And the switch tube S are respectively connected with a first resonant capacitor C in parallel r1 And a second resonance capacitor C r2 When (1):
when the primary inductance L p Or a parallel resonance capacitor C on the switching tube S r When (1):
wherein R is e For the secondary folding resistance, deltat is the turn-off time of a switching tube S in the primary resonant inversion module, and W is the resonant capacitance and the primary inductance L when the switching tube S in the primary resonant inversion module is turned off p The sum of the stored energies.
2. The non-contact single tube harmonic of claim 1The vibration transducer is characterized in that: the high-order compensation network is composed of a first compensation capacitor C 1 Second compensation capacitor C 2 Resonant inductance L 2 Composition of the secondary inductance L s And a first compensation capacitor C 1 After being connected in series, the capacitor is connected with a second compensation capacitor C 2 Connected in parallel and then with resonant inductance L 2 Are connected in series; the high-order compensation network parameters meet the following requirements, so that the non-contact single-tube resonant converter has quasi-constant current output characteristics:
wherein w is the switching angular frequency of the switching tube S.
3. The non-contact single tube resonant converter of claim 1, wherein: the high-order compensation network consists of a compensation capacitor C and a resonance inductance L 2 Composition of the secondary inductance L s Is connected in parallel with the compensation capacitor C and then is connected with the resonant inductor L 2 Are connected in series; the parameters of the high-order compensation network are required to meet the following requirements, so that the non-contact single-tube resonant converter has quasi-constant current output characteristics:
wherein w is the switching angular frequency of the switching tube S.
4. A non-contact single tube resonant converter according to claim 2 or 3, characterized in that: the rectification module comprises a rectifier and a filter, wherein the rectifier is a current doubler rectification or a voltage doubler rectification, and the filter is an LC filter or a C filter.
5. The non-contact single tube resonant converter of claim 4, wherein the rectifier is a controllable rectifier bridge, two bridgesArms each consisting of a diode connected in series with a MOSFET, the MOSFET being the lower tube, the MOSFET having a control characteristic D ctr The following formula is satisfied, so that the equivalent impedance of the rectifier bridge load is pure resistance;
wherein R is L Is the load resistance.
6. The non-contact single tube resonant converter of claim 2, wherein: the resonant capacitor in the resonant inversion module, the compensation capacitor in the high-order compensation network and the filter capacitor in the rectification module are composed of a plurality of capacitors which are connected in series and/or in parallel; the resonant inductance in the high-order compensation network and the filter inductance in the rectification module are composed of a plurality of inductances which are connected in series and/or in parallel.
7. A non-contact single tube resonant converter according to claim 3, wherein: the resonant capacitor in the resonant inversion module, the compensation capacitor in the high-order compensation network and the filter capacitor in the rectification module are composed of a plurality of capacitors which are connected in series and/or in parallel; the resonant inductance in the high-order compensation network and the filter inductance in the rectification module are composed of a plurality of inductances which are connected in series and/or in parallel.
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