CN209787128U - Transimpedance amplifier and transimpedance amplifier circuit - Google Patents
Transimpedance amplifier and transimpedance amplifier circuit Download PDFInfo
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- CN209787128U CN209787128U CN201920278410.0U CN201920278410U CN209787128U CN 209787128 U CN209787128 U CN 209787128U CN 201920278410 U CN201920278410 U CN 201920278410U CN 209787128 U CN209787128 U CN 209787128U
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Abstract
A transimpedance amplifier with direct current drift elimination function and automatic gain control function, it includes amplifier, transimpedance feedback loop, direct current drift elimination and automatic gain control loop; the direct current drift elimination and automatic gain control loop is respectively connected with the input end and the output end of the amplifier so as to match the direct current component in the input current signal and eliminate the direct current drift; and meanwhile, the electrical parameters of the loop are adjusted according to the magnitude of the output voltage signal so as to adjust the gain of the whole trans-impedance amplifier circuit. Therefore, compared with the traditional trans-impedance amplifier circuit, the direct current drift elimination function and the automatic gain control function are simultaneously realized by one circuit branch, the shape of a frequency response curve, the circuit bandwidth and the phase margin are not influenced, and the stability of the circuit is improved.
Description
Technical Field
The application belongs to the field of microelectronic circuits, and particularly relates to a Trans-Impedance Amplifier (TIA) and a Trans-Impedance Amplifier circuit integrating direct current drift elimination and automatic gain control functions.
Background
Transimpedance amplifiers are commonly used in optical signal receiving equipment systems, such as optical sensors and optical fiber communication systems, and perform amplification of weak electrical signals after optical signals are converted into electrical signals.
In the transimpedance amplifier circuit, a dc servo loop is generally required to eliminate the influence of the input dc current, so that the operating point of the transimpedance amplifier is not affected by the dc electrical signal input from the optical signal through the photodiode. In addition, since the variation range of the intensity of the input optical signal is relatively large, an Automatic Gain Control (AGC) circuit is required in the transimpedance amplifier circuit to adjust the Gain of the transimpedance amplifier, so as to obtain better load performance.
The conventional transimpedance amplifier generally adjusts the gain of the transimpedance amplifier by adjusting the resistance in the transimpedance feedback loop, but such a design may affect the stability of the circuit, and the frequency response characteristic of the corresponding transimpedance amplifier circuit may also be affected. For example, one loop is used to implement the dc drift cancellation function, and the other loop is used to adjust the feedback resistance to implement the automatic gain control. In actual practice, however, reducing the feedback resistance by reducing the resistance of the transistor will reduce the phase margin of the "and-and" feedback circuit, thereby causing stability problems. Even though the TIA system may still operate, the shape of the frequency response curve may change significantly as the degeneration resistance changes.
Disclosure of Invention
The application provides a transimpedance amplifier and a transimpedance amplifier circuit, and aims to solve the problem that when a gain of a traditional transimpedance amplifier is adjusted through adjusting a feedback resistor, the stability and the frequency response characteristic of the circuit are affected.
A first aspect of an embodiment of the present application provides a transimpedance amplifier, including:
An amplifier configured to amplify an input signal;
A transimpedance feedback loop connected between the input and output of the amplifier to provide negative feedback for the amplifier;
the direct current drift elimination and automatic gain control loop is respectively connected with the input end and the output end of the amplifier so as to match the direct current component in the input current signal and eliminate the direct current drift; and meanwhile, the electrical parameters of the control loop are adjusted according to the magnitude of the voltage signal output by the amplifier so as to adjust the gain of the whole transimpedance amplifier circuit.
A second aspect of the embodiments of the present application provides a transimpedance amplifier circuit including:
A pre-transimpedance amplifier which is the transimpedance amplifier as described above;
The first input end of the limiting amplifier is connected with the output end of the pre-transimpedance amplifier; the limiting amplifier can have one or more stages of limiting amplifier cascade connection according to the requirement of the output amplitude in practical application.
two input ends of the output buffer are connected with two output ends of the limiting amplifier, and two output ends of the output buffer are used as output ends of the transimpedance amplifier circuit; and
two input ends of the feedback loop are connected with two output ends of the output buffer, and the output end of the feedback loop is connected with the second input end of the limiting amplifier;
And the input end of the direct current drift elimination and automatic gain control loop is connected with the two output ends of the limiting amplifier or the two output ends of the output buffer.
The transimpedance amplifier and the transimpedance amplifier circuit integrate the functions of direct current drift elimination and automatic gain control into a loop network, the loop network not only can eliminate input direct current, but also can automatically control the gain of the transimpedance amplifier, and the loop network is not arranged in a transimpedance feedback loop of the transimpedance amplifier, so that the parameter change of the loop network does not influence the phase margin, the shape of a frequency response curve, the circuit bandwidth, the phase margin and the stability of the feedback of the amplifier.
Drawings
Fig. 1 is a schematic structural diagram of a transimpedance amplifier according to an embodiment of the present application;
fig. 2 is a schematic structural diagram of a transimpedance amplifier circuit according to an embodiment of the present application;
Fig. 3 is a schematic structural diagram of a transimpedance amplifier according to another embodiment of the present application;
Fig. 4 is a schematic circuit diagram of a transimpedance amplifier according to an embodiment of the present application.
Detailed Description
In order to make the objects, technical applications and advantages of the present application more apparent, the present application is described in further detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the present application and are not intended to limit the present application.
Referring to fig. 1, a transimpedance amplifier 10 according to an embodiment of the present application is generally used as an input current signal IinAmplifies and converts into a voltage signal VoutThe transimpedance amplifier 10 of the present embodiment includes an amplifier Tz, a transimpedance feedback loop 11, and a dc drift cancellation and automatic gain control loop 12.
The amplifier Tz is configured to amplify an input signal; a transimpedance feedback loop 11 is connected between the input of the amplifier Tz andNegative feedback is provided for the amplifier between the output ends of the amplifier Tz; the control loop 12 is connected to the input and output of the amplifier Tz for matching the input current signal IinD.c. component I ofDEliminating direct current drift; while according to the voltage signal V output by the amplifier TzoutAdjusts the electrical parameters of the control loop 12 to adjust the gain of the overall transimpedance amplifier circuit 10.
The transimpedance amplifier 10 integrates the dc drift cancellation and automatic gain control functions into a loop network, which not only can cancel the input dc current, but also can automatically control the gain of the transimpedance amplifier, and the loop network is not in the transimpedance feedback loop of the transimpedance amplifier, so that the parameter variation of the loop network does not affect the phase margin, the shape of the frequency response curve, and the stability of the feedback of the amplifier.
in some exemplary applications, referring to fig. 2, a pre-transimpedance amplifier, i.e., the transimpedance amplifier 10 described above, is generally used in conjunction with a photodiode D2, the photodiode D2 being configured to receive an optical signal and convert the optical signal to a current signal IinMost of the optical signal is directly converted into a current signal Iinthe current is weak, so that the pre-transimpedance amplifier 10 is required to perform transimpedance amplification on the current converted by the photodiode D2; in addition, the current signal IinComprising a direct current component I carrying no informationDAnd an information-carrying alternating current component IA. The pre-transimpedance amplifier 10 converts the single-ended current signal IAconversion to single-ended voltage signal Vout(ii) a At the same time, the single-ended voltage signal V is fed back by means of the feedback loop 40outConverted into a pair of voltage differential signals OUTP/OUTN at the limiting amplifier 20, and further amplified to a sufficiently large amplitude, and then outputted through the output buffer 30, i.e. the voltage signal VoutSingle-ended voltage signal V for output of amplifier TzoutThe voltage difference signal OUTP \ OUTN output by the pair of limiting amplifiers 20 or output buffer may be used.
in one embodiment, referring to FIG. 3, the control loop 12 includes a bypass networkA complex 121 and a gain control unit 122. The bypass network 121 is connected to the input of the amplifier Tz and is configured to match the I in the input current signalindirect current component I ofDfor eliminating DC drift, in particular for current signals IinD.c. component I ofDShunting to eliminate DC drift. The input terminal of the gain control unit 122 is connected to the common node of the transimpedance feedback loop 11 and the output terminal of the amplifier Tz, and is connected to the voltage signal VoutAnd connected to the bypass network 121, configured to be dependent on the voltage signal VoutAdjusts the electrical parameter of the bypass network 121 to adjust the current signal I connected to the input of the amplifier TzAIn order to adjust the gain of the transimpedance amplifier 10.
Referring to fig. 3 and 4, the resistance of the bypass network 121 is adjustable, specifically, the resistance changes according to the variation of the loaded voltage, and the gain control unit 122 detects the voltage signal Voutto adjust the resistance of the bypass network 121 to achieve current regulation and thereby regulate the ac component I of the input current signal coupled to the amplifier TzAto achieve automatic gain control.
The automatic gain control of the transimpedance amplifier 10 is achieved by reducing the resistance of the bypass network 121 if there is no alternating component I of the signal currentAFlows through bypass network 121, and the resistance of bypass network 121 is equal to infinity, at which time amplifier Tz operates at maximum gain. When the current signal IinWhen the voltage is larger, the resistance of the bypass network 121 is smaller, so that the alternating current component I of partial signal current is smallerAFlows away through bypass network 121 and does not enter amplifier Tz, thereby reducing VoutThus, automatic gain control is realized. In addition, the voltage controlled bypass network 121 is not in the transimpedance (negative) feedback loop 11 of the amplifier Tz, so that variations in the parameters of the bypass network 121 do not affect the phase margin and stability of the transimpedance amplifier and feedback. Therefore, on the premise of not influencing the frequency response characteristic, the transimpedance amplifier has better linear amplification capacity, and the overload resistance and the dynamic range are improved.
In one embodiment, please refer toIn fig. 4, the bypass network 121 includes a unidirectional device and a voltage divider, the input of the unidirectional device is connected to the input of the amplifier Tz, and the output of the unidirectional device is grounded via the voltage divider. The gain control unit 122 comprises an operational amplifier U1, a voltage signal V is connected to the input end of the operational amplifier U1outAnd the output end of the operational amplifier U1 is connected with the output end of the unidirectional conducting device. The resistance of the unidirectional device varies according to the variation of the voltage applied across it, i.e. the voltage V at the input of the amplifier TzinAnd the output voltage of the operational amplifier U1. For example, the one-way conduction device is a diode D1, so as to reduce the circuit cost. In other embodiments, the unidirectional conducting device may be a transistor processed to have diode characteristics, such as a triode or a field effect transistor shorting two of its electrodes. The voltage divider includes a resistor R1, and may further include a capacitor, a semiconductor device, and the like.
As described above, the voltage signal Voutsingle-ended voltage signal V for output of amplifier TzoutOr may be a pair of voltage differential signals. Wherein the voltage signal VoutIs a single-ended voltage signal VoutThe voltage is input to one input of an operational amplifier U1, and a reference voltage Vref may be added to the other input. Voltage signal Voutin the case of a pair of voltage differential signals, the reference voltage Vref does not need to be added.
Specifically, referring to FIG. 4, the bypass current flows through diode D1 and resistor R1 when the current signal I is assertedinWhen the voltage is too high, the control voltage from the output of the operational amplifier U1 is reduced and the voltage applied to the diode D1 is increased, so that more current flows through the diode D1, which ensures that the amplifier Tz operates under constant operating conditions.
In this embodiment, the automatic gain control function is achieved by reducing the resistance r of the diode D1D1to achieve this, the total resistance R1 of the bypass network 121 is equal to the resistance R of the diode D1D1And resistance R1R1Addition, where rD1＝Vin/ID1＝26mV/ID1. If no current flows through diode D1, the resistance of bypass network 121 equals infinity, at this timeThe transimpedance amplifier 10 operates in a maximum gain state. When inputting current signal IinWhen the comparison is large, the control voltage output by the operational amplifier U1 is reduced, and the voltage drop across the diode D1 is increased, so that the resistance r of the diode D1 is increasedD1Becomes smaller so as to bypass the current I of the network 121D1increase, the current ID1Flows through bypass network 121 to ground, thereby reducing the ac component I of the input current signal to amplifier TzAThus, automatic gain control is realized. The automatic gain control in this application does not change the feedback resistance RFTherefore, the frequency response of the (transimpedance) transimpedance amplifier 10 is not affected, nor is the stability of the transimpedance amplifier 10 affected. In other embodiments, the resistance R of the resistor R1 can be adjustedR1To implement the automatic gain control function.
In one embodiment, referring to fig. 1, 3 and 4, the transimpedance feedback loop 11 includes a first feedback resistor RFFirst feedback resistance RFConnected in series between the input and output of the amplifier Tz. The present application does not need to adjust the parameter (such as resistance) of the transimpedance feedback loop 11 to realize the automatic gain control, and therefore, only one feedback resistor R may be usedFA transimpedance feedback loop 11 is provided. In other embodiments, the feedback loop 11 may further include a feedback resistor RFCapacitors, transistors, etc. arranged in series-parallel.
In one example, a transimpedance amplifier 10 operating at 25Gb/s is designed and may be integrated on a chip with an average input signal current from the photodiode of about 5uA and the resistor R1 of the bypass network 121 selected to be 5.2k Ω to ensure high gain and low noise on the circuit chip. According to the above analysis, the variable resistor R1 of the bypass network 121 enables the chip to have an automatic gain control function, which improves the load capability of the chip under high input current, so that the output of the chip is more linear. For a 100G/400G coherent optical communication system, especially a PAM4(4Pulse amplitude modulation) modulation system, the linearity of the chip output is very important. Compared with a chip using the variable feedback resistor RF, since the variable resistor bypass network 121 employed in the present application is not in the negative feedback loop of the amplifier Tz, the gain of the chip can be adjusted without affecting the frequency response performance of the chip.
Referring to fig. 2, an embodiment of the present invention further provides a transimpedance amplifier circuit 100, where the transimpedance amplifier circuit 100 includes a pre-transimpedance amplifier, a limiting amplifier 20, an output buffer 30, and a feedback loop 40.
the pre-transimpedance amplifier is the transimpedance amplifier 10; the first input end of the limiting amplifier 20 is connected with the output end of the pre-transimpedance amplifier 10; two input ends of the output buffer 30 are connected to two output ends of the limiting amplifier 20, and two output ends of the output buffer 30 are used as output ends of the transimpedance amplifier circuit 100; two input ends of the feedback loop 40 are connected with two output ends of the output buffer 30, and the output end of the feedback loop 40 is connected with a second input end of the limiting amplifier 20; wherein, the input terminal of the dc drift cancellation and automatic gain control loop 12 in the transimpedance amplifier 10 is connected to the two output terminals of the limiting amplifier 20 or the two output terminals of the output buffer 30 to connect the voltage signal Vout。
In an optical sensor and an optical fiber communication system, an input end of a pre-transimpedance amplifier 10 is generally connected with an anode of a photodiode D2, a cathode of a photodiode D2 is connected with a power supply voltage VPD, incident light is converted into photocurrent through the photodiode D2, and the photocurrent converts a single-ended current signal into a single-ended voltage signal through the pre-transimpedance amplifier 10. Thereafter, the limiting amplifier 20 converts the single-terminal voltage signal into a double-terminal voltage differential signal, and inputs the double-terminal voltage differential signal to the output buffer 30. Alternatively, the limiting amplifier 20 and the output buffer 30 are both CML (Current-Mode Logic) devices.
In one embodiment, the transimpedance amplifier circuit 100 further includes a first differential load resistor R3 and a second differential load resistor R4, the first differential load resistor R3 and the second differential load resistor R4 being respectively connected between the two output terminals of the output buffer 30 and the power supply Vcc 1. The first and second differential load resistors R3 and R4 also act as load resistors for the entire circuit output.
In some embodiments, the feedback loop 40 includes an operational amplifier 41, two input terminals of the operational amplifier 41 are respectively connected to two output terminals of the output buffer 30, and an output terminal of the second operational amplifier 41 is connected to the second input terminal of the limiting amplifier 20. Optionally, two input terminals of the second operational amplifier 41 are respectively connected to two output terminals of the output buffer 30 through a current limiting resistor R5 and a current limiting resistor R6, and two input terminals of the second operational amplifier 41 are directly connected to a filter capacitor C1.
Optionally, an inverting input terminal of the pre-transimpedance amplifier 10 is connected to an anode of the photodiode D2, a non-inverting input terminal of the second operational amplifier 41 is connected to a non-inverting output terminal of the output buffer 30, and an inverting input terminal of the second operational amplifier 41 is connected to an inverting output terminal of the output buffer 30.
One application field of the present application is high-speed optical communication technology, for example, in a 100G/200G/400G high-speed optical communication system, the transimpedance amplifier circuit 100 and the transimpedance amplifier 10 designed by using the technology proposed in the present application have better linear amplification capability on the premise of not affecting the chip frequency response characteristic, and the overload resistance and the dynamic range of the transimpedance amplifier circuit 100 and the transimpedance amplifier 10 are both improved. Although the transimpedance amplifier circuit 100 and the transimpedance amplifier 10 are proposed to be applied to the field of high-speed optical communication, the application fields thereof are not limited thereto, and the technique proposed in the present application can be applied to any similar application to improve the performance of the circuit.
The comparison test of the high-speed transimpedance amplifier 10 chip adopting the technology proposed by the application and the high-speed transimpedance amplifier 10 chip not adopting the technology proposed by the application proves that the chip adopting the transimpedance amplifier 10 adopting the technology proposed by the application can change the gain of the circuit under the condition of keeping the frequency response characteristic unchanged, the dynamic range of the circuit is increased by 50 percent, and the overload resistance is obviously improved.
The above description is only exemplary of the present application and should not be taken as limiting the present application, as any modification, equivalent replacement, or improvement made within the spirit and principle of the present application should be included in the protection scope of the present application.
Claims (10)
1. a transimpedance amplifier, comprising:
An amplifier configured to amplify an input signal;
A transimpedance feedback loop connected between the input and output of the amplifier to provide negative feedback for the amplifier;
The direct current drift elimination and automatic gain control loop is respectively connected with the input end and the output end of the amplifier so as to match the direct current component in the input current signal and eliminate the direct current drift; and meanwhile, the electrical parameters of the control loop are adjusted according to the magnitude of the voltage signal output by the amplifier so as to adjust the gain of the whole transimpedance amplifier circuit.
2. The transimpedance amplifier according to claim 1, wherein the dc drift cancellation and automatic gain control loop comprises:
A bypass network connected to the input of the amplifier and configured to match a dc component in the input current signal to eliminate dc drift; and
And the gain control unit is connected into the voltage signal and is connected with the bypass network, and is configured to adjust the electrical parameter of the bypass network according to the magnitude of the voltage signal so as to adjust the gain of the whole transimpedance amplifier circuit.
3. the transimpedance amplifier according to claim 2, wherein a resistance of the bypass network is adjustable.
4. The transimpedance amplifier according to claim 2, wherein a resistance of the bypass network varies according to a variation of the applied voltage.
5. A transimpedance amplifier according to claim 2, 3 or 4, wherein said bypass network comprises a unidirectionally conducting device and a voltage dividing device, an input of said unidirectionally conducting device being connected to an input of said transimpedance amplifier, an output of said unidirectionally conducting device being connected to ground through said voltage dividing device.
6. The transimpedance amplifier according to claim 5, wherein the unidirectional conducting device is a diode or a transistor having a diode characteristic; the voltage dividing device includes a resistor.
7. The transimpedance amplifier according to claim 5, wherein the gain control unit comprises an operational amplifier, wherein an input terminal of the operational amplifier is connected to the voltage signal, and an output terminal of the operational amplifier is connected to an output terminal of the one-way conduction device.
8. The transimpedance amplifier according to claim 1, wherein the feedback loop comprises a first feedback resistor connected in series between the input and output of the transimpedance amplifier.
9. A transimpedance amplifier circuit comprising:
A pre-transimpedance amplifier according to any one of claims 1 to 8;
the first input end of the limiting amplifier is connected with the output end of the pre-transimpedance amplifier; according to the requirement of the output amplitude in practical application, the limiting amplifier can be cascaded by one or more stages of limiting amplifiers;
Two input ends of the output buffer are connected with two output ends of the limiting amplifier, and two output ends of the output buffer are used as output ends of the transimpedance amplifier circuit; and
Two input ends of the feedback loop are connected with two output ends of the output buffer, and the output end of the feedback loop is connected with the second input end of the limiting amplifier;
And the input end of the direct current drift elimination and automatic gain control loop is connected with the two output ends of the limiting amplifier or the two output ends of the output buffer.
10. The transimpedance amplifier circuit according to claim 9, further comprising a first differential load resistor and a second differential load resistor, the first differential load resistor and the second differential load resistor being respectively connected between two output terminals of the output buffer and a power supply;
The feedback loop comprises an operational amplifier, two input ends of the operational amplifier are respectively connected with two output ends of the output buffer, and the output end of the operational amplifier is connected with the second input end of the limiting amplifier.
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| Application Number | Priority Date | Filing Date | Title |
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| CN201920278410.0U CN209787128U (en) | 2019-03-05 | 2019-03-05 | Transimpedance amplifier and transimpedance amplifier circuit |
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| CN201920278410.0U CN209787128U (en) | 2019-03-05 | 2019-03-05 | Transimpedance amplifier and transimpedance amplifier circuit |
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109861661A (en) * | 2019-03-05 | 2019-06-07 | 深圳市傲科光电子有限公司 | A kind of trans-impedance amplifier and trans-impedance amplifier circuit |
| CN111726099A (en) * | 2020-07-27 | 2020-09-29 | 厦门亿芯源半导体科技有限公司 | Accurate automatic gain control circuit |
| CN113067553A (en) * | 2021-03-17 | 2021-07-02 | 中国科学院近代物理研究所 | Electronic cooling modulation method and device for feedback type pulse linear amplification |
-
2019
- 2019-03-05 CN CN201920278410.0U patent/CN209787128U/en active Active
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109861661A (en) * | 2019-03-05 | 2019-06-07 | 深圳市傲科光电子有限公司 | A kind of trans-impedance amplifier and trans-impedance amplifier circuit |
| CN111726099A (en) * | 2020-07-27 | 2020-09-29 | 厦门亿芯源半导体科技有限公司 | Accurate automatic gain control circuit |
| CN113067553A (en) * | 2021-03-17 | 2021-07-02 | 中国科学院近代物理研究所 | Electronic cooling modulation method and device for feedback type pulse linear amplification |
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