CN204559246U - Based on the magnet coupled resonant type wireless power transfer of low frequency PWM rectifier - Google Patents

Abstract

The utility model discloses a kind of magnet coupled resonant type wireless power transfer based on low frequency PWM rectifier, comprise rectifier, electric capacity of voltage regulation, inverter power switch, radiating circuit resonant capacitance, radiating circuit resonance coil, radiating circuit current sampling resistor, receiving circuit resonance coil, receiving circuit current sampling resistor, rectified power switch, resonator, filter electric capacity, resonator, filter inductance, load resistance, transmitting terminal signal conditioning circuit, transmitting terminal analog to digital converter, transmitting terminal microprocessor, transmitting terminal high-frequency inversion drive circuit, induced voltage magnetic test coil, receiving end signal modulate circuit, receiving terminal analog to digital converter, receiving terminal microprocessor and PWM rectifier drive circuit, the utility model ensure that the resonance of launching circuit achieves the constant output of the tracking of transmitting terminal operating frequency, the resonance of receiving circuit and load voltage, greatly reduce the requirement to device for power switching operating frequency, and provide space for device improves power work frequency.

Description

Based on the magnet coupled resonant type wireless power transfer of low frequency PWM rectifier

Technical field

The utility model belongs to wireless power transmission technical field, particularly relates to a kind of magnet coupled resonant type wireless power transfer, specifically a kind of magnet coupled resonant type wireless power transfer based on low frequency PWM rectifier.

Background technology

Wireless power transmission is a kind of delivery of electrical energy mode flexible and convenient to use, which overcomes the problems such as contact wear, easily the generation electric spark existed in conventional wires transmission means, improves the security reliability of system.Current wireless power transmission is mainly divided into radiant type, induction and magnet coupled resonant type three types of technology, and wherein magnet coupled resonant type wireless electric energy transmission technology needs to have obvious advantage when taking into account transmission range and through-put power at the same time.

Desirable magnet coupled resonant type wireless delivery of electrical energy is that radiating circuit by having identical resonance frequency and receiving circuit occur to resonate and realize under high frequency pumping, and therefore tuning is the key technology of magnet coupled resonant type wireless delivery of electrical energy.For the tuning problem existed in magnet coupled resonant type wireless delivery of electrical energy, the method generally adopted at present mainly contains and regulates supply frequency and the resonant network such as control capacittance or inductance component parameters two kinds.When regulating supply frequency, radiating circuit can understand the operating state of receiving circuit by the isoparametric monitoring of the electric current to receiving circuit, voltage and power output, and correspondingly regulates supply frequency to reach the state of system resonance.But when radiating circuit and single or multiple receiving circuit resonance frequency inconsistent time, regulate the method for supply frequency to ensure high efficiency delivery of electrical energy and the effective power supply to each load by being difficult to.Adopt control capacittance array to carry out tuning method and there is the discontinuous problem of controlled quentity controlled variable.Being tuned on a large scale when regulating of phased inductance can introduce larger harmonic wave, is therefore often used in the fine setting carried out near resonance frequency.For receiving circuit, when the induced voltage of receiving circuit resonance coil is consistent with current phase, receiving circuit reaches resonance, therefore can using the reference quantity of the induced voltage of receiving circuit resonance coil as the tuning control of receiving circuit.But the induced voltage of the receiving circuit resonance coil wanting Measurement accuracy to have electric current to flow through is more difficult, this is because receiving circuit resonance coil itself also exists resistance and self-induction.If directly measure the port voltage of receiving circuit resonance coil, then calculate and deduct the pressure drop of resistance and self-induction, so measure error of resistance, self-induction and resonance coil electric current, and in running, the change etc. of resistance and self-induction all can affect the accuracy of measurement of resonance coil induced voltage.Except tuning, the high-frequency electrical energy that receiving circuit receives generally needs just can power to the load through over commutation.Usually uncontrollable diode bridge rectification is adopted to obtain VD at present, but the uncertainty due to wireless transmission distance causes the change of mutual inductance between radiating circuit and receiving circuit coupled resonance coil, thus make the amplitude of this VD can not keep constant, have impact on use.Therefore a kind of magnet coupled resonant type wireless power transfer based on low frequency PWM rectifier is proposed here, it utilizes and is arranged on the induced voltage that the double-induction pressure magnetic test coil accepting circuit side detects receiving circuit resonance coil, and using the reference quantity of this induced voltage as the tuning control of receiving circuit, utilize half-bridge PWM rectifier to realize the resonance control of receiving circuit and the output of constant voltage simultaneously, regulate the high frequency electric source frequency of radiating circuit to realize the resonance of radiating circuit simultaneously, when high frequency electric source frequency changes, the Frequency Synchronization of the induced voltage of the receiving circuit resonance coil that double-induction pressure magnetic test coil detects changes, therefore half-bridge PWM rectifier can follow the tracks of high frequency electric source frequency change and realize receiving circuit resonance control, and half-bridge PWM rectifier adopts low frequency pulse modulation technology, reduce the requirement of power switch operating frequency, magnet coupled resonant type wireless power transfer so is at present there are no patent and other bibliographical information.

Summary of the invention

The problems referred to above being prior art exists to be solved in the utility model aim to provide a kind of magnet coupled resonant type wireless power transfer based on low frequency PWM rectifier, the receiving circuit of this device can realize resonance condition on the basis of following the tracks of the change of radiating circuit supply frequency, utilizes low frequency pulse modulation technology to reduce the requirement of PWM rectifier power switch operating frequency simultaneously.

The technical solution of the utility model: based on the magnet coupled resonant type wireless power transfer of low frequency PWM rectifier, it comprises rectifier, first electric capacity of voltage regulation, second electric capacity of voltage regulation, first inverter power switch, second inverter power switch, radiating circuit resonant capacitance, radiating circuit resonance coil, radiating circuit current sampling resistor, receiving circuit resonance coil, receiving circuit current sampling resistor, first rectified power switch, second rectified power switch, 3rd electric capacity of voltage regulation, 4th electric capacity of voltage regulation, resonator, filter electric capacity, resonator, filter inductance, load resistance, transmitting terminal signal conditioning circuit, transmitting terminal analog to digital converter, transmitting terminal microprocessor, transmitting terminal high-frequency inversion drive circuit, first induced voltage magnetic test coil, second induced voltage magnetic test coil, receiving end signal modulate circuit, receiving terminal analog to digital converter, receiving terminal microprocessor and PWM rectifier drive circuit, first electric capacity of voltage regulation, second electric capacity of voltage regulation, first inverter power switch and the second inverter power switch form half-bridge inverter, two lead-out terminals of two direct-flow input end sub-connection rectifiers of half-bridge inverter, two lead-out terminals of half-bridge inverter connect one end of radiating circuit resonant capacitance and one end of radiating circuit current sampling resistor respectively, the other end of radiating circuit resonant capacitance is connected with one end of radiating circuit resonance coil, the other end of radiating circuit current sampling resistor is connected with the other end of radiating circuit resonance coil, the voltage signal at the voltage between two of half-bridge inverter lead-out terminals and radiating circuit current sampling resistor two ends is carried out two input ports nursing one's health rear feeding transmitting terminal analog to digital converter by transmitting terminal signal conditioning circuit, transmitting terminal microprocessor accepts the digital signal from transmitting terminal analog to digital converter and produces the square wave control signal of frequency-adjustable as calculated afterwards, this square wave control signal drives the power switch of half-bridge inverter by high-frequency inversion drive circuit, first rectified power switch, second rectified power switch, 3rd electric capacity of voltage regulation and the 4th electric capacity of voltage regulation form half-bridge PWM rectifier, two input terminals of half-bridge PWM rectifier AC connect one end of receiving circuit resonance coil and one end of receiving circuit current sampling resistor respectively, the other end of receiving circuit resonance coil is connected with the other end of receiving circuit current sampling resistor, two lead-out terminals of half-bridge PWM rectifier DC side connect one end of resonator, filter electric capacity and one end of resonator, filter inductance respectively, the other end of resonator, filter electric capacity is connected with the other end of resonator, filter inductance, and two lead-out terminals of half-bridge PWM rectifier DC side connect two terminals of load resistance respectively, radiating circuit resonance coil and receiving circuit resonance coil parallel coaxial are placed also at intervals, first induced voltage magnetic test coil, second induced voltage magnetic test coil and receiving circuit resonance coil are coaxially fixed in same plane, first induced voltage magnetic test coil, the coil radius of the second induced voltage magnetic test coil and receiving circuit resonance coil is different, the non-same polarity of the first induced voltage magnetic test coil is connected with the non-same polarity of the second induced voltage magnetic test coil, the Same Name of Ends of the first induced voltage magnetic test coil is connected with first input port of receiving end signal modulate circuit with the Same Name of Ends of the second induced voltage magnetic test coil, the two ends of receiving circuit current sampling resistor are connected with second input port of receiving end signal modulate circuit, the two ends of load resistance are connected with the 3rd of receiving end signal modulate circuit the input port, the output signal of receiving end signal modulate circuit is through receiving terminal analog to digital converter input receiving terminal microprocessor, low frequency pulse-width modulation waveform is produced after receiving terminal microprocessor calculates, and the power switch of half-bridge PWM rectifier is driven by PWM rectifier drive circuit, two input terminals of rectifier are the power input port of device, two lead-out terminals of half-bridge PWM rectifier DC side are the DC voltage output end mouth of device.

Below the principle of the technical program is described further.

(1) basic functional principle

The receiving circuit of this device is made up of receiving circuit resonance coil, half-bridge PWM rectifier, receiving circuit current sampling resistor and load resistance, wherein half-bridge PWM rectifier AC circuit is the series circuit of receiving circuit resonance coil and receiving circuit current sampling resistor composition, and this circuit has following relational expression:

$u_s\left(t\right)=L_2\frac{{\mathrm{di}}_s\left(t\right)}{\mathrm{dt}}+R_s{i}_s\left(t\right)+u_{\mathrm{ab}}\left(t\right)---\left(1\right)$

U in formula _st () is the induced voltage of receiving circuit resonance coil, L ₂for the self-induction of receiving circuit resonance coil, R _sbe the circuitous resistance comprising receiving circuit resonance coil and receiving circuit current sampling resistor, i _st () is for flowing through the electric current of receiving circuit resonance coil and receiving circuit current sampling resistor, u _abt () is half-bridge PWM rectifier AC port voltage.The operating frequency of the radiating circuit high-frequency ac power regulating half-bridge inverter to provide, makes radiating circuit be tending towards resonance condition, now u _st () is tending towards sine voltage, and u _abt () is periodic non-sinusoidal wave voltage.So formula (1) both sides are multiplied by i ₂the power relation formula of receiving circuit AC circuit can be obtained after (t):

I in formula _s1and I _snbe respectively i _sthe first-harmonic of (t) and the effective value of nth harmonic component, U _sfor u _sthe effective value of (t), U _abnfor u _abthe first-harmonic (n=1) of (t) and the effective value of nth harmonic component, for U _sand I _s1phase angle difference, θ _nfor U _abnand I _snphase angle difference, for the active power that receiving circuit resonance coil receives, for periodic non-sinusoidal wave current i _st () flows through the loss that circuitous resistance produces, for the switching loss of the electric energy and power switch pipe that flow to the load of half-bridge PWM rectifier DC side.

Pulse width modulation functions S (t) of half-bridge PWM rectifier is:

In formula, upper underarm ON time is determined by pulse-width modulation result of calculation.Because S (t) is periodic non-sinusoidal wave, therefore Fourier expansion can be utilized, and its fundamental frequency is the operating frequency of radiating circuit high-frequency ac power.

Ignore half-bridge PWM rectifier DC side ripple voltage, the expression formula of load current can be obtained:

$i_{\mathrm{dc}}\left(t\right)=\frac{1}{2}{i}_s\left(t\right)S\left(t\right)=I_{\mathrm{dc}}+\mathrm{\Δ}{i}_{\mathrm{dc}}---\left(4\right)$

$I_{\mathrm{dc}}=\underset{n=1}{\overset{\∞}{\mathrm{\Σ}}}\frac{I_{\mathrm{sn}}{S}_n}{4}\cos {\mathrm{\δ}}_n---\left(5\right)$

Load current I in formula _dcfor i _dcthe DC component of (t), Δ i _dcfor i _dcthe alternating current component of (t), S _nfor the first-harmonic of S (t) and the effective value of nth harmonic component, δ _nfor S _nand I _snphase angle difference.From formula (5), I _dcby i _st () produces jointly with the same frequency component of S (t), i _st all harmonic components of () and S (t) all take part in the output of direct current, namely half-bridge PWM rectifier has all carried out rectification to each harmonic.Due to R _susually very little, therefore the appearance of harmonic wave does not reduce the conversion efficiency of half-bridge PWM rectifier.In deriving, only require that pulse width modulation functions S (t) is for periodic non-sinusoidal wave above, therefore the PWM method of low carrier ratio can be adopted, namely low frequency pulse modulation technology realizes the periodic non-sinusoidal wave of S (t), the modulator approach of only several pulse in the work period adopting radiating circuit high-frequency ac power here, now can reduce the requirement to power switch pipe and drive circuit works frequency thereof greatly.

(2) Cleaning Principle of receiving circuit resonance coil induced voltage

Radiating circuit resonance coil and receiving circuit resonance coil respectively flow through current i _p(t) and i _s(t), the first induced voltage magnetic test coil and the second induced voltage magnetic test coil are operated in open-circuit condition, and the output voltage of two magnetic test coils is:

$u_3\left(t\right)=M_{13}\frac{{\mathrm{di}}_p}{\mathrm{dt}}+M_{23}\frac{{\mathrm{di}}_s}{\mathrm{dt}}---\left(6\right)$

$u_4\left(t\right)=M_{14}\frac{{\mathrm{di}}_p}{\mathrm{dt}}+M_{24}\frac{{\mathrm{di}}_s}{\mathrm{dt}}---\left(7\right)$

U in formula ₃(t) and u ₄t () is respectively the output voltage of the first induced voltage magnetic test coil and the second induced voltage magnetic test coil, M ₁₃and M ₂₃be respectively the first induced voltage magnetic test coil and the mutual inductance between radiating circuit resonance coil and receiving circuit resonance coil, M ₁₄and M ₂₄be respectively the second induced voltage magnetic test coil and the mutual inductance between radiating circuit resonance coil and receiving circuit resonance coil.Due to the series resonance of radiating circuit by regulating high frequency inverter operating frequency to reach radiating circuit resonant capacitance and radiating circuit resonance coil self-induction, therefore i _pt () is sinusoidal wave, so the fundametal compoment in formula (6) and formula (7) only can be considered, and because the mutual inductance between two coils is primarily of the determining positions between coil radius size, the number of turn and two coils, M can be made by design ₂₃=M ₂₄and M ₁₃≠ M ₁₄, formula (6) is deducted formula (7) and obtains:

${\stackrel{\·}{U}}_3-{\stackrel{\·}{U}}_4=\mathrm{j\ω}(M_{13}-M_{14}){\stackrel{\·}{I}}_p---\left(8\right)$

In formula be the difference of the fundamental voltage output of voltage component effective value of the first induced voltage magnetic test coil and the second induced voltage magnetic test coil, for radiating circuit resonance coil current effective value, ω is the operating angle frequency of radiating circuit high-frequency ac power.Because receiving circuit resonance coil induced voltage is therefore formula (8) can be utilized to obtain receiving circuit resonance coil induced voltage u _st the information of (), both only exist amplitude proportion relation.Formula (8) can be exported by the differential concatenation form of the first induced voltage magnetic test coil and the second induced voltage magnetic test coil and be extracted fundametal compoment realization by low pass filter.

(3) system resonance and device constant voltage export control principle

Exported by the constant voltage adopting the double-closed-loop control structure of current inner loop and outer voltage to realize system resonance and device.First structure flows through the target current of receiving circuit resonance coil

$i_s^{*}\left(t\right)=[K_p(U_{\mathrm{dc}}^{*}-U_{\mathrm{dc}})+K_i{\∫}_0^t(U_{\mathrm{dc}}^{*}-U_{\mathrm{dc}})\mathrm{dt}]u_s\left(t\right)---\left(9\right)$

U in formula _dcfor the VD of device, for device constant output voltage desired value, K _pand K _ifor ratio and the integral control coefficient of PI controller.From formula (9), the error of device VD is to target current size and symbol play regulatory role, and target current with the induced voltage u of receiving circuit resonance coil _st () phase place is consistent, therefore work as i _st () equals target current time receiving circuit realize resonance, can the constant voltage of assurance device export simultaneously.The desired value of half-bridge PWM rectifier AC port voltage, and be designed to for the reference waveform of PWM:

$u_{\mathrm{ab}}^{*}\left(t\right)=u_s\left(t\right)-L_2\frac{{\mathrm{di}}_s^{*}\left(t\right)}{\mathrm{dt}}-R_s{i}_s^{*}\left(t\right)-K[i_s^{*}\left(t\right)-i_s\left(t\right)]---\left(10\right)$

In formula, K is proportional control factor.Formula (10) is deducted formula (1), obtains:

$L_2\frac{d[i_s^{*}\left(t\right)-i_s\left(t\right)]}{\mathrm{dt}}+(R_s+K)[i_s^{*}\left(t\right)-i_s\left(t\right)]+[u_{\mathrm{ab}}^{*}\left(t\right)-u_{\mathrm{ab}}\left(t\right)]=0---\left(11\right)$

Due to u _st () is sinusoidal wave for first-harmonic, therefore calculated by formula (9) also be that first-harmonic is sinusoidal wave, and the receiving circuit of half-bridge PWM rectifier AC is only made up of receiving circuit resonance coil and current sampling resistor, is therefore a linear circuit, so in formula (11) the superposition of fundamental voltage source and harmonic voltage source can be regarded as, for these fundamental voltage sources and harmonic voltage source individually act on the superposition of the electric current of lower generation.Assuming that fundamental voltage component be zero, i.e. half-bridge PWM rectifier its AC voltage u after low frequency pulse-width modulation _ab(t) and fundamental voltage component equal, so fundamental current component be also zero, i.e. i _sthe fundamental current component of (t) with equal, that is with u _st () phase place is consistent, so achieve resonance.Now, obtained by formula (11) each harmonic voltage source acting in conjunction under relational expression be:

$L_2\underset{n=2}{\overset{\∞}{\mathrm{\Σ}}}\frac{{\mathrm{di}}_{\mathrm{sn}}\left(t\right)}{\mathrm{dt}}+R_s\underset{n=2}{\overset{\∞}{\mathrm{\Σ}}}{i}_{\mathrm{sn}}\left(t\right)+\underset{n=2}{\overset{\∞}{\mathrm{\Σ}}}{u}_{\mathrm{abn}}\left(t\right)=0---\left(12\right)$

Visible harmonic current is only at circuitous resistance R _supper lossy, and the R of little resistance _scan reduce the wastage.

The utility model is 220V based on the input voltage of the magnet coupled resonant type wireless power transfer of low frequency PWM rectifier, frequency is 50Hz, radiating circuit high frequency inverter frequency can reach 1MHz, the distance of radiating circuit resonance coil and receiving circuit resonance coil can reach 80cm, the VD of device can reach 19.5V, and the load resistance of device is minimum is 5 Ω.

As preferably, radiating circuit high frequency inverter He Ne laser scope is 50KHz to 1MHz.

As preferably, radiating circuit resonance coil and receiving circuit resonance coil adopt hollow annular concentrating coil or hollow disc coil, and described coil forms by the coiling of high quality factor litz wire.

As preferably, resonant capacitance adopts the high pressure ceramic disc capacitor of high stability.

As preferably, radiating circuit current sampling resistor and receiving circuit current sampling resistor all adopt resistance to be that 50m Ω, temperature drift are lower than the purely resistive precision resistance of 10ppm/ DEG C.

The benefit that the utility model brings:

(1) the magnet coupled resonant type wireless power transfer based on the low frequency PWM rectifier described in the utility model radiating circuit high-frequency ac power that utilizes half-bridge inverter to provide operating frequency adjustable, utilize half-bridge PWM rectifier on the one hand for load provides constant direct voltage simultaneously, realize on the other hand the resonance of receiving circuit, overcome common magnet coupled resonant type wireless power transfer and accept circuit tuning electric capacity and can not regulate brought tuning problem continuously.

(2) the magnet coupled resonant type wireless power transfer based on low frequency PWM rectifier described in the utility model utilizes two induced voltage magnetic test coils to obtain the information of the induced voltage of receiving circuit resonance coil, therefore this tuning system can follow the tracks of the change of radiating circuit high-frequency ac power operating frequency, and solving receiving circuit resonance coil is difficult to accurately calculate its induced voltage problem when there being electric current to export, thus to the change of the resistance and self-induction numerical value that receive circuit resonance coil, there is adaptivity.Meanwhile, owing to allowing radiating circuit high-frequency ac power operating frequency adjustable, therefore can realize the resonance of primary circuit easily, make whole device realize complex resonance.

(3) the magnet coupled resonant type wireless power transfer based on low frequency PWM rectifier described in the utility model adopts the low frequency pulse modulation technology of low carrier ratio to carry out PWM rectification, greatly reduce the requirement to device for power switching, drive circuit and operation frequency of microprocessor, also reduce the loss of device for power switching simultaneously, decrease the cost of heat abstractor.From another point of view, also provide space for device improves power work frequency, thus the transmittability of system can be improved further.

(4) the magnet coupled resonant type wireless power transfer based on low frequency PWM rectifier described in the utility model also can utilize full bridge PWM rectifier to realize same function, but utilize half-bridge PWM rectifier to realize resonance and the constant voltage output of receiving circuit, decrease the usage quantity of power switch pipe.

Accompanying drawing explanation

Fig. 1 is the magnet coupled resonant type wireless power transfer structure chart based on low frequency PWM rectifier;

Fig. 2 is the low frequency pulse-width modulation waveform of the low carrier ratio of a kind of PWM rectifier that the utility model adopts, and it gives radiating circuit high-frequency ac power work period corresponding waveform;

Fig. 3 is a kind of radiating circuit resonance coil, receiving circuit resonance coil, the first induced voltage magnetic test coil and the second induced voltage magnetic test coil placement location schematic diagram that the utility model adopts.

In figure, 1 is rectifier, 2 is first electric capacity of voltage regulation, 3 is second electric capacity of voltage regulation, 4 is first inverter power switches, 5 is second inverter power switches, 6 is radiating circuit resonant capacitances, 7 is radiating circuit resonance coils, 8 is radiating circuit current sampling resistors, 9 is receiving circuit resonance coils, 10 is receiving circuit current sampling resistors, 11 is first rectified power switches, 12 is second rectified power switches, 13 is the 3rd electric capacity of voltage regulation, 14 is the 4th electric capacity of voltage regulation, 15 is resonator, filter electric capacity, 16 is resonator, filter inductance, 17 is load resistances, 18 is transmitting terminal signal conditioning circuits, 19 is transmitting terminal analog to digital converters, 20 is transmitting terminal microprocessors, 21 is transmitting terminal high-frequency inversion drive circuits, 22 is first induced voltage magnetic test coils, 23 is second induced voltage magnetic test coils, 24 is receiving end signal modulate circuits, 25 is receiving terminal analog to digital converters, 26 is receiving terminal microprocessors, 27 is PWM rectifier drive circuits.

Embodiment

A kind of magnet coupled resonant type wireless power transfer based on low frequency PWM rectifier that the utility model proposes, embodiment is as Fig. 1, shown in Fig. 2 and Fig. 3, it comprises rectifier 1, first electric capacity of voltage regulation 2, second electric capacity of voltage regulation 3, first inverter power switch 4, second inverter power switch 5, radiating circuit resonant capacitance 6, radiating circuit resonance coil 7, radiating circuit current sampling resistor 8, receiving circuit resonance coil 9, receiving circuit current sampling resistor 10, first rectified power switch 11, second rectified power switch 12, 3rd electric capacity of voltage regulation 13, 4th electric capacity of voltage regulation 14, resonator, filter electric capacity 15, resonator, filter inductance 16, load resistance 17, transmitting terminal signal conditioning circuit 18, transmitting terminal analog to digital converter 19, transmitting terminal microprocessor 20, transmitting terminal high-frequency inversion drive circuit 21, first induced voltage magnetic test coil 22, second induced voltage magnetic test coil 23, receiving end signal modulate circuit 24, receiving terminal analog to digital converter 25, receiving terminal microprocessor 26 and PWM rectifier drive circuit 27, first electric capacity of voltage regulation 2, second electric capacity of voltage regulation 3, first inverter power switch 4 and the second inverter power switch 5 form half-bridge inverter, two lead-out terminals of two direct-flow input end sub-connection rectifiers 1 of half-bridge inverter, two lead-out terminals of half-bridge inverter connect one end of radiating circuit resonant capacitance 6 and one end of radiating circuit current sampling resistor 8 respectively, the other end of radiating circuit resonant capacitance 6 is connected with one end of radiating circuit resonance coil 7, the other end of radiating circuit current sampling resistor 8 is connected with the other end of radiating circuit resonance coil 7, the voltage signal at the voltage between two of half-bridge inverter lead-out terminals and radiating circuit current sampling resistor 8 two ends is carried out two input ports nursing one's health rear feeding transmitting terminal analog to digital converter 19 by transmitting terminal signal conditioning circuit 18, transmitting terminal microprocessor 20 accepts the digital signal from transmitting terminal analog to digital converter 19 and produces the square wave control signal of frequency-adjustable as calculated afterwards, this square wave control signal drives the power switch of half-bridge inverter by high-frequency inversion drive circuit 21, first rectified power switch 11, second rectified power switch 12,3rd electric capacity of voltage regulation 13 and the 4th electric capacity of voltage regulation 14 form half-bridge PWM rectifier, two input terminals of half-bridge PWM rectifier AC connect one end of receiving circuit resonance coil 9 and one end of receiving circuit current sampling resistor 10 respectively, the other end of receiving circuit resonance coil 9 is connected with the other end of receiving circuit current sampling resistor 10, two lead-out terminals of half-bridge PWM rectifier DC side connect one end of resonator, filter electric capacity 15 and one end of resonator, filter inductance 16 respectively, the other end of resonator, filter electric capacity 15 is connected with the other end of resonator, filter inductance 16, and two lead-out terminals of half-bridge PWM rectifier DC side connect two terminals of load resistance 17 respectively, radiating circuit resonance coil 7 and receiving circuit resonance coil 9 parallel coaxial are placed also at intervals, first induced voltage magnetic test coil 22, second induced voltage magnetic test coil 23 is coaxially fixed in same plane with receiving circuit resonance coil 9, first induced voltage magnetic test coil 22, the coil radius of the second induced voltage magnetic test coil 23 and receiving circuit resonance coil is different, the non-same polarity of the first induced voltage magnetic test coil 22 is connected with the non-same polarity of the second induced voltage magnetic test coil 23, the Same Name of Ends of the first induced voltage magnetic test coil 22 is connected with first input port of receiving end signal modulate circuit 24 with the Same Name of Ends of the second induced voltage magnetic test coil 23, the two ends of receiving circuit current sampling resistor 10 are connected with second input port of receiving end signal modulate circuit 24, the two ends of load resistance 17 are connected with the 3rd of receiving end signal modulate circuit 24 the input port, the output signal of receiving end signal modulate circuit 24 inputs receiving terminal microprocessor 26 through receiving terminal analog to digital converter 25, receiving terminal microprocessor 26 calculates rear generation low frequency pulse-width modulation waveform, and the power switch of half-bridge PWM rectifier is driven by PWM rectifier drive circuit 27, two input terminals of rectifier 1 are the power input port of device, two lead-out terminals of half-bridge PWM rectifier DC side are the DC voltage output end mouth of device.

The present embodiment specific design parameter is: the input voltage based on the magnet coupled resonant type wireless power transfer of low frequency PWM rectifier is 220V, frequency is 50Hz, the VD of rectifier 1 is 6V, the operating frequency of the radiating circuit high-frequency ac power that half-bridge inverter provides is 100KHz, the capacitance of radiating circuit resonant capacitance 6 is 49nF, the number of turn of radiating circuit resonance coil 7 is 20, radius is 4cm, inductance value is 52 μ H, the number of turn of receiving circuit resonance coil 9 is 4, radius is 4cm, inductance value is 2.5 μ H, the distance of radiating circuit resonance coil 7 and receiving circuit resonance coil 9 is 5cm, the number of turn of the first induced voltage magnetic test coil 22 is 6, radius is 3cm, inductance value is 3.7217 μ H, the number of turn of the second induced voltage magnetic test coil 23 is 4, radius is 5.03cm, inductance value is 3.3706 μ H, the VD of half-bridge PWM rectifier is 15V, the resistance of load 17 is 25 Ω, first electric capacity of voltage regulation 2, second electric capacity of voltage regulation 3, the value of the 3rd electric capacity of voltage regulation 13 and the 4th electric capacity of voltage regulation 14 is 47 μ F, resonator, filter electric capacity 15 capacitance is 122nF, resonator, filter inductance 16 inductance value is 5.2 μ H, first inverter power switch 4, second inverter power switch 5, first rectified power switch 11 and the second rectified power switch 12 all adopt model to be the MOSFET of IRF840, high-frequency inversion drive circuit 21 and receiving circuit drive circuit 27 all adopt driving chip IR2110, transmitting terminal microprocessor 26 and receiving terminal microprocessor 26 all adopt 32 STM32F103C8 microcontrollers.

The content be not described in detail in the utility model specification belongs to the known technology of those skilled in the art.

It is understood that above-described embodiment is just to explanation of the present utility model, instead of to restriction of the present utility model, any utility model do not exceeded in the utility model spirit is created, and all falls within protection range of the present utility model.

Claims (4)

1. based on the magnet coupled resonant type wireless power transfer of low frequency PWM rectifier, comprise rectifier (1), first electric capacity of voltage regulation (2), second electric capacity of voltage regulation (3), first inverter power switch (4), second inverter power switch (5), radiating circuit resonant capacitance (6), radiating circuit resonance coil (7), radiating circuit current sampling resistor (8), receiving circuit resonance coil (9), receiving circuit current sampling resistor (10), first rectified power switch (11), second rectified power switch (12), 3rd electric capacity of voltage regulation (13), 4th electric capacity of voltage regulation (14), resonator, filter electric capacity (15), resonator, filter inductance (16), load resistance (17), transmitting terminal signal conditioning circuit (18), transmitting terminal analog to digital converter (19), transmitting terminal microprocessor (20), transmitting terminal high-frequency inversion drive circuit (21), first induced voltage magnetic test coil (22), second induced voltage magnetic test coil (23), receiving end signal modulate circuit (24), receiving terminal analog to digital converter (25), receiving terminal microprocessor (26) and PWM rectifier drive circuit (27), it is characterized in that the first electric capacity of voltage regulation (2), second electric capacity of voltage regulation (3), first inverter power switch (4) and the second inverter power switch (5) form half-bridge inverter, two lead-out terminals of two direct-flow input end sub-connection rectifiers (1) of half-bridge inverter, two lead-out terminals of half-bridge inverter connect one end of radiating circuit resonant capacitance (6) and one end of radiating circuit current sampling resistor (8) respectively, the other end of radiating circuit resonant capacitance (6) is connected with one end of radiating circuit resonance coil (7), the other end of radiating circuit current sampling resistor (8) is connected with the other end of radiating circuit resonance coil (7), the voltage signal at the voltage between two of half-bridge inverter lead-out terminals and radiating circuit current sampling resistor (8) two ends is carried out two input ports nursing one's health rear feeding transmitting terminal analog to digital converter (19) by transmitting terminal signal conditioning circuit (18), transmitting terminal microprocessor (20) accepts the digital signal from transmitting terminal analog to digital converter (19) and produces the square wave control signal of frequency-adjustable as calculated afterwards, this square wave control signal drives the power switch of half-bridge inverter by high-frequency inversion drive circuit (21), first rectified power switch (11), second rectified power switch (12), 3rd electric capacity of voltage regulation (13) and the 4th electric capacity of voltage regulation (14) form half-bridge PWM rectifier, two input terminals of half-bridge PWM rectifier AC connect one end of receiving circuit resonance coil (9) and one end of receiving circuit current sampling resistor (10) respectively, the other end of receiving circuit resonance coil (9) is connected with the other end of receiving circuit current sampling resistor (10), two lead-out terminals of half-bridge PWM rectifier DC side connect one end of resonator, filter electric capacity (15) and one end of resonator, filter inductance (16) respectively, the other end of resonator, filter electric capacity (15) is connected with the other end of resonator, filter inductance (16), and two lead-out terminals of half-bridge PWM rectifier DC side connect two terminals of load resistance (17) respectively, radiating circuit resonance coil (7) and receiving circuit resonance coil (9) parallel coaxial are placed also at intervals, first induced voltage magnetic test coil (22), second induced voltage magnetic test coil (23) and receiving circuit resonance coil (9) are coaxially fixed in same plane, first induced voltage magnetic test coil (22), the coil radius of the second induced voltage magnetic test coil (23) and receiving circuit resonance coil is different, the non-same polarity of the first induced voltage magnetic test coil (22) is connected with the non-same polarity of the second induced voltage magnetic test coil (23), the Same Name of Ends of the first induced voltage magnetic test coil (22) is connected with first input port of receiving end signal modulate circuit (24) with the Same Name of Ends of the second induced voltage magnetic test coil (23), the two ends of receiving circuit current sampling resistor (10) are connected with second input port of receiving end signal modulate circuit (24), the two ends of load resistance (17) are connected with the 3rd input port of receiving end signal modulate circuit (24), the output signal of receiving end signal modulate circuit (24) is through receiving terminal analog to digital converter (25) input receiving terminal microprocessor (26), low frequency pulse-width modulation waveform is produced after receiving terminal microprocessor (26) calculates, and the power switch of half-bridge PWM rectifier is driven by PWM rectifier drive circuit (27), two input terminals of rectifier (1) are the power input port of device, two lead-out terminals of half-bridge PWM rectifier DC side are the DC voltage output end mouth of device.

2., as claimed in claim 1 based on the magnet coupled resonant type wireless power transfer of low frequency PWM rectifier, it is characterized in that radiating circuit high frequency inverter He Ne laser scope is 50KHz to 1MHz.

3. as claimed in claim 1 based on the magnet coupled resonant type wireless power transfer of low frequency PWM rectifier, it is characterized in that described radiating circuit resonance coil (7) and receiving circuit resonance coil (9) adopt hollow annular concentrating coil or hollow disc coil, described coil forms by the coiling of high quality factor litz wire.

4., as the magnet coupled resonant type wireless power transfer based on low frequency PWM rectifier of claim 1-3 as described in any one, it is characterized in that described radiating circuit current sampling resistor (8) and receiving circuit current sampling resistor (10) all adopt resistance to be that 50m Ω, temperature drift are lower than the purely resistive precision resistance of 10ppm/ DEG C.