CN203800839U - Bootstrap driving unipolar SPWM non-isolated grid-connected inverter circuit - Google Patents
Bootstrap driving unipolar SPWM non-isolated grid-connected inverter circuit Download PDFInfo
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- CN203800839U CN203800839U CN201320835749.9U CN201320835749U CN203800839U CN 203800839 U CN203800839 U CN 203800839U CN 201320835749 U CN201320835749 U CN 201320835749U CN 203800839 U CN203800839 U CN 203800839U
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Abstract
The utility model provides a bootstrap driving unipolar SPWM non-isolated grid-connected inverter circuit, and the inverter circuit comprises a power inverter circuit, wherein the power inverter circuit comprises six controllable power switches, two power diodes, and two power inductors. The inverter circuit also comprises a bootstrap driving circuit which comprises four diodes, four capacitors, and one driving power supply. The inverter circuit provided by the utility model is novel, is additionally provided with the two controllable power switches and the two power diodes on the basis of a classic H-bridge inverter circuit, and employs a modulation mode of unipolar-type SPWM, thereby enabling the conversion efficiency to be higher and generating no leakage current. Meanwhile, the circuit characteristics and modulation mode of the inverter circuit enable the isolation drive power supplies of all floating controllable power switches to be generated in a bootstrap mode. The inverter circuit is simple, does not need special control, and further reduces the cost.
Description
Technical field
The utility model relates to new forms of energy photovoltaic field, and particularly a kind of bootstrapping drives Unipolar SPWM to modulate non-isolated grid-connected inverter circuit.
Background technology
Combining inverter is that the direct current of photovoltaic battery array (PV) output is converted to the device that alternating current outputs to electrical network.According to PV side and grid side, whether have electrical isolation, combining inverter generally can be divided into the combining inverter that has transformer isolation, is called for short isolation type grid-connected inverter; With the combining inverter of transless isolation, be called for short non-isolation type combining inverter.
Isolation type grid-connected inverter generally has low frequency isolation and two kinds of modes of high-frequency isolation.Low frequency isolation mode is taked to use Industrial Frequency Transformer between inverter outlet side and grid side, thereby causes whole inverter machine volume large, heaviness, and cost is high; The DC voltage conversion that high-frequency isolation mode generally provides photovoltaic array by High Frequency Link inversion transformation technique is that the isolated DC voltage that quality is higher carries out inversion again, now isolating transformer is operated in high frequency mode, the advantage little, lightweight, cost is low that therefore relative low frequency isolation type has volume.And non-isolation type inverter is not because inside is used isolating transformer completely, compare isolation type grid-connected inverter, there is volume less, weight is lighter, and efficiency is higher, the advantage that cost is lower, thereby obtain applying more widely.
Although non-isolation type combining inverter has above-mentioned more advantages, but non-isolation type combining inverter due between photovoltaic array and electrical network without electrical isolation, make the distributed capacitance existing between photovoltaic array and the earth, will under inverter HF switch mode of operation, produce leakage current, thereby increased potential safety hazard, so non-isolation type inverter must be selected the corresponding control mode of suitable topological sum.
Existing a large amount of document analysis and contrasted the various topologys that are applied at present non-isolation type combining inverter, they are produced under different PWM modulation systems to the principle of leakage current, size, and detailed analysis and comparison has all been made in conversion efficiency aspect, can obtain conclusion: the conventional H bridge inverter being formed by four power switchs, if be operated under bipolar SPWM modulating mode, can not produce leakage current, but there is relatively low conversion efficiency, if and be operated under Unipolar SPWM modulating mode, there is relatively high conversion efficiency, but can cause larger leakage current.
Utility model content
The technical problems to be solved in the utility model is to provide and a kind ofly can produce a kind of bootstrapping that leakage current, conversion efficiency are high and drive Unipolar SPWM to modulate non-isolated grid-connected inverter circuit.
In order to solve above technical problem, the utility model provides a kind of bootstrapping to drive Unipolar SPWM to modulate non-isolated grid-connected inverter circuit, comprise power inversion circuit, wherein, described power inversion circuit comprises six controlled power switches, two power diodes and two power inductances, described inverter circuit also comprises Bootstrapping drive circuit, described Bootstrapping drive circuit comprises four diodes, four electric capacity and a driving power, described Bootstrapping drive circuit provides driving voltage for each controlled power switch in described power inversion circuit, the input of described power inversion circuit is electrically connected to the output busbar voltage of front stage circuits, the output of described power inversion circuit is electrically connected to electrical network.
Preferably, described six controlled power switches are respectively controlled power switch Q1, controlled power switch Q2, controlled power switch Q3, controlled power switch Q4, controlled power switch Q5 and controlled power switch Q6, described two power diodes are respectively power diode D7 and power diode D8, and two described power inductances are power inductance L1 and power inductance L2;
After being electrically connected to the anode of described controlled power switch Q2, the anode of described controlled power switch Q1 is electrically connected to the anode of described busbar voltage, the cathodic electricity of described controlled power switch Q1 connects one end of described power inductance L1, the other end of described power inductance L1 is electrically connected to the L end of electrical network, the cathodic electricity of described controlled power switch Q2 connects one end of described power inductance L2, and the other end of described power inductance L2 is electrically connected to the N end of electrical network;
The anode of described controlled power switch Q3 is electrically connected to the negative electrode of described controlled power switch Q1, the cathodic electricity of described controlled power switch Q3 connects the anode of described controlled power switch Q5, and the cathodic electricity of described controlled power switch Q5 connects the negative terminal of described busbar voltage; The anode of described controlled power switch Q4 is electrically connected to the negative electrode of described controlled power switch Q2, and the cathodic electricity of described controlled power switch Q4 connects the anode of described controlled power switch Q6, the negative terminal of the cathodic electricity connection bus voltage of described controlled power switch Q6;
The anode of described power diode D8 is electrically connected to the negative electrode of described controlled power switch Q3, the cathodic electricity of described power diode D8 connects the negative electrode of described controlled power switch Q2, the anode of described power diode D7 is electrically connected to the negative electrode of described controlled power switch Q4, and the cathodic electricity of described power diode D7 connects the negative electrode of described controlled power switch Q1.
Preferably, described four diodes are respectively diode D1, diode D2, diode D3 and diode D4, and described six electric capacity are respectively capacitor C 1, capacitor C 2, capacitor C 3, capacitor C 4, capacitor C 5 and capacitor C 6, and described driving power is Vdri;
One end of described capacitor C 1 is electrically connected to the negative electrode of described controlled power switch Q1, the other end of described capacitor C 1 is electrically connected to the negative electrode of described diode D1, one end of described capacitor C 2 is electrically connected to the negative electrode of described controlled power switch Q2, the other end of described capacitor C 2 is electrically connected to the negative electrode of described diode D2, one end of described capacitor C 3 is electrically connected to the negative electrode of described controlled power switch Q3, the other end of described capacitor C 3 is electrically connected to the negative electrode of described diode D3, one end of described capacitor C 4 is electrically connected to the negative electrode of described controlled power switch Q4, the other end of described capacitor C 4 is electrically connected to the negative electrode of described diode D4, one end of described capacitor C 5 is electrically connected to the negative electrode of described controlled power switch Q5, the other end of described capacitor C 5 is electrically connected to the anode of described driving power Vdri, one end of described capacitor C 6 is electrically connected to the negative electrode of described controlled power switch Q6, the other end of described capacitor C 6 is electrically connected to the anode of described driving power Vdri,
The anode of described diode D1 is electrically connected to the negative electrode of described diode D4, the anode of described diode D2 is electrically connected to the negative electrode of described diode D3, the common anode that is electrically connected to described driving power Vdri of anode of the anode of described diode D3 and described diode D4, the negative terminal of described driving power Vdri is electrically connected to the negative terminal of described busbar voltage.
Preferably, described controlled power switch is IGBT, the C utmost point that the anode of described controlled power switch is described IGBT, the E utmost point that the negative electrode of described controlled power switch is described IGBT.
Preferably, described controlled power switch is MOSEFT pipe, and the anode of described controlled power switch is the D utmost point of described MOSEFT pipe, and the negative electrode of described controlled power switch is the S utmost point of described MOSEFT pipe.
Preferably, described capacitor C 1, capacitor C 2, capacitor C 3 and capacitor C 4 are equivalent capacitance.
Preferably, described power inductance is sendust core coiling, and described power inductance L1 and described power inductance L2 are respectively independently power inductance; Or described power inductance is sendust core coiling, described power inductance L1 and described power inductance L2 are the power inductance of coupling.
Preferably, described controlled power switch Q3 and described controlled power switch Q4 are operated in low frequency on off state, and described controlled power switch Q1, described controlled power switch Q6, described controlled power switch Q2 and described controlled power switch Q5 are operated in HF switch state.
Preferably, the state of described controlled power switch Q3 and described controlled power switch Q4 switches according to the polarity of line voltage.
Preferably, the state of described controlled power switch Q1, described controlled power switch Q6, described controlled power switch Q2 and described controlled power switch Q5 is controlled according to Unipolar SPWM modulation system.
The utility model proposes a kind of bootstrapping drives Unipolar SPWM to modulate non-isolated grid-connected inverter circuit, this circuit is on classical H bridge inverter circuit base, by increasing by two controlled power switches and two power diodes, and adopt class Unipolar SPWM modulation system, make its existing higher conversion efficiency, can not produce leakage current again; Meanwhile, the electric circuit characteristic of himself and modulation system, can produce by the mode of bootstrapping the isolation drive power supply of its each floating ground controlled power switch, and circuit is simple, does not need special control, has further reduced the cost of circuit.
Accompanying drawing explanation
Below in conjunction with the drawings and specific embodiments, the utility model is described in further detail:
Fig. 1 is that a kind of bootstrapping of the utility model drives Unipolar SPWM to modulate the circuit theory diagrams of non-isolated grid-connected inverter circuit embodiment;
Fig. 2 is that a kind of bootstrapping of the utility model drives Unipolar SPWM to modulate the modulation system schematic diagram of non-isolated grid-connected inverter circuit embodiment;
When being Q1, Q4, Q6 conducting simultaneously, Fig. 3 (a) forms with L1, L2 the operation mode figure that is connected the forward copped wave passage between Vdc and Grid, Fig. 3 (b) is the operation mode figure that Q4, D7, L1, L2 and Grid form forward afterflow passage, Fig. 3 (c) is that Q2, Q3, Q5 form with L1, L2 the operation mode figure that is connected the negative sense copped wave passage between Vdc and Grid, and Fig. 3 (d) is the operation mode figure that Q3, D8, L1, L2 and Grid form negative sense afterflow passage;
Fig. 4 is a kind of 3KW theory analysis oscillogram of booting and driving Unipolar SPWM to modulate non-isolated grid-connected inverter circuit embodiment of the utility model
Fig. 5 is that a kind of bootstrapping of the utility model drives Unipolar SPWM to modulate the actual test waveform figure of 3KW of non-isolated grid-connected inverter circuit embodiment.
Embodiment
For above-mentioned purpose of the present utility model, feature and advantage can be become apparent more, below in conjunction with accompanying drawing, embodiment of the present utility model is described in detail, it will be more clear making above-mentioned and other object of the present utility model, Characteristics and advantages.In whole accompanying drawings, identical Reference numeral is indicated identical part.Deliberately do not draw in proportion accompanying drawing, focus on illustrating purport of the present utility model.
Embodiment:
The utility model provides a kind of bootstrapping to drive Unipolar SPWM to modulate non-isolated grid-connected inverter circuit, comprise power inversion circuit, wherein, described power inversion circuit comprises six controlled power switches, two power diodes and two power inductances, described inverter circuit also comprises Bootstrapping drive circuit, described Bootstrapping drive circuit comprises four diodes, four electric capacity and a driving power, described Bootstrapping drive circuit provides driving voltage for each controlled power switch in described power inversion circuit, the input of described power inversion circuit is electrically connected to the output busbar voltage of front stage circuits, the output of described power inversion circuit is electrically connected to electrical network.Described power switch is for conducting or cut off current path, and described power inductance is for the filtering of described inverter circuit output current.
As shown in Figure 1, described six controlled power switches are respectively controlled power switch Q1, controlled power switch Q2, controlled power switch Q3, controlled power switch Q4, controlled power switch Q5 and controlled power switch Q6, described two power diodes are respectively power diode D7 and power diode D8, and two described power inductances are power inductance L1 and power inductance L2.
After being electrically connected to the anode of described controlled power switch Q2, the anode of described controlled power switch Q1 is electrically connected to the anode of described busbar voltage, the cathodic electricity of described controlled power switch Q1 connects one end of described power inductance L1, the other end of described power inductance L1 is electrically connected to the L end of electrical network, the cathodic electricity of described controlled power switch Q2 connects one end of described power inductance L2, and the other end of described power inductance L2 is electrically connected to the N end of electrical network.
The anode of described controlled power switch Q3 is electrically connected to the negative electrode of described controlled power switch Q1, the cathodic electricity of described controlled power switch Q3 connects the anode of described controlled power switch Q5, and the cathodic electricity of described controlled power switch Q5 connects the negative terminal of described busbar voltage; The anode of described controlled power switch Q4 is electrically connected to the negative electrode of described controlled power switch Q2, and the cathodic electricity of described controlled power switch Q4 connects the anode of described controlled power switch Q6, the negative terminal of the cathodic electricity connection bus voltage of described controlled power switch Q6.
The anode of described power diode D8 is electrically connected to the negative electrode of described controlled power switch Q3, the cathodic electricity of described power diode D8 connects the negative electrode of described controlled power switch Q2, the anode of described power diode D7 is electrically connected to the negative electrode of described controlled power switch Q4, and the cathodic electricity of described power diode D7 connects the negative electrode of described controlled power switch Q1.
Described four diodes are respectively diode D1, diode D2, diode D3 and diode D4, and described six electric capacity are respectively capacitor C 1, capacitor C 2, capacitor C 3, capacitor C 4, capacitor C 5 and capacitor C 6, and described driving power is Vdri.
One end of described capacitor C 1 is electrically connected to the negative electrode of described controlled power switch Q1, the other end of described capacitor C 1 is electrically connected to the negative electrode of described diode D1, one end of described capacitor C 2 is electrically connected to the negative electrode of described controlled power switch Q2, the other end of described capacitor C 2 is electrically connected to the negative electrode of described diode D2, one end of described capacitor C 3 is electrically connected to the negative electrode of described controlled power switch Q3, the other end of described capacitor C 3 is electrically connected to the negative electrode of described diode D3, one end of described capacitor C 4 is electrically connected to the negative electrode of described controlled power switch Q4, the other end of described capacitor C 4 is electrically connected to the negative electrode of described diode D4, one end of described capacitor C 5 is electrically connected to the negative electrode of described controlled power switch Q5, the other end of described capacitor C 5 is electrically connected to the anode of described driving power Vdri, one end of described capacitor C 6 is electrically connected to the negative electrode of described controlled power switch Q6, the other end of described capacitor C 6 is electrically connected to the anode of described driving power Vdri.
The anode of described diode D1 is electrically connected to the negative electrode of described diode D4, the anode of described diode D2 is electrically connected to the negative electrode of described diode D3, the common anode that is electrically connected to described driving power Vdri of anode of the anode of described diode D3 and described diode D4, the negative terminal of described driving power Vdri is electrically connected to the negative terminal of described busbar voltage.
As shown in Figure 2, in this enforcement, described controlled power switch Q3 and described controlled power switch Q4 are operated in low frequency on off state, and described controlled power switch Q1, described controlled power switch Q6, described controlled power switch Q2 and described controlled power switch Q5 are operated in HF switch state.The state of described controlled power switch Q3 and described controlled power switch Q4 switches according to the polarity of line voltage.The state of described controlled power switch Q1, described controlled power switch Q6, described controlled power switch Q2 and described controlled power switch Q5 is controlled according to Unipolar SPWM modulation system.
The operation principle of the present embodiment:
Power inverting part: when the positive half cycle of line voltage, in a switch periods Ts, the ton time period (ratio of ton and Ts is defined as duty ratio D) of controlled power switch Q1, Q4, Q6 conducting simultaneously, they and power inductance L1, L2 form the forward copped wave passage between connection bus voltage Vdc and electrical network Grid, electric current flows to electrical network along Vdc+ → Q1 → L1 → Grid → L2 → Q4 → Q6 → Vdc-path from bus, output AC power, its operation mode is as shown in Fig. 3 (a), and wherein heavy line represents power current path; Controlled power switch turn-offs at Q1, Q6, the toff stage (toff=Ts-Ton) of only having Q4 conducting, Q4, D7, L1, L2 and Grid form forward afterflow passage, electric current carries out afterflow along L1 → Grid → L2 → Q4 → D7 path, guarantee the continuous of the interior stored energy of L1 and L2, its operation mode is as shown in Fig. 3 (b).
When line voltage negative half period, in a switch periods Ts, controlled power switch Q2, Q3, Q5 conducting simultaneously ton are in the time, they and power inductance L1, L2 form the negative sense copped wave passage between connection bus voltage Vdc and electrical network Grid, electric current flows to electrical network along Vdc+ → Q2 → L2 → Grid → L1 → Q3 → Q5 → Vdc-path from bus, output AC power, its operation mode is as shown in Fig. 3 (c); When Q2, Q5 turn-off, in the toff stage of only having Q3 conducting, Q3, D8, L1, L2 and Grid form negative sense afterflow passage, and electric current carries out afterflow along L2 → Grid → L1 → Q3 → D8 path, guarantee the continuous of the interior stored energy of L1 and L2, its operation mode is as shown in Fig. 3 (d).
Because the conducting of each power switch is to modulate according to Unipolar SPWM mode with turn-offing sequential, theory analysis is known, the first-harmonic of its output current is the sinusoidal current with frequency homophase with line voltage, through power inductance L1, L2 to switch time ripple filtering after, form the grid-connected current that flows into electrical network Grid.
Bootstrapping drive part: due to controlled power switch Q5, with busbar voltage Vdc altogether, so Q6 driving power Vdri can directly offer controlled power switch Q5, Q6 as driving power.At the positive half cycle of line voltage, when controlled power switch Q1, Q6 conducting simultaneously, Q4, Vdri are except directly providing driving power to Q6, also by Vdri+ → D4 → C4 → Q6 → Vaux-loop, capacitor C 4 is charged and obtained the driving voltage V4 of controlled power switch Q4, according to the drive current of the ON time ton of controlled power switch Q6 and controlled power switch Q4, choose suitable capacitor C 4 values, can guarantee that V4 is charged completely and is stabilized in the magnitude of voltage Vdri identical with driving power; When controlled power switch Q1, Q6 turn-off, only has controlled power switch Q4 still during conducting, capacitor C 4, except providing driving power to controlled power switch Q4, also can charge to Vdri to capacitor C 1 by the loop of C4+ → D1 → C1 → L1 → Grid → L2 → Q4 → C4-; When next switch periods Ts starts, Q1, Q6 are again during conducting, and C1 provides driving power to Q1.At line voltage negative half period, when controlled power switch Q2, Q3, Q5 conducting simultaneously, driving power Vdri is except providing driving power directly to controlled power switch Q5, also can to capacitor C 3, charge to driving power Vdri by Vdri+ → D3 → C3 → Q5 → Vaux-, obtain the driving voltage V3 of controlled power switch Q3; When controlled power switch Q2, Q5 turn-off, while only having controlled power switch Q3 conducting, capacitor C 3 is except providing driving power directly to controlled power switch Q3, and also the loop by C3+ → D2 → C2 → L2 → L1 → Q3 → C3-charges to driving power Vdri to capacitor C 2; When next switch periods Ts starts, controlled power switch Q2, Q5 are again during conducting, and capacitor C 2 provides driving power to controlled power switch Q2.
With 3KW combining inverter, prove the feasibility of this circuit, the parameter of this inverter is as follows:
Complete machine rated power: 3KW;
Busbar voltage Vdc:400V;
Line voltage Vac:220V/50Hz;
Filter inductance L1, L2:1mH
High-frequency tube switching frequency: 20KHz
Driving power Vdri:15V;
Bootstrapping drives electric capacity: C1=C2=C3=C4=4.7uF
According to above-mentioned parameter setting, select the IGBT of 600V/47A as controlled power switch, select the Ultrafast recovery diode of 600V/20A as fly-wheel diode, select to form whole loop of power circuit by the output inductor of sendust core coiling; Select the ceramic condenser of 50V/4.7uF as bootstrapping, to drive the charging capacitor C1～C4 in loop, select the Ultrafast recovery diode of 600V/1A as bootstrapping charging two utmost point D1～D4.Dsp chip TMS320F2808 by TI builds digital control circuit as core control CPU, to the grid-connected control of main power circuit type Unipolar SPWM.
Known by theory analysis, at the positive half cycle of line voltage, in the ton stage, brachium pontis mid point output common mode voltage is 0.5* (Vdc+0)=0.5Vdc; In the toff stage, brachium pontis mid point output common mode voltage is 0.5* (0.5Vdc+0.5Vdc)=0.5Vdc; In whole switch periods Ts, brachium pontis mid point output common mode voltage constant is 0.5Vdc, so its common mode current causing in parasitic common mode capacitance is 0; Known by same analysis, at line voltage negative half period, in whole switch periods Ts, brachium pontis mid point output common mode voltage constant is 0.5Vdc, and the common mode current causing in parasitic common mode capacitance is 0.So this circuit, under Unipolar SPWM modulating mode, can not bring leakage problem.Fig. 4 (b) is the simulation waveform of net side leakage electric current, and wherein equivalent parasitic capacitances is set to 100nF.From simulation result, only when grid-connected current zero crossing due to low-frequency tube Q3, switch the spike leakage current that can bring tens milliamperes that arranges of Dead Time, there is not leakage current in Q4 rest interval, thereby the mean value of leakage current is very little in whole power frequency period, be less than 10mA, far below the permissible value of grid-connected standard regulation.
Actual tests grid-connected current waveform and leakage current waveform are respectively as Fig. 5, and under the test condition of grid-connected standard regulation, its AC leakage current actual measurement is for 6.8mA, far below 30mA permissible value.Test waveform has been proved the volume feasibility of scheme.
Certainly, described controlled power switch is IGBT, and described controlled power switch also can be MOSEFT pipe.
The utility model proposes a kind of bootstrapping drives Unipolar SPWM to modulate non-isolated grid-connected inverter circuit, this circuit is on classical H bridge inverter circuit base, by increasing by two controlled power switches and two power diodes, and adopt class Unipolar SPWM modulation system, make its existing higher conversion efficiency, can not produce leakage current again; Meanwhile, the electric circuit characteristic of himself and modulation system, can produce by the mode of bootstrapping the isolation drive power supply of its each floating ground controlled power switch, and circuit is simple, does not need special control, has further reduced the cost of circuit.
Introducing due to low frequency power pipe and two additional diode, make the inductive current afterflow stage, electrical network and busbar voltage depart from completely, thereby kept the constant of brachium pontis mid point output voltage, avoid the leakage current bringing by parasitic capacitance because of the switch of inverter leg mid point output voltage time dither, be suitable for non-isolated grid-connected inverter applications.This circuit has had the advantage of H bridge inverter high conversion efficiency and the advantage of bipolar SPWM modulation H bridge inverter low-leakage current problem of Unipolar SPWM modulation concurrently simultaneously.
Simultaneously, the Bootstrapping drive circuit of introducing in conjunction with this circuit self structure feature and control mode, without multichannel isolation drive power supply and special control in the situation that, can obtain the isolation drive voltage of each floating ground power tube, thereby reduce the job costs of circuit.
In above description, a lot of details have been set forth so that fully understand the utility model.But above description is only preferred embodiment of the present utility model, the utility model can be implemented to be much different from alternate manner described here, so the utility model is not subject to the restriction of disclosed concrete enforcement above.Any skilled personnel are not departing from technical solutions of the utility model scope situation simultaneously, all can utilize method and the technology contents of above-mentioned announcement to make many possible changes and modification to technical solutions of the utility model, or be revised as the equivalent embodiment of equivalent variations.Every content that does not depart from technical solutions of the utility model,, all still belongs in the scope of technical solutions of the utility model protection any simple modification made for any of the above embodiments, equivalent variations and modification according to technical spirit of the present utility model.
Claims (10)
1. a bootstrapping drives Unipolar SPWM to modulate non-isolated grid-connected inverter circuit, comprise power inversion circuit, it is characterized in that, described power inversion circuit comprises six controlled power switches, two power diodes and two power inductances, described inverter circuit also comprises Bootstrapping drive circuit, described Bootstrapping drive circuit comprises four diodes, four electric capacity and a driving power, described Bootstrapping drive circuit provides driving voltage for each controlled power switch in described power inversion circuit, the input of described power inversion circuit is electrically connected to the output busbar voltage of front stage circuits, the output of described power inversion circuit is electrically connected to electrical network.
2. a kind of bootstrapping according to claim 1 drives Unipolar SPWM to modulate non-isolated grid-connected inverter circuit, it is characterized in that, described six controlled power switches are respectively controlled power switch Q1, controlled power switch Q2, controlled power switch Q3, controlled power switch Q4, controlled power switch Q5 and controlled power switch Q6, described two power diodes are respectively power diode D7 and power diode D8, and two described power inductances are power inductance L1 and power inductance L2;
After being electrically connected to the anode of described controlled power switch Q2, the anode of described controlled power switch Q1 is electrically connected to the anode of described busbar voltage, the cathodic electricity of described controlled power switch Q1 connects one end of described power inductance L1, the other end of described power inductance L1 is electrically connected to the L end of electrical network, the cathodic electricity of described controlled power switch Q2 connects one end of described power inductance L2, and the other end of described power inductance L2 is electrically connected to the N end of electrical network;
The anode of described controlled power switch Q3 is electrically connected to the negative electrode of described controlled power switch Q1, the cathodic electricity of described controlled power switch Q3 connects the anode of described controlled power switch Q5, and the cathodic electricity of described controlled power switch Q5 connects the negative terminal of described busbar voltage; The anode of described controlled power switch Q4 is electrically connected to the negative electrode of described controlled power switch Q2, and the cathodic electricity of described controlled power switch Q4 connects the anode of described controlled power switch Q6, the negative terminal of the cathodic electricity connection bus voltage of described controlled power switch Q6;
The anode of described power diode D8 is electrically connected to the negative electrode of described controlled power switch Q3, the cathodic electricity of described power diode D8 connects the negative electrode of described controlled power switch Q2, the anode of described power diode D7 is electrically connected to the negative electrode of described controlled power switch Q4, and the cathodic electricity of described power diode D7 connects the negative electrode of described controlled power switch Q1.
3. a kind of bootstrapping according to claim 2 drives Unipolar SPWM to modulate non-isolated grid-connected inverter circuit, it is characterized in that, described four diodes are respectively diode D1, diode D2, diode D3 and diode D4, described six electric capacity are respectively capacitor C 1, capacitor C 2, capacitor C 3, capacitor C 4, capacitor C 5 and capacitor C 6, and described driving power is Vdri;
One end of described capacitor C 1 is electrically connected to the negative electrode of described controlled power switch Q1, the other end of described capacitor C 1 is electrically connected to the negative electrode of described diode D1, one end of described capacitor C 2 is electrically connected to the negative electrode of described controlled power switch Q2, the other end of described capacitor C 2 is electrically connected to the negative electrode of described diode D2, one end of described capacitor C 3 is electrically connected to the negative electrode of described controlled power switch Q3, the other end of described capacitor C 3 is electrically connected to the negative electrode of described diode D3, one end of described capacitor C 4 is electrically connected to the negative electrode of described controlled power switch Q4, the other end of described capacitor C 4 is electrically connected to the negative electrode of described diode D4, one end of described capacitor C 5 is electrically connected to the negative electrode of described controlled power switch Q5, the other end of described capacitor C 5 is electrically connected to the anode of described driving power Vdri, one end of described capacitor C 6 is electrically connected to the negative electrode of described controlled power switch Q6, the other end of described capacitor C 6 is electrically connected to the anode of described driving power Vdri,
The anode of described diode D1 is electrically connected to the negative electrode of described diode D4, the anode of described diode D2 is electrically connected to the negative electrode of described diode D3, the common anode that is electrically connected to described driving power Vdri of anode of the anode of described diode D3 and described diode D4, the negative terminal of described driving power Vdri is electrically connected to the negative terminal of described busbar voltage.
4. a kind of bootstrapping according to claim 3 drives Unipolar SPWM to modulate non-isolated grid-connected inverter circuit, it is characterized in that, described controlled power switch is IGBT, the C utmost point that the anode of described controlled power switch is described IGBT, the E utmost point that the negative electrode of described controlled power switch is described IGBT.
5. a kind of bootstrapping according to claim 3 drives Unipolar SPWM to modulate non-isolated grid-connected inverter circuit, it is characterized in that, described controlled power switch is MOSEFT pipe, the anode of described controlled power switch is the D utmost point of described MOSEFT pipe, and the negative electrode of described controlled power switch is the S utmost point of described MOSEFT pipe.
6. a kind of bootstrapping according to claim 3 drives Unipolar SPWM to modulate non-isolated grid-connected inverter circuit, it is characterized in that, described capacitor C 1, capacitor C 2, capacitor C 3 and capacitor C 4 are equivalent capacitance.
7. a kind of bootstrapping according to claim 3 drives Unipolar SPWM to modulate non-isolated grid-connected inverter circuit, it is characterized in that, described power inductance is sendust core coiling, and described power inductance L1 and described power inductance L2 are respectively independently power inductance; Or described power inductance is sendust core coiling, described power inductance L1 and described power inductance L2 are the power inductance of coupling.
8. a kind of bootstrapping according to claim 3 drives Unipolar SPWM to modulate non-isolated grid-connected inverter circuit, it is characterized in that, described controlled power switch Q3 and described controlled power switch Q4 are operated in low frequency on off state, and described controlled power switch Q1, described controlled power switch Q6, described controlled power switch Q2 and described controlled power switch Q5 are operated in HF switch state.
9. a kind of bootstrapping according to claim 8 drives Unipolar SPWM to modulate non-isolated grid-connected inverter circuit, it is characterized in that, the state of described controlled power switch Q3 and described controlled power switch Q4 switches according to the polarity of line voltage.
10. a kind of bootstrapping according to claim 8 drives Unipolar SPWM to modulate non-isolated grid-connected inverter circuit, it is characterized in that, the state of described controlled power switch Q1, described controlled power switch Q6, described controlled power switch Q2 and described controlled power switch Q5 is controlled according to Unipolar SPWM modulation system.
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| Application Number | Priority Date | Filing Date | Title |
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| CN201320835749.9U CN203800839U (en) | 2013-12-17 | 2013-12-17 | Bootstrap driving unipolar SPWM non-isolated grid-connected inverter circuit |
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| CN201320835749.9U CN203800839U (en) | 2013-12-17 | 2013-12-17 | Bootstrap driving unipolar SPWM non-isolated grid-connected inverter circuit |
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103762871A (en) * | 2013-12-17 | 2014-04-30 | 江苏博纬新能源科技有限公司 | Bootstrap drive non-isolated grid-connected inverter circuit adopting unipolarity SPWM |
| CN107437890A (en) * | 2016-05-25 | 2017-12-05 | 松下知识产权经营株式会社 | Power transformation circuit and electrical power transmission system |
-
2013
- 2013-12-17 CN CN201320835749.9U patent/CN203800839U/en not_active Expired - Lifetime
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103762871A (en) * | 2013-12-17 | 2014-04-30 | 江苏博纬新能源科技有限公司 | Bootstrap drive non-isolated grid-connected inverter circuit adopting unipolarity SPWM |
| CN107437890A (en) * | 2016-05-25 | 2017-12-05 | 松下知识产权经营株式会社 | Power transformation circuit and electrical power transmission system |
| CN107437890B (en) * | 2016-05-25 | 2020-09-01 | 松下知识产权经营株式会社 | Power conversion circuit and power transmission system |
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