CN102148566B - Boost-type voltage balance converter - Google Patents

Boost-type voltage balance converter Download PDF

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CN102148566B
CN102148566B CN 201110100205 CN201110100205A CN102148566B CN 102148566 B CN102148566 B CN 102148566B CN 201110100205 CN201110100205 CN 201110100205 CN 201110100205 A CN201110100205 A CN 201110100205A CN 102148566 B CN102148566 B CN 102148566B
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voltage
power switch
switch tube
filter capacitor
boost
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CN102148566A (en
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张先进
张春光
宋永献
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Huaihai Institute of Techology
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Abstract

The invention discloses a boost-type voltage balance converter which is characterized by comprising an input direct current voltage source, a boost inductance circuit, a bridge circuit and an output filter circuit. The boost-type voltage balance converter can be controlled through an output voltage controller, an output voltage balance controller and a PWM (pulse-width modulation) generator. By using the boost-type voltage balance converter, not only can the purpose of boosting be realized, but also the balance of the output balance is realized by constructing a neutral line at an output end; a low input direct current voltage is converted into a high output direct current voltage, and the high output direct current voltage is converted into two low direct current voltages with the same sizes and different polarities by using the neutral line so as to realize the series connection and voltage-sharing of an electrolytic capacitor when the high voltage is output, and meet a requirement of the converter on the input voltage balance or the requirement of the electric equipment on different input voltages; and the voltage stress of each power device is a half of the output voltage, and a low-voltage power device can be adopted so as to improve the efficiency of the converter.

Description

A kind of boost-type voltage balance converter
Technical field
The present invention relates to direct current non-isolated variable device, particularly a kind of boost-type voltage balance converter in a kind of electrical energy changer.
Background technology
Booster converter is widely used among the systems such as grid-connected power generation system, storage battery power supply, low input is elevated to the high voltage of the requirement of satisfying power consumption equipment by booster converter.For example, in grid-connected power generation system, utilize booster converter that the new forms of energy output LOW voltage is transformed into high voltage, incorporate direct current network into; In uninterrupted power supply (UPS), utilize booster converter that the output voltage of storage battery is elevated to the satisfied thereafter requirement of converter input voltage.But the output voltage of traditional non-isolation boosting converter only has a kind of specification direct voltage, can't satisfy simultaneously various rear class power inverters or power consumption equipment to the requirement of input voltage.For example, the input terminal voltage of half-bridge (comprising tri-level half-bridge) converter must balance (input dc partial voltage electric capacity will all be pressed), otherwise half-bridge converter output voltage, current waveform will distorteds or can't be realized well that power device three level states affect power device safety.Simultaneously, higher owing to output voltage in the boosting inverter system, so output adopts the electrochemical capacitor series connection usually.Because series connection electrolysis electric capacity can not accomplish that impedance operator is in full accord, so can appearring in series capacitance, uneven the pressure manifest, this will seriously shorten electrochemical capacitor life.
Summary of the invention
Technical problem to be solved by this invention be for traditional booster converter output only have a kind of direct voltage and can't satisfy simultaneously the rear class converter or power consumption equipment to the deficiency of the requirement of input voltage balance, provide a kind of structure more reasonable, a kind of low-voltage direct input can be transformed into a kind of high voltage direct current output, and at center line of high voltage direct current output end structure high voltage direct current output is transformed into two equal-sized direct voltages series connection, when solving the output high pressure electrochemical capacitor series average-voltage problem and satisfy the rear class converter or power consumption equipment to the boost-type voltage balance converter of the requirement of input voltage balance.
Technical problem to be solved by this invention is to realize by following technical scheme.The present invention is a kind of boost-type voltage balance converter, is characterized in, it comprises input dc power potential source U In, boost inductance circuit, bridge circuit and output filter circuit;
Described boost inductance circuit comprises the first boost inductance L 1With the second boost inductance L 2, the first boost inductance L 1An end, the second boost inductance L 2An end respectively with input dc power potential source U InAnode, negative terminal link to each other;
Described bridge circuit comprises the first sustained diode 1, the first power switch tube S 1, the second power switch tube S 2With the second sustained diode 2, the first power switch tube S 1Drain electrode and the first sustained diode 1Anode be connected its junction and the first boost inductance L 1The other end be connected the first power switch tube S 1Source electrode and the second power switch tube S 2Drain electrode is connected, the second power switch tube S 2Source electrode and the second sustained diode 2Negative electrode be connected its junction and the second boost inductance L 2The other end is connected;
Described output filter circuit comprises the first filter capacitor C 1With the second filter capacitor C 2, the first filter capacitor C 1An end and the first sustained diode 1Negative electrode be connected the second filter capacitor C 2An end and the second sustained diode 2Anode be connected the first filter capacitor C 1The other end and the second filter capacitor C 2The other end be connected in series its junction and the first power switch tube S 1Source electrode and the second power switch tube S 2Drain electrode connection and center line L NBe connected.
The control that above-described boost-type voltage balance converter can be undertaken by output voltage controller, output voltage balance controller and PWM generator;
Described output voltage controller comprises Voltage loop adjuster I and electric current loop adjuster, wherein output voltage U oReference value U RefAnd output voltage U oDifference through the controlled signal U of Voltage loop adjuster I E1, control signal U E1As the first boost inductance L in the electric current loop adjuster 1Current i L1Feedback signal reference value and the first boost inductance L 1Current i L1The difference of feedback signal is through the controlled signal U of electric current loop adjuster E2U o=U Out1+ U Out2, U Out1Be the first filter capacitor C 1Upper voltage, U Out2Be the second filter capacitor C 2Upper voltage;
Described output voltage balance controller is Voltage loop adjuster II, the second filter capacitor C 2Upper voltage U Out2Reference value U RefThe/2 and second filter capacitor C 2Upper voltage U Out2Difference through the controlled signal U of Voltage loop adjuster II E3, and and control signal U E2Make the controlled signal U of difference operation E4
Described PWM generator comprises comparator I, comparator II and triangular wave U Tr, control signal U E2Send into comparator I and generate driving signal U Gs1Drive the first power switch tube S 1, control signal U E4Send into comparator II, generate and drive signal U Gs2Drive the second power switch tube S 2
Compared with prior art, boost-type voltage balance converter of the present invention not only can be realized the function that traditional booster converter boosts, and can construct center line at output and form stable a, voltage and equal half neutral voltage of output voltage.It not only realizes the purpose of boosting, and can solve series connection electrolysis capacitor voltage equalizing problem, satisfies rear class converter or power consumption equipment to the requirement of input voltage balance.Simultaneously, the voltage stress of every power device only has half of output voltage, can adopt low voltage power devices, is conducive to improve the efficient of converter.
Description of drawings
Fig. 1 is the circuit diagram of boost-type voltage balance converter of the present invention.
Fig. 2 is the control chart of boost-type voltage balance converter of the present invention.
Fig. 3 is the load R of boost-type voltage balance converter of the present invention 2R 1The time main oscillogram.
Fig. 4 is the load R of boost-type voltage balance converter of the present invention 2R 1The time mode 1, mode 5 equivalent circuit diagrams.
Fig. 5 is the load R of boost-type voltage balance converter of the present invention 2R 1The time mode 2, mode 4 equivalent circuit diagrams.
Fig. 6 is the load R of boost-type voltage balance converter of the present invention 2R 1The time mode 3 equivalent circuit diagrams.
Fig. 7 is the load R of boost-type voltage balance converter of the present invention 1R 2The time main oscillogram.
Fig. 8 is the artificial circuit figure of boost-type voltage balance converter of the present invention.
Fig. 9 is the load R of boost-type voltage balance converter of the present invention 2R 1The time inductive current, power device on voltage and driving simulation figure.
Figure 10 is the load R of a kind of boost-type voltage balance converter of the present invention 2R 1The time input direct voltage, output voltage analogous diagram.
Figure 11 is the load R of boost-type voltage balance converter of the present invention 1R 2The time inductive current, power device on voltage and driving simulation figure.
Figure 12 is the load R of boost-type voltage balance converter of the present invention 1R 2The time input direct voltage, output voltage analogous diagram.
Symbol among Fig. 1-12 and element names are said the name of sth. bright as follows:
U In: DC input voitage source, L 1, L 2: the first boost inductance, the second boost inductance, i L1, i L2: the first boost inductance L 1Electric current, the second boost inductance L 2Electric current, S 1, S 2: the first power switch pipe, the second power switch pipe, D 1, D 2: the first fly-wheel diode, the second fly-wheel diode, C 1, C 2: the first filter capacitor, the second filter capacitor, L N: output center line, U Out1, U Out2: the first filter capacitor C 1Upper voltage, the second filter capacitor C 2Upper voltage, U o: the first filter capacitor C 1With the second filter capacitor C 2Upper voltage sum, U Ref: output voltage U oReference value, U RefThe/2: second filter capacitor C 2Upper voltage U Out2Reference value, U E1: Voltage loop adjuster I exports control signal, U E2: electric current loop adjuster output control signal, U E3: Voltage loop adjuster II exports control signal, U E4: the output of electric current loop adjuster deducts Voltage loop adjuster II output control signal, U Tr: triangular wave, U Gs1, U Gs2: the first power switch tube S 1Drive signal, the second power switch tube S 2Drive signal, R 1, R 2: the first filter capacitor C 1Upper load, the second filter capacitor C 2Upper load, U Ds1, U Ds2: the first power switch tube S 1Drain-source voltage, the second power switch tube S 2Drain-source voltage, U D1, U D2: the first fly-wheel diode cathode to anode voltage, the second fly-wheel diode cathode to anode voltage.
Embodiment
Referring to accompanying drawing, further describe concrete technical scheme of the present invention, so that those skilled in the art understands the present invention further, and do not consist of its Copyright law.
Embodiment 1, with reference to Fig. 1-2, and a kind of boost-type voltage balance converter, it comprises input dc power potential source U In1, boost inductance circuit 2, bridge circuit 3 and output filter circuit 4;
Described boost inductance circuit 2 comprises the first boost inductance L 1With the second boost inductance L 2, the first boost inductance L 1An end, the second boost inductance L 2An end respectively with input dc power potential source U In1 anode, negative terminal link to each other;
Described bridge circuit 3 comprises the first sustained diode 1, the first power switch tube S 1, the second power switch tube S 2With the second sustained diode 2, the first power switch tube S 1Drain electrode and the first sustained diode 1Anode be connected its junction and the first boost inductance L 1The other end be connected the first power switch tube S 1Source electrode and the second power switch tube S 2Drain electrode is connected, the second power switch tube S 2Source electrode and the second sustained diode 2Negative electrode be connected its junction and the second boost inductance L 2The other end is connected;
Described output filter circuit 4 comprises the first filter capacitor C 1With the second filter capacitor C 2, the first filter capacitor C 1An end and the first sustained diode 1Negative electrode be connected the second filter capacitor C 2An end and the second sustained diode 2Anode be connected the first filter capacitor C 1The other end and the second filter capacitor C 2The other end be connected in series its junction and the first power switch tube S 1Source electrode and the second power switch tube S 2Drain electrode connection and center line L NBe connected.
Embodiment 2, the control that embodiment 1 described boost-type voltage balance converter can be undertaken by output voltage controller 5, output voltage balance controller 6 and PWM generator 7;
Described output voltage controller 5 comprises Voltage loop adjuster I and electric current loop adjuster, wherein output voltage U o(U o=U Out1+ U Out2) reference value U RefAnd output voltage U oDifference through the controlled signal U of Voltage loop adjuster I E1, control signal U E1As the first boost inductance L in the electric current loop adjuster 1Current i L1Feedback signal reference value and the first boost inductance L 1Current i L1The difference of feedback signal is through the controlled signal U of electric current loop adjuster E2U Out1Be the first filter capacitor C 1Upper voltage, U Out2Be the second filter capacitor C 2Upper voltage;
Described output voltage balance controller 6 is Voltage loop adjuster II, the second filter capacitor C 2Upper voltage U Out2Reference value U RefThe/2 and second filter capacitor C 2Upper voltage U Out2Difference through the controlled signal U of Voltage loop adjuster II E3, and and control signal U E2Make the controlled signal U of difference operation E4
Described PWM generator 7 comprises comparator I, comparator II and triangular wave U Tr, control signal U E2Send into comparator I and generate driving signal U Gs1Drive the first power switch tube S 1, control signal U E4Send into comparator II, generate and drive signal U Gs2Drive the second power switch tube S 2
Can draw according to above: as the second filter capacitor C 2Upper load R 2Greater than the first filter capacitor C 1Upper load R 1The time, the second power switch tube S 2ON time is greater than the first power switch tube S 1ON time; Otherwise, the second power switch tube S 2ON time is less than the first power switch tube S 1ON time.
Embodiment 3, and with reference to Fig. 3-6, present embodiment only provides boost-type voltage balance converter of the present invention with the second filter capacitor C 2Upper load R 2Greater than the first filter capacitor C 1Upper load R 1Describe the operation principle of boost-type voltage balance converter of the present invention in detail.The second filter capacitor C 2Upper load R 2Less than the first filter capacitor C 1Upper load R 1Situation is ignored at this.Specifically describe as follows:
Mode 1: (the first power switch tube S 1, the second power switch tube S 2Fig. 4 is seen in simultaneously conducting).
Within this time period, the first power switch tube S 1, the second power switch tube S 2Simultaneously conducting is added in the first inductance L 1With the second inductance L 2On voltage be input direct voltage U In, inductive current i under this voltage effect L1And i L2Linear increasing is until t 1Constantly turn-off the first power switch tube S 1Till.Load R 1And R 2Respectively by the first filter capacitor C 1With the second filter capacitor C 2Power supply.
Because the first power switch tube S 1, the second power switch tube S 2Simultaneously conducting is so be added in the first sustained diode 1With the second sustained diode 2Male-female pole tension U D1, U D2Be respectively the first capacitor filtering C 1With the second filter capacitor C 2Upper voltage U Out1, U Out2When stable state, U Out1=U Out2=U o/ 2, so U D1, U D2 Difference output voltage 1/2nd.
Mode 2:
Figure 987752DEST_PATH_IMAGE004
(the first power switch tube S 1Cut-off, the second power switch tube S 2Fig. 5 is seen in conducting)
At t 1Constantly turn-off the first power switch tube S 1, owing to inductive current can not suddenly change, so the first inductance L 1With the second inductance L 2Current i L1, i L2By the first sustained diode 1, the second power switch tube S 2Carry out afterflow.Inductive current i L1, i L2At voltage (U Out1-U In) the linear decline of effect, and to the first filter capacitor C 1With load R on it 1Power supply; Load R 2Continuation is by the second filter capacitor C 2Power supply.
Because the second power switch tube S 2With the first sustained diode 1So conducting is the first power switch tube S 1Drain-source voltage U Ds1Be U Out1, i.e. U o/ 2; The second sustained diode 2Male-female pole tension U D2Remain unchanged.This process is continued until t 2Constantly turn-off the second power switch tube S 2
Mode 3:
Figure 445278DEST_PATH_IMAGE006
(the first power switch tube S 1Cut-off, the second power switch tube S 2Fig. 6 is seen in cut-off)
At t 2Constantly turn-off the second power switch tube S 2, the first inductance L 1With the second inductance L 2Current i L1, i L2Will be by the first sustained diode 1With the second sustained diode 2Continue afterflow.Inductive current i L1, i L2At voltage (U o-U In) decline of effect lower linear, and to the first filter capacitor C 1With load R on it 1And the second filter capacitor C 2With load R on it 2Power supply.
Because the first sustained diode 1With the second sustained diode 2So the conducting afterflow is the first power switch tube S 1Drain-source voltage U Ds1With the second power switch tube S 2Drain-source voltage U Ds2Be respectively U Ou1, U Out2, i.e. U o/ 2.This process is continued until t 3Constantly open the second power switch tube S 2
Mode 4:
Figure 259651DEST_PATH_IMAGE008
(the first power switch tube S 1Cut-off, the second power switch tube S 2Fig. 5 is seen in conducting)
At t 3Constantly open the second power switch tube S 2, the first inductance L 1With the second inductance L 2Current i L1, i L2Will be by the first sustained diode 1With the second power switch tube S 2Continue afterflow.This process and mode 2 are in full accord, until t 4Constantly open the first power switch tube S 1Till.
Mode 5:
Figure 82113DEST_PATH_IMAGE010
(the first power switch tube S 1, the second power switch tube S 2Fig. 4 is seen in conducting)
At t 4Constantly open the first power switch tube S 1, the first power switch tube S 1, the second power switch tube S 2Simultaneously conducting enters mode 1 state.From entering the next work period.
Embodiment 4, with reference to Fig. 2, Fig. 8-12, carry out the principle simulating, verifying with embodiment 1 described non-isolation boosting formula balance of voltage device.
Simulation parameter is as follows: switching frequency is 25kHz, the first boost inductance L 1Inductance value and the second boost inductance L 2Inductance value is respectively 100 μ H, the first filter capacitor C 1With the second filter capacitor C 2Be respectively 560 μ F, input voltage is 96V, output voltage U o(U Out1+ U Out2) wish to be controlled at 300V.
Fig. 9, Figure 10 have provided load R 1Equal 20 Ω, R 2Equal 50 Ω simulation results; Figure 11, Figure 12 have provided load R 1Equal 50 Ω, R 2Equal 20 Ω simulation results.
Can find out from Fig. 9, Figure 10: work as R 2Greater than R 1The time, output voltage U o=300V, the first filter capacitor C 1With the second filter capacitor C 2Upper voltage U Out1, U Out2Be controlled in respectively 150V.Obviously simulation result is realized output voltage balance purpose.Simultaneously, the second power switch tube S 2Driving signal U Gs2Width is greater than the first power switch tube S 1Driving signal U Gs1Width, the first boost inductance L 1With the second boost inductance L 2Voltage U on current i L1, iL2 and the power device Ds2, U Ds2, U D1, U D2Maximum equals half of output voltage.
Also can find out from Figure 11, Figure 12: work as R 1Greater than R 2The time, output voltage U o(U Out1+ U Out2) be controlled at U o=300V, the first filter capacitor C 1With the second filter capacitor C 2Upper voltage U Out1, U Out2Be controlled in respectively 150V.Obviously simulation result is also realized output voltage balance purpose.Simultaneously, the first power switch tube S 1Driving signal U Gs1Width is greater than the second power switch tube S 2Driving signal U Gs2Width, the first boost inductance L 1With the second boost inductance L 2Current i L1, i L2And the voltage U on the power device Ds2, U Ds2, U D1, U D2Maximum equal output voltage half.
Simulation result shows: boost-type voltage balance converter of the present invention can be realized boosting and the purpose of output voltage balance well.

Claims (1)

1. boost-type voltage balance converter, it is characterized in that: it comprises input dc power potential source U In(1), boost inductance circuit (2), bridge circuit (3) and output filter circuit (4);
Described boost inductance circuit (2) comprises the first boost inductance L 1With the second boost inductance L 2, the first boost inductance L 1An end, the second boost inductance L 2An end respectively with input dc power potential source U In(1) anode, negative terminal link to each other;
Described bridge circuit (3) comprises the first sustained diode 1, the first power switch tube S 1, the second power switch tube S 2With the second sustained diode 2, the first power switch tube S 1Drain electrode and the first sustained diode 1Anode be connected its junction and the first boost inductance L 1The other end be connected the first power switch tube S 1Source electrode and the second power switch tube S 2Drain electrode is connected, the second power switch tube S 2Source electrode and the second sustained diode 2Negative electrode be connected its junction and the second boost inductance L 2The other end is connected;
Described output filter circuit (4) comprises the first filter capacitor C 1With the second filter capacitor C 2, the first filter capacitor C 1An end and the first sustained diode 1Negative electrode be connected the second filter capacitor C 2An end and the second sustained diode 2Anode be connected the first filter capacitor C 1The other end and the second filter capacitor C 2The other end be connected in series its junction and the first power switch tube S 1Source electrode and the second power switch tube S 2Drain electrode connection and center line L NBe connected;
The control that this converter is undertaken by output voltage controller (5), output voltage balance controller (6) and PWM generator (7);
Described output voltage controller (5) comprises Voltage loop adjuster I and electric current loop adjuster, wherein output voltage U oReference value U RefAnd output voltage U oDifference through the controlled signal U of Voltage loop adjuster I E1, control signal U E1As the first boost inductance L in the electric current loop adjuster 1Current i L1Feedback signal reference value and the first boost inductance L 1Current i L1The difference of feedback signal is through the controlled signal U of electric current loop adjuster E2U o=U Out1+ U Out2, U Out1Be the first filter capacitor C 1Upper voltage, U Out2Be the second filter capacitor C 2Upper voltage;
Described output voltage balance controller (6) is Voltage loop adjuster II, the second filter capacitor C 2Upper voltage U Out2Reference value U RefThe/2 and second filter capacitor C 2Upper voltage U Out2Difference through the controlled signal U of Voltage loop adjuster II E3, and and control signal U E2Make the controlled signal U of difference operation E4
Described PWM generator (7) comprises comparator I, comparator II and triangular wave U Tr, control signal U E2Send into comparator I and generate driving signal U Gs1Drive the first power switch tube S 1, control signal U E4Send into comparator II, generate and drive signal U Gs2Drive the second power switch tube S 2
CN 201110100205 2011-04-21 2011-04-21 Boost-type voltage balance converter Expired - Fee Related CN102148566B (en)

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