CN203301373U - Switching power supply and switching power supply controller for realizing constant output current - Google Patents
Switching power supply and switching power supply controller for realizing constant output current Download PDFInfo
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- CN203301373U CN203301373U CN2013203066919U CN201320306691U CN203301373U CN 203301373 U CN203301373 U CN 203301373U CN 2013203066919 U CN2013203066919 U CN 2013203066919U CN 201320306691 U CN201320306691 U CN 201320306691U CN 203301373 U CN203301373 U CN 203301373U
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Abstract
The utility model provides a switching power supply and a switching power supply controller for realizing constant output current. The controller comprises a switching-off time control circuit, a comparator, a logic and drive circuit and a loop control module. The switching-off time control circuit is used for determining a switching-off time; a first input end of the comparator receives a first reference voltage and a second input end of the comparator receives externally-input sampling voltages; the logic and drive circuit generates a drive signal according to output signals of the switching-off time control circuit and the comparator, and the drive signal is used for controlling switching-on/off of a power switch; and an input end of the loop control module receives the sampling voltages, an output end of the loop control module is connected with an input end of the switching-off time control circuit, and the loop control module is used for adjusting the switching-off time to make the average value of the sampling voltages in the switching-on period of the power switch equal to a second reference voltage, wherein the first reference voltage is smaller than twice the second reference voltage. The switching power supply controller can accurately control the output current so as to make the output current invulnerable to the influence of parameters such as output voltage and input voltage.
Description
Technical field
The utility model relates to switch power technology, relates in particular to a kind of Switching Power Supply and realizes the switch power controller of constant output current.
Background technology
With reference to figure 1, in the LED drive circuit of traditional buck configuration, during power switch M1 conducting, ON time is Ton, input current flow through power switch M1, sampling resistor Rcs, inductance L 1 and output load capacitance C1, the electric current on inductance L 1 increases, inductance L 1 stored energy, at this moment, the flow through electric current of output load capacitance C1, output is identical with the electric current that flows through sampling resistor Rcs.When electric current reached set point Vr1/Rcs, the upset of the output signal of comparator 113, generated corresponding triggering signal Reset through logic and driver circuitry 112, makes power switch M1 turn-off.Turn-off time Toff is determined by turn-off time control circuit 111, by external resistance R 1, regulates turn-off time Toff.At power switch M1, close and to have no progeny, the electric current on inductance L 1 is through sustained diode 1 afterflow, the sustained diode of flowing through 1 and output load capacitance C1, output, and the electric current on inductance L 1 reduces, inductance L 1 release energy output load capacitance C1 and output.
As Fig. 2, during power switch M1 conducting, the average electrical value of suppose to flow through output load capacitance C1, output is Iout1; When upper power switch M1 turn-offed, the average current value of suppose to flow through output load capacitance C1, output was Iout2, and when circuit was in the continuous current mode pattern, Iout1 was identical with Iout2.When output voltage is fixed, because peak current is fixed as Vr1/Rcs, and turn-off time Toff fixes, in Toff time internal inductance electric current drop-out value, fix, thereby the ripple of electric current determine, and then can accomplish that output current fixes.
Switching Power Supply in Fig. 1 has realized output current control, and circuit is simple, cost is lower, but shortcoming is also arranged.When output voltage changed, the turn-off time, Toff was constant, and variation has just occurred the inductive current drop-out value in identical turn-off time Toff, thereby average output current changes, and causes the load regulation of output current poor.And in the circuit of Fig. 1, due to inevitable circuit delay, from the output signal of comparator 113, being turned to power switch M1 turn-offs one section turn-off delay time is arranged, and peak electricity fails to be convened for lack of a quorum and continue to increase in this turn-off delay time, thereby while causing input voltage to change, output current also can change, and namely the constant-current characteristics of circuit is good not, the precision deficiency that constant current is controlled.
The utility model content
The technical problems to be solved in the utility model is to provide a kind of Switching Power Supply and realizes the switch power controller of constant output current, can accurately control output current, makes that output current is not subjected to output voltage, input voltage is isoparametric affects.
For solving the problems of the technologies described above, the utility model provides a kind of switch power controller of realizing constant output current, comprising:
The turn-off time control circuit, for determining the turn-off time of Switching Power Supply power switch;
Comparator, its first input end receives the first reference voltage, and its second input receives the sampled voltage of outside input;
Logic and driver circuitry, produce the driving signal according to the output signal of described turn-off time control circuit and comparator, and this driving signal is for controlling the turn-on and turn-off of described power switch;
The loop control module, its input receives described sampled voltage, its output is connected with the input of described turn-off time control circuit, for regulating the described turn-off time so that the mean value of described power switch described sampled voltage of conduction period equates with the second reference voltage, wherein, described the first reference voltage is less than 2 times of described the second reference voltage.
According to an embodiment of the present utility model, described loop control module comprises: trsanscondutance amplifier, in described power switch conduction period, its output current is directly proportional to the difference of described the second reference voltage and sampled voltage, and this output current is for repaying circuit and discharge and recharge to filling, at described power switch blocking interval, the output current of described trsanscondutance amplifier stops discharging and recharging to described compensating circuit, the turn-off time that the voltage on described compensating circuit produces for regulating described turn-off time control circuit.
according to an embodiment of the present utility model, the first input end of described trsanscondutance amplifier receives described sampled voltage, the second input of described trsanscondutance amplifier receives described the second reference voltage, the output of described trsanscondutance amplifier connects the first end of the first switch, the second end of described the first switch connects the input of described compensating circuit and described turn-off time control circuit, the control end of described the first switch receives described driving signal, at described power switch described the first switch conduction of conduction period, at described the first switch of described power switch blocking interval, turn-off.
according to an embodiment of the present utility model, the first input end of described trsanscondutance amplifier connects the first end of second switch and the first end of the 3rd switch, the second input of described trsanscondutance amplifier receives described the second reference voltage, the output of described trsanscondutance amplifier connects the input of described compensating circuit and described turn-off time control circuit, the second termination of described second switch is received described sampled voltage, the control end of described second switch receives described driving signal, the second termination of described the 3rd switch is received described the second reference voltage, the control end of described the 3rd switch receives the inversion signal of described driving signal, in described power switch conduction period, described second switch conducting and described the 3rd switch turn-off, at described power switch blocking interval, described second switch turn-offs and described the 3rd switch conduction.
According to an embodiment of the present utility model, when described sampled voltage reached described the first reference voltage, the driving signal that the output signal of described comparator makes described logic and driver circuitry produce turn-offed this power switch.
According to an embodiment of the present utility model, after the time that described power switch is turned off reaches the described turn-off time, this power switch of driving signal conduction that the output signal of described turn-off time control circuit makes described logic and driver circuitry produce.
The utility model also provides a kind of Switching Power Supply, comprising:
The described switch power controller of above any one;
Fly-wheel diode, its negative pole receives input voltage;
Output capacitance and the inductance of series connection, in parallel with described fly-wheel diode;
Power switch, its first end connects the positive pole of described fly-wheel diode, and the described sampled voltage of its second end output is to described switch power controller, and its control end receives the driving signal of described switch power controller output;
Sampling resistor, its first end connects the second end of described power switch, its second end ground connection.
Compared with prior art, the utlity model has following advantage:
The switch power controller of the utility model embodiment obtains the sampled voltage on sampling resistor in the power switch conduction device sampling of Switching Power Supply, and by the loop control module, the turn-off time is carried out to loop adjustment, the mean value of controlling this sampled voltage remains unchanged, characteristics while utilizing the Switching Power Supply of buck configuration to be in the continuous current mode pattern, reach the purpose of constant output current.
Furthermore, the loop control module of the utility model embodiment mainly comprises trsanscondutance amplifier, it carries out the error amplification to the sampled voltage on sampling resistor and the second reference voltage, its output connects compensating circuit, voltage transmission on compensating circuit to the turn-off time control circuit in order to determine the turn-off time, after loop stability, the mean value of the sampled voltage on power switch conduction period sampling resistor is identical with this second reference voltage, and output current is determined by the resistance value of this second reference voltage and sampling resistor.
Switching Power Supply and the controller circuitry thereof of the utility model embodiment are simple, and all it doesn't matter for the parameters such as output current and input voltage, output voltage, inductance value, can realize accurate constant-current characteristics.
The accompanying drawing explanation
Fig. 1 is the structural representation of a kind of Switching Power Supply of buck configuration continuous operation mode in prior art;
Fig. 2 is the signal timing diagram of Switching Power Supply shown in Figure 1;
Fig. 3 is the structural representation of the Switching Power Supply of the utility model the first embodiment;
Fig. 4 is the structural representation of the Switching Power Supply of the utility model the second embodiment;
Fig. 5 is the signal timing diagram of Fig. 3 and Switching Power Supply shown in Figure 4;
Fig. 6 is the electrical block diagram of the trsanscondutance amplifier in the switch power controller of the utility model embodiment.
Embodiment
The utility model is described in further detail below in conjunction with specific embodiments and the drawings, but should not limit protection range of the present utility model with this.
With reference to the Switching Power Supply in figure 3, the first embodiment, mainly comprise: power switch M1, inductance L 1, sampling resistor Rcs, sustained diode 1, output capacitance C1 and switch power controller 300.
wherein, the negative pole of sustained diode 1 receives input voltage vin, the first end of output capacitance C1 connects the negative pole of sustained diode 1, the first end of inductance L 1 connects the positive pole of sustained diode 1, the second end of inductance L 1 connects the second end of output capacitance C1, the first end of power switch M1 connects the positive pole of sustained diode 1, the second end of power switch M1 connects the first end of sampling resistor Rcs, the driving signal GT of control end receiving key power-supply controller of electric 300 outputs of power switch M1, the first end of sampling resistor Rcs connects the second end of power switch M1, the second end ground connection of sampling resistor Rcs, sampled voltage on switch power controller 300 reception sampling resistor Rcs output drive signal GT are to the control end of power switch M1, turn-on and turn-off in order to power ratio control switch M1.
Furthermore, output capacitance C1 mainly plays the effect of output current filtering, reduces the ripple of output current and output voltage.And connect between inductance L 1 and output capacitance C1, the link position of the two can exchange, and output capacitance C1 is configured in parallel with load.
During power switch M1 conducting, inductance L 1 stored energy, the electric current of the inductance L 1 of flowing through this moment is identical with the electric current of flow through output capacitance C1 and output end vo ut, and output current is identical with the electric current of the sampling resistor Rcs that flows through.When power switch M1 turn-offed, the electric current of the inductance L of flowing through 1 to output capacitance C1 and output end vo ut afterflow, continued transferring energy to load through sustained diode 1.All the time greater than zero, the average current of the inductance L 1 of flowing through when the average current of the inductance L 1 of flowing through during power switch M1 conducting turn-offs with power switch M1 is identical, and is also identical with the electric current of the output capacitance C1 that flows through, output end vo ut when the electric current of inductance L 1.
Furthermore, the first input end of comparator circuit 313 receives the first reference voltage V r1, the second input connects the first end of sampling resistor Rcs, when the sampled voltage on sampling resistor Rcs during higher than default the first reference voltage V r1, the output signal upset of comparator 313, output cut-off signals Reset is to logic and driver circuitry 312.Turn-off time control circuit 311 is determined the turn-off time according to the control voltage Vc of loop control module 310 outputs, when power switch M1 turn-offs, starts timing, and after timing reached this turn-off time, output was opened signal Set to logic and driver circuitry 312.Logic and driver circuitry 312 is according to the cut-off signals Reset of turn-off time control circuit 311 and comparator 313 outputs and open signal Set and produce and drive signal GT, turn-on and turn-off state for power switched switch M1, when opening signal Set arrival, drive signal GT and make power switch M1 conducting, when cut-off signals Reset arrives, drive signal GT and make power switch M1 turn-off.The input of loop control module 310 receives the sampled voltage on sampling resistor Rcs, its output produces this control voltage Vc, control the turn-off time that voltage Vc determines for regulating turn-off time control circuit 311, so that the mean value of the sampled voltage of power switch M1 conduction period and the second reference voltage V r2 equate, wherein the first reference voltage V r1 is less than 2 times of the second reference voltage V r2.
It should be noted that, because the turn-off time in side circuit postpones, the sampled voltage while causing actual power switch M1 to turn-off is wanted a little higher than the first reference voltage V r1.
In the first embodiment, loop control module 310 comprises trsanscondutance amplifier 314 and the first switch S 1.Wherein, the first input end of trsanscondutance amplifier 314 receives sampled voltage, the second input of trsanscondutance amplifier 314 receives the second reference voltage V r2, the output of trsanscondutance amplifier connects the first end of the first switch S 1, the second end of the first switch S 1 connects the first end of building-out capacitor C2 and the input of turn-off time control circuit 311, the control end of the first switch S 1 receives and drives signal GT, the second end ground connection of building-out capacitor C2.In power switch M1 conduction period first switch S 1 conducting, in power switch M1 blocking interval the first switch S 1, turn-off.
Furthermore, in 314 normal operations of power switch M1 conduction period trsanscondutance amplifier, the output current Igm of trsanscondutance amplifier 314 is the electric currents that are directly proportional to the input voltage difference of trsanscondutance amplifier 314, the value that namely is directly proportional to (Vr2-Vcs), specifically be expressed as Igm=Gm*(Vr2-Vcs), wherein, Gm is the mutual conductance of trsanscondutance amplifier 314, for the circuit of determining, be a steady state value, Vr2 is the magnitude of voltage of the second reference voltage V r2, and Vcs is the magnitude of voltage of sampled voltage.At power switch M1 blocking interval, the disconnection that is connected of trsanscondutance amplifier 314 and building-out capacitor C2.The output current Igm of trsanscondutance amplifier 314 is for to building-out capacitor C2, discharging and recharging, thereby generation is for regulating the control voltage Vc of turn-off time.
Negative feedback characteristic by loop is as can be known, when output current is bigger than normal, cause the output current of trsanscondutance amplifier 314 less than normal and make and control voltage Vc and reduce, and then the turn-off time that makes turn-off time control circuit 311 determine is elongated, thereby regulate, reduces output current.The output current integration of building-out capacitor C2 to trsanscondutance amplifier 314 equates that with the mean value of two inputs finally realizing trsanscondutance amplifier 314 after loop stability, the control voltage Vc on building-out capacitor C2 is stable, and the turn-off time is determined.
In addition, it will be appreciated by those skilled in the art that building-out capacitor C2 can adopt the other forms of compensating circuits such as connection in series-parallel of resistance capacitance to replace, with stability and the dynamic characteristic of regulating circuit.
the operation principle of this Switching Power Supply is as follows: power switch M1 conduction period, on sampling resistor Rcs, has sampled voltage Vcs, sampled voltage Vcs is input to an input of trsanscondutance amplifier 314, another input of trsanscondutance amplifier 314 connects the second reference voltage V r2, trsanscondutance amplifier has following characteristic: the output current Igm of trsanscondutance amplifier is directly proportional to the input difference voltage (Vr2-Vcs) of trsanscondutance amplifier 314, be Igm=Gm*(Vr2-Vcs), Gm is the mutual conductance of trsanscondutance amplifier 314, for the circuit of determining, it is a steady state value, the output of trsanscondutance amplifier 314 is connected to compensating circuit, at power switch M1 blocking interval, the output of trsanscondutance amplifier 314 and the path between compensating circuit disconnect, voltage on compensating circuit has determined the turn-off time of power switch M1, when sampled voltage reached the first reference voltage V r1 of setting, power switch M1 turn-offed, in order to guarantee that Switching Power Supply is in the continuous current mode pattern, require the first reference voltage V r1 less than the second reference voltage V r2 of 2 times, after loop stability, the mean value of the output current Igm of trsanscondutance amplifier 314 is zero, and the constant output current of whole Switching Power Supply is exactly the ratio of the second reference voltage V r2 and sampling resistor Rcs.
Fig. 4 shows the structure of the Switching Power Supply of the second embodiment, and itself and Switching Power Supply shown in Figure 3 are similar, are only that the concrete structure of loop control module makes an adjustment.As shown in Figure 4, the loop control module in the second embodiment comprises trsanscondutance amplifier 314, second switch S2 and the 3rd switch S 3.wherein, the first input end of trsanscondutance amplifier 314 connects the first end of second switch S2 and the first end of the 3rd switch S 3, the second input of trsanscondutance amplifier 314 receives the second reference voltage V r2, the output of trsanscondutance amplifier 314 connects the input of compensating circuit and turn-off time control circuit 311, the second termination of second switch S2 is received sampled voltage, the control end of second switch S2 receives and drives signal GT, the second termination of the 3rd switch S 3 is received the second reference voltage V r2, the control end of the 3rd switch receives the inversion signal that drives signal GT, in power switch M1 conduction period, second switch S2 conducting and the 3rd switch S 3 are turn-offed, at power switch M1 blocking interval, second switch S2 turn-offs and the 3rd switch S 3 conductings.More specifically, drive the inversion signal of signal GT by inverter 315 generations.
From on effect, in power switch M1 conduction period, the negative input end of trsanscondutance amplifier 314 connects sampling resistor Rcs, and the positive input terminal of trsanscondutance amplifier 314 receives the second reference voltage V r2.At power switch M1 blocking interval, it is certain that the positive input terminal of trsanscondutance amplifier 314 and negative input end all receive the second reference voltage V r2(, this current potential can be also other any current potentials), characteristic by trsanscondutance amplifier 314 can be known, this moment, the output current of trsanscondutance amplifier 314 was zero, be equivalent to disconnect being connected between trsanscondutance amplifier 314 and building-out capacitor C2, so loop control module equivalence in its circuit function and the first embodiment.
It should be noted that, what in Fig. 3 and Fig. 4, provide is only example, as long as in fact can meet trsanscondutance amplifier, in power switch M1 conduction period, to compensating circuit, discharges and recharges, and at power switch M1 blocking interval, stops discharging and recharging and getting final product to compensating circuit.
With reference to figure 5, Fig. 5 shows the working signal oscillogram of Fig. 3 and Switching Power Supply shown in Figure 4.During power switch M1 conducting, the average electrical value of suppose to flow through output capacitance C1, output end vo ut is Iout1; When power switch M1 turn-offed, the average current value of suppose to flow through output capacitance C1, output end vo ut was Iout2.When circuit is in the continuous current mode pattern, Iout1 and Iout2 should be identical, so in the utility model, pass through to control Iout1, correspondingly controlled the output current of whole switch periods.
Under inductive current is in continuous mode, the current ripples of supposing output current Iout is Ib-Ia, wherein Ib is peak current, Ia is minimum current, Ib is arranged greater than Vr1/Rcs, Vr2/Rcs=(Ib+Ia)/2 is arranged again, Vr2/Rcs=(Ib+Ia)/2 is obviously arranged Ib/2 > Vr1/ (2*Rcs), also namely can obtain Vr2 > 1/2*Vr1.Therefore, the first reference voltage V r1 that is used as the peak current comparison point in the present embodiment is less than the second reference voltage V r2 as Average Current Control point of 2 times, to guarantee that circuit working is at continuous current mode.
Fig. 6 shows the particular circuit configurations of the trsanscondutance amplifier of the present embodiment employing, mainly comprises: current mirror 61, current mirror 62, current mirror 63, triode Q1, triode Q2, resistance R 1, resistance R 2 and current source I0.
Wherein, current mirror 61 comprises MOS transistor M3 and MOS transistor M7, and current mirror 62 comprises MOS transistor M2 and MOS transistor M4, and current mirror 63 comprises MOS transistor M5 and M6.Sampled voltage Vcs inputs to the base stage of triode Q1, and the second reference voltage V r2 inputs to the base stage of triode Q2.Suppose MOS transistor M2 to the image current of MOS transistor M4 than being K2, MOS transistor M7 is K1 via MOS transistor M3, M5 to the image ratio of MOS transistor M6, the electric current I 4 of the MOS transistor of flowing through M4 is: I
4=K
2I
2, the electric current I 6 of the MOS transistor of flowing through M6 is: I
6=K
1I
1.The output current Icomp of whole trsanscondutance amplifier is:
I
comp=I
4-I
6=K
2·I
2-K
1·I
1
General Requirements K1=K2=K, R1=R2=R, current source I
0The electric current I that provides
0Enough large, guarantee that I1 and I2, greater than zero, have following relation to set up:
Be that mutual conductance Gm is:
After circuit was stable, the current average Icompavg of output current Icomp was zero, namely
I
compavg=0
Therefore there is the mean value of sampled voltage Vcs of input identical with the mean value of the second reference voltage V r2, the mean value of sampled voltage Vcs is exactly the mean value of switch power supply output current divided by the resistance value of sampling resistor Rcs, and the current value of the output current of Switching Power Supply is Vr2/Rcs thus.
Shown in Figure 6 is only example, it will be appreciated by those skilled in the art that trsanscondutance amplifier can also adopt other any suitable structures.
The above, be only preferred embodiment of the present utility model, not the utility model done to any pro forma restriction.Therefore, every content that does not break away from technical solutions of the utility model, just according to technical spirit of the present utility model to any simple modification made for any of the above embodiments, the conversion that is equal to, all still belong in the protection range of technical solutions of the utility model.
Claims (7)
1. switch power controller of realizing constant output current comprises:
The turn-off time control circuit, for determining the turn-off time of Switching Power Supply power switch;
Comparator, its first input end receives the first reference voltage, and its second input receives the sampled voltage of outside input;
Logic and driver circuitry, produce the driving signal according to the output signal of described turn-off time control circuit and comparator, and this driving signal is for controlling the turn-on and turn-off of described power switch;
It is characterized in that,
The loop control module, its input receives described sampled voltage, its output is connected with the input of described turn-off time control circuit, for regulating the described turn-off time so that the mean value of described power switch described sampled voltage of conduction period equates with the second reference voltage, wherein, described the first reference voltage is less than 2 times of described the second reference voltage.
2. switch power controller according to claim 1, it is characterized in that, described loop control module comprises: trsanscondutance amplifier, in described power switch conduction period, its output current is directly proportional to the difference of described the second reference voltage and sampled voltage, and this output current is for discharging and recharging to compensating circuit, at described power switch blocking interval, the output current of described trsanscondutance amplifier stops discharging and recharging to described compensating circuit, the turn-off time that the voltage on described compensating circuit produces for regulating described turn-off time control circuit.
3. switch power controller according to claim 2, it is characterized in that, the first input end of described trsanscondutance amplifier receives described sampled voltage, the second input of described trsanscondutance amplifier receives described the second reference voltage, the output of described trsanscondutance amplifier connects the first end of the first switch, the second end of described the first switch connects the input of described compensating circuit and described turn-off time control circuit, the control end of described the first switch receives described driving signal, at described power switch described the first switch conduction of conduction period, at described the first switch of described power switch blocking interval, turn-off.
4. switch power controller according to claim 2, it is characterized in that, the first input end of described trsanscondutance amplifier connects the first end of second switch and the first end of the 3rd switch, the second input of described trsanscondutance amplifier receives described the second reference voltage, the output of described trsanscondutance amplifier connects the input of described compensating circuit and described turn-off time control circuit, the second termination of described second switch is received described sampled voltage, the control end of described second switch receives described driving signal, the second termination of described the 3rd switch is received described the second reference voltage, the control end of described the 3rd switch receives the inversion signal of described driving signal, in described power switch conduction period, described second switch conducting and described the 3rd switch turn-off, at described power switch blocking interval, described second switch turn-offs and described the 3rd switch conduction.
5. switch power controller according to claim 1, is characterized in that, when described sampled voltage reached described the first reference voltage, the driving signal that the output signal of described comparator makes described logic and driver circuitry produce turn-offed this power switch.
6. switch power controller according to claim 5, it is characterized in that, after the time that described power switch is turned off reaches the described turn-off time, this power switch of driving signal conduction that the output signal of described turn-off time control circuit makes described logic and driver circuitry produce.
7. a Switching Power Supply, is characterized in that, comprising:
The described switch power controller of any one in claim 1 to 6;
Fly-wheel diode, its negative pole receives input voltage;
Output capacitance and the inductance of series connection, in parallel with described fly-wheel diode;
Power switch, its first end connects the positive pole of described fly-wheel diode, and the described sampled voltage of its second end output is to described switch power controller, and its control end receives the driving signal of described switch power controller output;
Sampling resistor, its first end connects the second end of described power switch, its second end ground connection.
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| CN2013203066919U CN203301373U (en) | 2013-05-30 | 2013-05-30 | Switching power supply and switching power supply controller for realizing constant output current |
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| CN2013203066919U CN203301373U (en) | 2013-05-30 | 2013-05-30 | Switching power supply and switching power supply controller for realizing constant output current |
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103248227A (en) * | 2013-05-30 | 2013-08-14 | 杭州士兰微电子股份有限公司 | Switching power supply and switching power supply controller for realizing constant output current |
| CN103916018A (en) * | 2014-03-28 | 2014-07-09 | 上海新进半导体制造有限公司 | Switching power supply |
-
2013
- 2013-05-30 CN CN2013203066919U patent/CN203301373U/en not_active Expired - Fee Related
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103248227A (en) * | 2013-05-30 | 2013-08-14 | 杭州士兰微电子股份有限公司 | Switching power supply and switching power supply controller for realizing constant output current |
| CN103916018A (en) * | 2014-03-28 | 2014-07-09 | 上海新进半导体制造有限公司 | Switching power supply |
| CN103916018B (en) * | 2014-03-28 | 2016-09-21 | 上海新进半导体制造有限公司 | A kind of Switching Power Supply |
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