CN203278746U - Low power consumption and high gain upper mixer - Google Patents
Low power consumption and high gain upper mixer Download PDFInfo
- Publication number
- CN203278746U CN203278746U CN 201320031759 CN201320031759U CN203278746U CN 203278746 U CN203278746 U CN 203278746U CN 201320031759 CN201320031759 CN 201320031759 CN 201320031759 U CN201320031759 U CN 201320031759U CN 203278746 U CN203278746 U CN 203278746U
- Authority
- CN
- China
- Prior art keywords
- nmos
- pipe
- nmos pipe
- drain electrode
- input
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Withdrawn - After Issue
Links
Images
Landscapes
- Amplifiers (AREA)
Abstract
Provided is a low power consumption and high gain upper mixer providing with a current source unit, an input transconductance unit, a switch unit, a load unit and a current injection unit. An output terminal of the current source unit is connected with the input transconductance unit; the input transconductance unit amplifies signals and enhances signals via positive feedback, and respectively transmits to the switch unit and the current injection unit; and an output terminal of the switch unit is connected with the load unit. Difference radio frequency output signals are outputted between the load unit and the switch unit, difference base-bands or intermediate frequency signals are inputted between the input transconductance unit and the current source unit, and local oscillator input signals are inputted to the switch unit.
Description
Technical field
The utility model relates to the frequency changer circuit in all kinds of transmitting sets, especially a kind of upper frequency mixer of low-power consumption high-gain, can be applied to rf chip, for example in the transceiving chips such as wireless lan (wlan), wireless sense network (WSN), global positioning system (GPS), radio-frequency recognition system (RFID), Bluetooth system, mobile communication system, mobile digital TV (CMMB, TMMB).
Background technology
Generally as the frequency changer circuit of all kinds of transmitting sets, its function is that low frequency signal is converted to the high-frequency signal that is beneficial to wireless transmission to upper frequency mixer, and for most volume radio-frequency (RF) emission system, upper frequency mixer is a requisite module.In order to extend system battery useful life, wish that in transmitter, each module reduces power consumption, and on the basis that reduces power consumption, upper frequency mixer need provide certain or higher voltage gain.The upper frequency mixer IP kernel that designs a low-power consumption high-gain has application prospect and using value comparatively widely.
Traditional gilbert mixer is widely used in the design of upper frequency mixer, and main cause is that it has certain gain and larger isolation, and traditional gilbert mixer circuit as shown in Figure 1.By regulating M1 and setovering and to control the circuital current size.Difference base band or intermediate-freuqncy signal are from the grid input of M2, M3, and the size and the biasing thereof that change M2 and M3 can be regulated frequency mixer mutual conductance g
m, then the size of regulating load resistance R 5 and R6, can obtain different voltage gains.M4-M7 is switching tube, by regulating its size and bias voltage thereof, and at the local oscillation signal of its grid input difference, can make them be operated on off state, realizes local oscillation signal and amplifies base band or the intermediate-freuqncy signal of coming from M2 and M3 and carry out mixing.This structure has certain gain and higher isolation.But traditional gilbert mixer has following shortcoming:
The firstth, power consumption is large, in order to make mixer, certain gain is arranged, and to satisfy system requirements, its electric current need reach a milliampere level.
The secondth, gain low, the size of load impedance is depended in the gain of tradition gilbert mixer to a great extent, but heavy load impedance meeting brings too much pressure drop, and the existence due to parasitic capacitance, gain meeting at high frequency treatment sharply descends, even if produce than heavy load with the LC resonant tank without pressure drop almost, but can not produce very large load impedance because its quality factor are limited.
The 3rd is that noise factor is large, the tradition gilbert mixer is from grid end input signal, and the input impedance of seeing into from the grid end is very large, and is poor with front stage circuits output impedance (being generally more than 100 ohm) or 50 ohm of matching degrees, cause noise factor larger, be difficult to satisfy system's needs.
Summary of the invention
The purpose of this utility model is for overcoming the deficiency of traditional gilbert's upper frequency mixer, propose a kind of upper frequency mixer of low-power consumption high-gain, can when reducing circuit power consumption, improving circuit gain, noise-reduction coefficient.
the technical scheme that the utility model is taked is as follows: a kind of upper frequency mixer of low-power consumption high-gain, it is characterized in that: be provided with current source cell, the input transconductance cell, switch element, load unit and electric current inject the unit, the output of current source cell connects the input transconductance cell, input transconductance cell amplifying signal also strengthens signal by positive feedback, then export respectively switch element and electric current to and inject the unit, the output of switch element connects load unit, difference radio frequency output signal is exported between load unit and switch element, difference base band or intermediate-freuqncy signal input between input transconductance cell and current source cell, the local oscillator input signal inputs to switch element, wherein:
Current source cell comprises NMOS pipe M1 and NMOS pipe M2, the source ground of NMOS pipe M1 and NMOS pipe M2, and grid connects bias voltage V
b1, drain electrode connects the positive and negative two ends that connect respectively difference base band or intermediate-freuqncy signal;
The input transconductance cell comprises NMOS pipe M3 and NMOS pipe M4, NMOS pipe M3 be connected M4 with NMOS source electrode is managed with the NMOS of current source cell M1 is connected M2 with NMOS drain electrode respectively and is connected, the positive input terminal of base band or intermediate-freuqncy signal is from the source electrode input of NMOS pipe M3, the negative input end of base band or intermediate-freuqncy signal is from the source electrode input of NMOS pipe M4, the grid of NMOS pipe M3 is connected to the drain electrode of NMOS pipe M4, and the grid of NMOS pipe M4 is connected to the drain electrode of NMOS pipe M3;
Switch element comprises NMOS pipe M5, NMOS pipe M6, NMOS pipe M7, NMOS pipe M8, resistance R 1, resistance R 2, and NMOS pipe M5 is connected the gate interconnection of M8 and connects supply voltage V by series resistance R2 with NMOS
dd, NMOS pipe M6 is connected the gate interconnection of M7 and connects supply voltage V by series resistance R1 with NMOS
ddNMOS pipe M5 is connected M6 with NMOS source electrode interconnects and connects the drain electrode that the NMOS that inputs transconductance cell manages M3, NMOS pipe M7 is connected M8 with NMOS source electrode interconnects and connects the drain electrode that the NMOS that inputs transconductance cell manages M4, the drain electrode interconnection of the drain electrode of NMOS pipe M5 and NMOS pipe M7, the drain electrode interconnection of the drain electrode of NMOS pipe M6 and NMOS pipe M8, local oscillator input signal anode connects the grid of NMOS pipe M5 and NMOS pipe M8, and local oscillator input signal negative terminal connects the grid of NMOS pipe M6 and NMOS pipe M7;
Load unit comprises PMOS pipe M9, PMOS pipe M10, inductance L 1, capacitor C 1, inductance L 2, capacitor C 2, the drain electrode of PMOS pipe M9 and the NMOS of switch element manage that M5 is connected M7 with NMOS drain electrode is connected and as the signal positive output end of upper frequency mixer, the drain electrode of PMOS pipe M10 and the NMOS of switch element manage that M6 is connected M8 with NMOS drain electrode is connected and as the signal negative output terminal of upper frequency mixer, the grid of PMOS pipe M9 connects the drain electrode of PMOS pipe M10, the grid of PMOS pipe M10 connects the drain electrode of PMOS pipe M9, inductance L 1 is in parallel with capacitor C 1, their end and supply voltage V
ddConnect, the other end is connected with the source electrode of PMOS pipe M9, and inductance L 2 is in parallel with capacitor C 2, their end and supply voltage V
ddConnect, the other end is connected with the source electrode of PMOS pipe M10;
Electric current injects the unit and comprises PMOS pipe M11 and PMOS pipe M12, and the grid of PMOS pipe M11 and PMOS pipe M12 is connected to bias voltage V
b2The drain electrode of PMOS pipe M11 is connected with the drain electrode of input transconductance cell NMOS pipe M3, the grid of NMOS pipe M4 and switch element NMOS pipe M5 is connected M6 with NMOS source electrode, the drain electrode of PMOS pipe M12 is connected with the drain electrode of input transconductance cell NMOS pipe M4, the grid of NMOS pipe M3 and switch element NMOS pipe M7 is connected M8 with NMOS source electrode, source electrode and the supply voltage V of PMOS pipe M11 and PMOS pipe M12
ddConnect.
Field effect transistor in foregoing circuit also can realize with bipolar transistor, only the NMOS pipe need to be replaced to NPN type triode, and the PMOS pipe replaces to the positive-negative-positive triode and gets final product.
Advantage of the present utility model and remarkable result:
(1) low-power consumption.
The utility model uses positive feedback technique to improve the equivalent transconductance of mutual conductance pipe.And use the LC shunt-resonant circuit with transistor series as load to increase load impedance, simultaneously transistor is connected into the positive feedback form with the increase output signal.Above two kinds of technology make the utility model compare with traditional upper frequency mixer, in the situation that it is lower to obtain the identical gain power consumption.
In the 2.4-2.5GHz frequency range, supply voltage is 1.8V, under the condition of identical gain (10dB), the utility model power consumption is 0.9mW, the tradition gilbert mixer is 4.5mW, only the frequency mixer of working load enhancing technology and current injection is 1.5mW, only uses the frequency mixer of mutual conductance positive feedback technique and current injection to be 2mW.The utility model power consumption is far below other structures.
(2) high-gain.
The utility model uses positive feedback technique to improve the equivalent transconductance of mutual conductance pipe; And use LC shunt-resonant circuit and transistor series as load, simultaneously transistor is connected into the positive feedback form.With only have the LC shunt-resonant circuit to do load to compare, increased load impedance and output signal, thereby increased substantially gain.
At 2.4-2.5GHz frequency range and identical power consumption (supply voltage 1.8V, operating current 0.5mA) under condition, by emulation, conversion gain of the present invention and other three kinds of frequency mixers are compared, gain of the present utility model is 10dB, the gain of tradition gilbert mixer is-5dB, only the mixer gain of working load enhancing technology and current injection is 4dB, only uses the mixer gain of mutual conductance positive feedback technique and current injection to be 0dB.Gain of the present utility model is far above other structures.
(3) low noise.
The utility model has reduced the input impedance of circuit from mutual conductance pipe source electrode input signal, makes itself and genertor impedance form better coupling, thereby has reduced noise factor.
In the 2.4-2.5GHz frequency range, supply voltage is 1.8V, operating current is 0.5mA, the signal source internal resistance is in the situation of 50 ohm, by emulation, noise factor of the present utility model and other three kinds of frequency mixers are compared, noise factor of the present utility model is lower than 14dB, only the mixer noiser coefficient of working load enhancing technology and current injection is the 14.3dB left and right, only use the mixer noiser coefficient of mutual conductance positive feedback technique and current injection to be the 14.5dB left and right, the noise factor of traditional gilbert mixer is greater than 40dB.The utility model also has superiority on noise factor.
(4) the utility model adopts gilbert's structure+mutual conductance positive feedback technique+load to strengthen the upper frequency mixer of technology+mutual conductance source electrode input+current injection, can significantly reduce power consumption, improve the changing voltage gain, noise-reduction coefficient can be applied in radio frequency front-end with low power consumption.
Description of drawings
Fig. 1 is the circuit theory diagrams of traditional gilbert mixer;
Fig. 2 is the circuit block diagram of the utility model upper frequency mixer;
Fig. 3 is the circuit theory diagrams of the utility model upper frequency mixer;
Fig. 4 is that under identical power consumption, the conversion gain simulation curve compares;
Fig. 5 is that under identical power consumption, the noise factor simulation curve compares;
Fig. 6 is the implementing circuit figure that the field effect transistor in Fig. 3 circuit is substituted with bipolar transistor.
Embodiment
Referring to Fig. 2, the utility model is provided with current source cell 1, input transconductance cell 2, switch element 3, load unit 4 and electric current and injects unit 5.The positive and negative two ends V of difference base band or intermediate-freuqncy signal
in+, V
in-connect respectively between current source cell 1 and input transconductance cell, current source cell 1 output is connected with the input of input transconductance cell 2, input transconductance cell 2 amplifying signals and positive feedback are injected unit 5 in self then exporting switch element 3 and electric current to, the output of switch element 3 connects load unit 4, difference radio frequency output signal V
rf+, V
rf-between load unit 4 and switch element 3 output, switch element 3 also with local oscillator input signal V
LO+, V
LO-connect.
Referring to Fig. 3, current source cell 1 is comprised of the NMOS pipe, can control the electric current (power consumption) of whole upper frequency mixer circuit by regulating NMOS pipe size and their gate bias, can arrange power consumption less by current source cell 1 in the present invention.The base band of difference or intermediate-freuqncy signal have reduced the input impedance of upper frequency mixer from the source electrode input of the NMOS pipe of input transconductance cell 2 from the source electrode input, improved the matching degree with source impedance, thereby have reduced the noise factor of whole circuit.Adopt the intersection positive feedback technique between the NMOS pipe of input transconductance cell 2, the gain that has improved upper frequency mixer.The output of input transconductance cell 2 is connected to switch element 3, makes its output carry out mixing with local oscillation signal at switch element 3.The output of switch element 3 is connected to load unit 4.Load unit 4 employing LC resonant tanks produce a part of load impedance, and adopt the PMOS pipe to strengthen its load impedance, and the while strengthens mixer output signal by the intersection positive feedback of PMOS pipe again, thereby improves the gain of upper frequency mixer.Difference radio frequency output signal is from the PMOS pipe drain electrode output of load unit 4.Electric current injects unit 5 and is connected with output and the switch element 3 of input transconductance cell 2, can regulate the electric current of flow through switch element 3 and load unit 4 by the biasing of regulating its PMOS pipe, thus the noise of control switch unit 3 and the size of load unit 4 positive feedbacks.Current source cell 1 is provided with NMOS pipe M1, M2; Input transconductance cell 2 is provided with NMOS pipe M3, M4; Switch element 3 is provided with NMOS pipe M5, M6, M7, M8 and resistance R 1, R2; Load unit 4 is provided with PMOS pipe M9, M10, inductance L 1, L2 and capacitor C 1, C2; Electric current injects the unit and is provided with PMOS pipe M11, M12; Circuit connecting relation is as follows:
The source electrode of NMOS pipe M1, the M2 of current source cell 1 is connected and ground connection, and the grid of M1, M2 is connected to bias voltage V
b1, the drain electrode of M1, M2 is connected respectively to the source electrode of NMOS pipe M3, the M4 of input transconductance cell 2.
Difference base band or intermediate frequency input signal V
in+, V
in-respectively from the source electrode input of NMOS pipe M3, the M4 of input transconductance cell 2, the grid of M3 is connected with the drain electrode of M4, the grid of M4 is connected with the drain electrode of M3, and the drain electrode of M3 is connected with the source electrode of the NMOS of switch element pipe M5, M6, and the drain electrode of M4 is connected with the source electrode of the NMOS of switch element pipe M7, M8.
Difference local oscillator input signal V
LO+, V
LO-manage respectively the grid input of grid and NMOS pipe M6, the M7 of M5, M8 from the NMOS of switch element 3, the grid of M6, M7 is connected to supply voltage V by series resistance R1
dd, the grid of M5, M8 is connected to supply voltage V by series resistance R2
dd, the drain electrode of NMOS pipe M5, M7 is connected, and is connected to the drain electrode of the PMOS pipe M9 of load unit 4, and the drain electrode of NMOS pipe M6, M8 is connected, and is connected to the drain electrode of the PMOS pipe M10 of load unit 4.
The grid of the PMOS pipe M9 of load unit 4 is connected with the drain electrode of PMOS pipe M10, and the grid of PMOS pipe M10 is connected with the drain electrode of PMOS pipe M9, difference radio frequency output signal V
rf+, V
rf-respectively from the drain electrode output of M9, M10, L1, C1 are in parallel, and their end is connected to the source electrode of M9, and the other end is connected to supply voltage V
dd, L2, C2 are in parallel, and their end is connected to the source electrode of M10, and the other end is connected to supply voltage V
dd
Electric current injects source electrode and the supply voltage V of PMOS pipe M11, the M12 of unit 5
ddConnect, the grid of M11, M12 is connected to bias voltage V
b2The drain electrode of M11 is connected with the drain electrode of input transconductance cell NMOS pipe M3, the grid of NMOS pipe M4 and switch element NMOS pipe M5 is connected M6 with NMOS source electrode, and the drain electrode of M12 is connected with the drain electrode of input transconductance cell NMOS pipe M4, the grid of NMOS pipe M3 and switch element NMOS pipe M7 is connected M8 with NMOS source electrode.
Difference base band or intermediate-freuqncy signal V
in+, V
in-from the source electrode input of NMOS mutual conductance pipe M3, the M4 of input transconductance cell 2, its input impedance is about 1/ (g
m+ g
mb), from mutual conductance tube grid input, for low frequency signal, the input impedance of NMOS tube grid is a very large value to traditional gilbert's amplifier usually, and from the input impedance 1/ (g of source electrode input
m+ g
mb) be much smaller comparatively speaking, can be better with 50 ohm of source impedances or the less output impedance of front stage circuits coupling, reduced the noise factor of upper frequency mixer.
Input signal V
in+ with V
in-be a pair of differential signal, establish V
in+=V, V
inThe V of-=-, the mutual conductance of NMOS mutual conductance pipe M3, M4 is g
m, mutual conductance pipe output load impedance is R.Positive input signal V
in+ convert electric current (g to by mutual conductance pipe M3
mV) by the drain electrode output of M3, the voltage in drain electrode is g
mVR, this voltage feed back to the grid of NMOS pipe M4 simultaneously, have strengthened the signal voltage between the grid source electrode of M4, thereby have increased the equivalent transconductance of mutual conductance pipe M4.In like manner, for mutual conductance pipe M3, above derivation is also set up.Therefore, this intersects positive feedback structure, can effectively improve the equivalent transconductance of input trsanscondutance amplifier, thereby improves the gain of frequency mixer.The introducing of this intersection positive feedback structure, the while has also been introduced the possibility of circuit oscillation.This intersection positive feedback structure can be regarded as a negative resistance, as long as regulate positive resistance in parallel with it, to offset this negative resistance, just can prevent circuit oscillation.In the present invention, as long as regulate the size of NMOS pipe M5, M6, M7, M8, make the input impedance of switch element 3 less than the absolute value of the negative resistance of this positive feedback generation, just can avoid circuit oscillation.
The impedance that the impedance that the load impedance of load unit 4 is produced by parallel resonance by inductance L 1, capacitor C 1 and inductance L 2, capacitor C 2 and PMOS pipe M9 and PMOS pipe M10 produce is in series.The load impedance that is produced by inductance capacitance has the frequency-selecting function, can be according to different frequency range should be used for regulating this inductance capacitance.The introducing of PMOS pipe M9 and PMOS pipe M10, on the one hand, connecting with the LC resonant tank has directly increased the load impedance of frequency mixer; On the other hand, M9 and M10 connect into the positive feedback form, have increased output signal, thereby improve the gain of upper frequency mixer.
Electric current injects unit 5 and uses 2 PMOS pipe M11 and M12, by regulating the biasing of its grid, control their electric current of flowing through, their practical significance is the size of current of controlling flow through switch element 3 and load unit 4, because upper frequency mixer circuit total current is determined by current source cell 1, in case set current source cell 1, the circuit total current is exactly a definite value.Increased the electric current that the electric current of flowing through injects unit 5, the electric current of must reduce to flow through switch element 3 and load unit 4.Inject unit 5 shunt currents can reduce the to flow through electric current of switch element 3 by electric current, just reduced the noise of this part generation, the most important thing is, controlled the electric current of the load unit of flowing through, just can control load the intensity of positive feedback in unit 4, the adjusting of injecting the unit by electric current can obtain a suitable positive feedback big or small, mixer load can be strengthened on the one hand, circuit oscillation can be prevented again on the other hand.
Referring to Fig. 4 as seen, under identical power consumption, the voltage gain curve of the utility model and load enhancing technology+current injection, mutual conductance positive feedback technique+current injection, traditional gilbert mixer compares, and its result shows that the gain of the upper frequency mixer that the utility model designs is the highest.
Referring to Fig. 5 as seen, under identical power consumption, the noise factor curve of the utility model and load enhancing technology+current injection, mutual conductance positive feedback technique+current injection, traditional gilbert mixer compares, and its result shows that the noise of the upper frequency mixer that the utility model designs is minimum.
Although the simulation result that provides in the utility model is the 2.4-2.5GHz frequency range, by adjusting component parameters of the present utility model, the utility model is equally applicable to other frequency ranges.
The utility model structure also can realize with bipolar transistor except realizing with field effect transistor.When realizing with bipolar transistor, only the NMOS pipe need to be replaced to NPN type triode, the PMOS pipe replaces to the positive-negative-positive triode and gets final product.Specific embodiments as shown in Figure 6.
Claims (2)
1. the upper frequency mixer of a low-power consumption high-gain, it is characterized in that: be provided with current source cell, the input transconductance cell, switch element, load unit and electric current inject the unit, the output of current source cell connects the input transconductance cell, input transconductance cell amplifying signal also strengthens signal by positive feedback, then export respectively switch element and electric current to and inject the unit, the output of switch element connects load unit, difference radio frequency output signal is exported between load unit and switch element, difference base band or intermediate-freuqncy signal input between input transconductance cell and current source cell, the local oscillator input signal inputs to switch element, wherein:
Current source cell comprises NMOS pipe M1 and NMOS pipe M2, the source ground of NMOS pipe M1 and NMOS pipe M2, and grid connects bias voltage V
b1, drain electrode connects the positive and negative two ends that connect respectively difference base band or intermediate-freuqncy signal;
The input transconductance cell comprises NMOS pipe M3 and NMOS pipe M4, NMOS pipe M3 be connected M4 with NMOS source electrode is managed with the NMOS of current source cell M1 is connected M2 with NMOS drain electrode respectively and is connected, the positive input terminal of base band or intermediate-freuqncy signal is from the source electrode input of NMOS pipe M3, the negative input end of base band or intermediate-freuqncy signal is from the source electrode input of NMOS pipe M4, the grid of NMOS pipe M3 is connected to the drain electrode of NMOS pipe M4, and the grid of NMOS pipe M4 is connected to the drain electrode of NMOS pipe M3;
Switch element comprises NMOS pipe M5, NMOS pipe M6, NMOS pipe M7, NMOS pipe M8, resistance R 1, resistance R 2, and NMOS pipe M5 is connected the gate interconnection of M8 and connects supply voltage V by series resistance R2 with NMOS
dd, NMOS pipe M6 is connected the gate interconnection of M7 and connects supply voltage V by series resistance R1 with NMOS
ddNMOS pipe M5 is connected M6 with NMOS source electrode interconnects and connects the drain electrode that the NMOS that inputs transconductance cell manages M3, NMOS pipe M7 is connected M8 with NMOS source electrode interconnects and connects the drain electrode that the NMOS that inputs transconductance cell manages M4, the drain electrode interconnection of the drain electrode of NMOS pipe M5 and NMOS pipe M7, the drain electrode interconnection of the drain electrode of NMOS pipe M6 and NMOS pipe M8, local oscillator input signal anode connects the grid of NMOS pipe M5 and NMOS pipe M8, and local oscillator input signal negative terminal connects the grid of NMOS pipe M6 and NMOS pipe M7;
Load unit comprises PMOS pipe M9, PMOS pipe M10, inductance L 1, capacitor C 1, inductance L 2, capacitor C 2, the drain electrode of PMOS pipe M9 and the NMOS of switch element manage that M5 is connected M7 with NMOS drain electrode is connected and as the signal positive output end of upper frequency mixer, the drain electrode of PMOS pipe M10 and the NMOS of switch element manage that M6 is connected M8 with NMOS drain electrode is connected and as the signal negative output terminal of upper frequency mixer, the grid of PMOS pipe M9 connects the drain electrode of PMOS pipe M10, the grid of PMOS pipe M10 connects the drain electrode of PMOS pipe M9, inductance L 1 is in parallel with capacitor C 1, their end and supply voltage V
ddConnect, the other end is connected with the source electrode of PMOS pipe M9, and inductance L 2 is in parallel with capacitor C 2, their end and supply voltage V
ddConnect, the other end is connected with the source electrode of PMOS pipe M10;
Electric current injects the unit and comprises PMOS pipe M11 and PMOS pipe M12, and the grid of PMOS pipe M11 and PMOS pipe M12 is connected to bias voltage V
b2The drain electrode of PMOS pipe M11 is connected with the drain electrode of input transconductance cell NMOS pipe M3, the grid of NMOS pipe M4 and switch element NMOS pipe M5 is connected M6 with NMOS source electrode, the drain electrode of PMOS pipe M12 is connected with the drain electrode of input transconductance cell NMOS pipe M4, the grid of NMOS pipe M3 and switch element NMOS pipe M7 is connected M8 with NMOS source electrode, source electrode and the supply voltage V of PMOS pipe M11 and PMOS pipe M12
ddConnect.
2. the upper frequency mixer of low-power consumption high-gain according to claim 1, the field effect transistor in circuit can realize by enough bipolar transistors, and only the NMOS pipe need to be replaced to NPN type triode, the PMOS pipe replaces to the positive-negative-positive triode.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 201320031759 CN203278746U (en) | 2013-01-18 | 2013-01-18 | Low power consumption and high gain upper mixer |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 201320031759 CN203278746U (en) | 2013-01-18 | 2013-01-18 | Low power consumption and high gain upper mixer |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN203278746U true CN203278746U (en) | 2013-11-06 |
Family
ID=49509068
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN 201320031759 Withdrawn - After Issue CN203278746U (en) | 2013-01-18 | 2013-01-18 | Low power consumption and high gain upper mixer |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN203278746U (en) |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103117707A (en) * | 2013-01-18 | 2013-05-22 | 东南大学 | Lower power consumption high gain upper mixer |
| CN106921346A (en) * | 2017-03-01 | 2017-07-04 | 成都通量科技有限公司 | High linearity wide band upper frequency mixer |
-
2013
- 2013-01-18 CN CN 201320031759 patent/CN203278746U/en not_active Withdrawn - After Issue
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103117707A (en) * | 2013-01-18 | 2013-05-22 | 东南大学 | Lower power consumption high gain upper mixer |
| CN103117707B (en) * | 2013-01-18 | 2015-05-06 | 东南大学 | Lower power consumption high gain upper mixer |
| CN106921346A (en) * | 2017-03-01 | 2017-07-04 | 成都通量科技有限公司 | High linearity wide band upper frequency mixer |
| CN106921346B (en) * | 2017-03-01 | 2020-11-24 | 成都通量科技有限公司 | High linearity broadband up-mixer |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN102868377B (en) | Total 3G (Third Generation Telecommunication) CMOS (Complementary Metal-Oxide-Semiconductor Transistor) differential low-noise amplifier based on controllable active inductor | |
| CN102082579B (en) | Ultralow-power consumption constant-envelope transceiver system and implementation method thereof | |
| CN106385240B (en) | A kind of RF front-end circuit that gain is continuously adjustable | |
| CN107276548A (en) | A kind of NEXT series of products CMOS automatic gain control circuits | |
| CN103236821B (en) | A kind of multimode multi-channel mixer based on adjustable negative resistance structure | |
| CN100539395C (en) | A kind of CMOS inductance capacitance resonant cavity voltage controlled oscillator of extra low voltage | |
| CN103117707B (en) | Lower power consumption high gain upper mixer | |
| CN106921346A (en) | High linearity wide band upper frequency mixer | |
| CN106301240A (en) | A kind of trans-impedance amplifier | |
| CN104883135A (en) | Resistance-feedback noise-cancelling broadband low-nose transconductance amplifier | |
| Walling et al. | A g m-Boosted Current-Reuse LNA in 0.18 μm CMOS | |
| CN109873625A (en) | A kind of active switch structure suitable for millimeter wave phased array system | |
| CN104124923B (en) | A kind of low-noise mixer circuit | |
| CN103762947A (en) | Cross-coupling input low-noise trans-conductance amplifier | |
| CN203278746U (en) | Low power consumption and high gain upper mixer | |
| CN103269233B (en) | Receiving and transmitting integrated multifunctional circuit | |
| CN202772848U (en) | Fully third generation telecommunication (3G) complementary metal oxide semiconductor (CMOS) difference low noise amplifier based on controllable active inductor | |
| Lee et al. | Gbps 60ghz cmos ook modulator and demodulator | |
| CN102130654A (en) | Integrated circuit chip of dual frequency band reconfigurable frequency mixer | |
| CN106505901B (en) | A kind of linear-resonance combined type hyperfrequency inverter | |
| CN203278747U (en) | Low-consumption high-gain down-conversion mixer | |
| CN104104336A (en) | Broadband radio frequency front end circuit with noise cancellation capability and low power consumption | |
| CN204013484U (en) | A kind of novel low-voltage frequency divider | |
| CN207304487U (en) | A kind of super low-power consumption up-conversion mixer | |
| CN103117708A (en) | Low-consumption high-gain down-conversion mixer |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant | ||
| AV01 | Patent right actively abandoned |
Granted publication date: 20131106 Effective date of abandoning: 20150506 |
|
| RGAV | Abandon patent right to avoid regrant |