CN203086362U - Switching power supply and controller thereof - Google Patents
Switching power supply and controller thereof Download PDFInfo
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- CN203086362U CN203086362U CN 201320047818 CN201320047818U CN203086362U CN 203086362 U CN203086362 U CN 203086362U CN 201320047818 CN201320047818 CN 201320047818 CN 201320047818 U CN201320047818 U CN 201320047818U CN 203086362 U CN203086362 U CN 203086362U
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Abstract
The utility model provides a switching power supply and a controller thereof. The controller is composed of a constant-current/constant-voltage control module, a segment control error amplifier, and a PWM generator. Specifically, the constant-current/constant-voltage control module detects an output constant-current value/output constant-voltage value of a switching power supply and converts the output constant-current value/output constant-voltage value into an equivalent value; the segment control error amplifier that is connected with the constant-current/constant-voltage control module carries out error amplification on the equivalent value and a preset reference value, wherein the transconductance or amplification factor of the segment control error amplifier is reduced gradually in continuous two or more periods of time after the starting of the circuit; and the PWM generator that is connected with the output terminal of segment control error amplifier determines a duty ratio of a driving signal according the output signal of the segment control error amplifier, wherein the driving signal is used for driving a power tube of the switching power supply. According to the utility model, the rapid starting of the circuit can be realized on the premise that the power supply time of the VCC capacitor is not increased; the overshooting of the output voltage/current can be prevented; and the stable work of the circuit is not influenced.
Description
Technical field
The utility model relates to switch power technology, relates in particular to a kind of Switching Power Supply and controller thereof of quick startup.
Background technology
Fig. 1 shows traditional inverse-excitation type single-stage LED driving power that has trsanscondutance amplifier, comprise: input rectifying bridge 101, alternating current source 102, input filter capacitor 103, starting resistance 104, VCC electric capacity 105, anti-violent change depressor T, output rectifier diode 107, output capacitance 114, output light emitting diode 112, power tube 109, sampling resistor Rs, auxiliary winding power-supply rectifying diode 111, and controller 120.
Wherein anti-violent change depressor T comprises former limit winding 106, secondary winding 110, auxiliary winding 108.
Wherein, the feeder ear of controller 120 is port VCC.The start-up course of circuit is as follows: charged through 104 pairs of VCC electric capacity of starting resistance 105 by input voltage vin earlier, by 120 power supplies of 105 pairs of controllers of electric capacity.The signal waveform of VCC electric capacity 105 charging and discharging processes as shown in Figure 2, the cut-in voltage V2 of controller 120 and close and have difference V2-V1, i.e. hysteresis voltage between the voltage V1.In input voltage vin by starting resistance 104 with the voltage charging at VCC electric capacity 105 two ends during to cut-in voltage V2, controller 120 is started working.Begin to consume the electric charge on the VCC electric capacity 105 after controller 120 work, make the voltage of VCC electric capacity 105 reduce, begin simultaneously to transmit energy to output.
If VCC electric capacity 105 be reduced to close voltage V1 before, output voltage is set up, and give VCC electric capacity 105 power supplies by the anti-sharp voltage of auxiliary winding 108 generations, then the voltage of VCC electric capacity 105 can remain on and close on the voltage V1, make circuit normally start and operate as normal.If the voltage drop of VCC electric capacity 105 be low to moderate close voltage V1 before, output voltage is not also set up, then can't produce anti-sharp voltage by auxiliary winding 108 gives VCC electric capacity 105 power supplies, cause the voltage of VCC electric capacity 105 to be reduced to less than closing voltage V1 always, controller 120 quits work, then input voltage vin will be again by 105 chargings of 104 pairs of VCC electric capacity of starting resistance, repeat above process, may cause the situation of controller 120 like this through repeatedly starting or can not start all the time repeatedly.
Whether controller 120 can normally start, relevant with the charging charge of VCC electric capacity 105, and also the power consumption with controller 120 is relevant with hysteresis voltage (cut-in voltage V2 and the difference of closing voltage V1).The capacitance of supposing VCC electric capacity 105 is C1, and the power consumption electric current of controller 120 is I1, if, can be to the power-on time t1 of controller 120 then fully by 105 power supplies of VCC electric capacity:
Within power-on time t1, if output can be set up, instead swashing voltage just can be to 105 power supply of VCC electric capacity, and circuit also just can disposablely start; Otherwise circuit can not disposablely start.
Usually, if power-on time t1 long enough just can guarantee the normal startup of circuit.For the power-on time t1 that extends, need to strengthen the capacitance C1 of VCC electric capacity 105, or strengthen hysteresis voltage V2-V1, or reduce the power consumption electric current I 1 of controller 120.VCC electric capacity 105 strengthens, and can cause the charging interval of 104 pairs of electric capacity 105 of starting resistance elongated, causes start-up time elongated, and in order to reduce start-up time, then need starting resistance 104 is reduced, this can cause the power consumption on the starting resistance 104 to become big again, influences system effectiveness.On the other hand, hysteresis voltage V2-V1 can't increase to very big, this be by controller 120 can operate as normal the power supply voltage range decision; The power consumption electric current I 1 that reduces controller 120 also is a kind of comparatively feasible method, but under the very little situation of the power consumption of controller 120, further reduces power consumption electric power I1 and just become very difficult.
If the power-on time that do not extend t1 then in order to accelerate start-up course, generally can adopt the mode of initial raising output energy, can set up output voltage fast like this, shorten needed output voltage settling time.But this mode can be brought negative interaction, particularly when input voltage is higher, is easy to generate the problem of output current, output voltage overshoot, influences the safety of circuit.
Still turn back to foregoing problems, as long as before output voltage is set up, the voltage of VCC electric capacity 105 is not reduced to closes voltage V1, and then circuit can one-shot.Generally speaking, output voltage or electric current are that example illustrates with the controller that has the power factor adjustment by loop control below, but its result also is applicable to the switch power controller of other band road controls.
Still with reference to figure 1, in the circuit that the power factor of band road control is adjusted, need set up stable loop fast.Usually, in order to improve the speed of response, generally require the capacitance of building-out capacitor 113 less; And, then need the capacitance of building-out capacitor 113 bigger again for the function of power factor adjustment is preferably arranged, with the impulse waveform behind the filtering input rectifying, but this can reduce loop response speed again.Therefore, the two is conflicting, is difficult to accomplish both taking into account.
If adopt bigger building-out capacitor 113, because loop control response is slower, when the voltage of input voltage vin changes, different situations can take place.When input voltage vin was low, because it is less to start initial output energy, loop response was slower, start very slowly, start 105 discharges of back VCC electric capacity, VCC electric capacity 105 discharges into when closing voltage V1, if output voltage is not also set up, then appearance can't one-shot easily, causes poor starting.And when input voltage vin was higher, because initial output energy is more, loop response was slower, and output voltage generation overshoot when causing starting easily influences the fail safe of circuit.On the other hand, if adopt less building-out capacitor 113, though the process of setting up of loop can accelerate to start the time, operate as normal can cause power factor lower later on again, and the bad stability of circuit.
Therefore, need a kind of new solution to accelerate the circuit start process, and don't influence other performance parameters such as power consumption, circuit stability.
The utility model content
The technical problems to be solved in the utility model provides a kind of Switching Power Supply and controller thereof, can under the prerequisite of VCC capacitances to supply power time that do not extend, realize the quick startup of circuit, prevent the output voltage generating process, and the characteristic when not influencing the circuit steady operation.
For solving the problems of the technologies described above, the utility model provides a kind of switch power controller, comprising:
The constant current/constant voltage control module, the output constant current value of sense switch power supply/output constant voltage value is converted to equivalence value with described output constant current value/output constant voltage value;
Segmentation departure amplifier, link to each other with described constant current/constant voltage control module, described equivalence value and preset reference value are carried out the error amplification, and the mutual conductance of described segmentation departure amplifier or multiplication factor two or more continuous time periods behind circuit start reduce successively;
PWM generator links to each other with the output of described segmentation departure amplifier, and determines the duty ratio of drive signal according to the output signal of described segmentation departure amplifier, and described drive signal is used to drive the power tube of described Switching Power Supply.
According to an embodiment of the present utility model, described segmentation departure amplifier comprises:
Start time block, begin timing during circuit start and produce timing signal;
The transconductance type error amplifier, link to each other with described constant current/constant voltage control module, described equivalence value and preset reference value are carried out the error amplification and convert error current to, and the output of described transconductance type error amplifier links to each other with described PWM generator as the output of described segmentation departure amplifier;
Mutual conductance segmentation control module links to each other with the transconductance type error amplifier with described startup time block, regulates the mutual conductance of described transconductance type error amplifier according to described timing signal.
According to an embodiment of the present utility model, described transconductance type error amplifier comprises:
First triode, its base stage receives described equivalence value, and its emitter connects reference current source via first resistance;
Second triode, its base stage receives described preset reference value, and its emitter connects described reference current source via second resistance;
First mirror current source, its input connects the collector electrode of described first triode;
Second mirror current source, its input connects the collector electrode of described second triode;
The 3rd mirror current source, its input connects the output of described first mirror current source, and its output connects the output of described second mirror current source and as the output of described transconductance type error amplifier.
According to an embodiment of the present utility model, the current mirror that described mutual conductance segmentation control module is regulated described first mirror current source, second mirror current source, the 3rd mirror current source according to described timing signal than and/or the resistance value of described first resistance, second resistance, to regulate the mutual conductance of described transconductance type error amplifier.
According to an embodiment of the present utility model, described segmentation departure amplifier comprises:
Start time block, begin timing during circuit start and produce timing signal;
The voltage-type error amplifier, link to each other with described constant current/constant voltage control module, described equivalence value and preset reference value are carried out the error amplification, and the output of described voltage-type error amplifier links to each other with described PWM generator as the output of described segmentation departure amplifier;
Multiplication factor segmentation control module links to each other with the voltage-type error amplifier with described startup time block, regulates the multiplication factor of described voltage-type error amplifier according to described timing signal.
The utility model also provides a kind of Switching Power Supply, comprises above any described switch power controller.
According to an embodiment of the present utility model, described Switching Power Supply is inverse-excitation type switch power-supply, positive activation type Switching Power Supply, step down switching regulator, boosted switch power supply or buck Switching Power Supply.
Compared with prior art, the utlity model has following advantage:
In the switch power controller of the utility model embodiment, the mutual conductance of segmentation departure amplifier or the multiplication factor two or more continuous time period behind circuit start reduces successively, also time period mutual conductance or the multiplication factor that has promptly just started at circuit is bigger, make that loop response speed is very fast, help setting up fast stablizing loop, accelerate toggle speed, prevent poor starting when input voltage is low; And in the follow-up time period, mutual conductance or multiplication factor reduce gradually, are reduced to conventional normal mutual conductance or multiplication factor after starting, and prevent to take place when input voltage is higher the output overshoot.Therefore, adopt the switch power controller of the utility model embodiment, overshoot can not take place again in the quick startup in the time of can either realizing low input when high input voltage.
Description of drawings
Fig. 1 is a kind of electrical block diagram that has the inverse-excitation type single-stage led drive circuit of trsanscondutance amplifier in the prior art;
Fig. 2 is the working waveform figure of led drive circuit shown in Figure 1;
Fig. 3 is the electrical block diagram of the Switching Power Supply of the utility model first embodiment;
Fig. 4 is the detailed circuit diagram of the transconductance type error amplifier of the utility model embodiment;
Fig. 5 is the electrical block diagram of the Switching Power Supply of the utility model second embodiment;
Fig. 6 is the electrical block diagram of the Switching Power Supply of the utility model the 3rd embodiment.
Embodiment
The utility model is described in further detail below in conjunction with specific embodiments and the drawings, but should not limit protection range of the present utility model with this.
With reference to figure 3, Fig. 3 shows the circuit structure of the inverse-excitation type switch power-supply of first embodiment, and what it adopted is the constant current control loop.This Switching Power Supply comprises: input rectifying bridge 101, alternating current source 102, input filter capacitor 103, starting resistance 104, VCC electric capacity 105, anti-violent change depressor T(comprise former limit winding 106, secondary winding 110 and auxiliary winding 108), output rectifier diode 107, output capacitance 114, power tube 109, sampling resistor Rs, output light emitting diode 112, output winding power-supply rectifying diode 111, controller 130.Wherein, the ordinary tap power supply of describing in the connected mode of the miscellaneous part except that controller 130 and operation principle and the background technology is identical.
Wherein, controller 130 comprises: constant current control module 121, segmentation departure amplifier 132, PWM generator 123.
Wherein, the output constant current value of constant current control module 121 sense switch power supplys should be exported constant current value and be converted to equivalence value Va.Furthermore, constant current control module 121 detects the output constant current value of Switching Power Supply according to the feedback signal FB that the voltage on the sampling resistor Rs and auxiliary winding 108 produces, and should export constant current value calculating and be converted to equivalence value Va.
Wherein, the control of the mutual conductance of 134 pairs of transconductance type error amplifiers 135 of mutual conductance segmentation control module can be two sections controls, also can be multistage control.Be controlled to be example with two sections, the very first time section behind circuit start, 134 mutual conductances with transconductance type error amplifier 135 of mutual conductance segmentation control module are adjusted to the response time that bigger, bigger mutual conductance helps shortening loop, accelerate start-up course; And in second time period after following very first time section closely, mutual conductance segmentation control module 134 turns the mutual conductance of transconductance type error amplifier 135 to default normal mutual conductance down, makes the circuit operate as normal.For two sections controls and multistage control, wherein the duration of each time period is arbitrarily, can set according to the demand of practical application.
Adopt segmentation departure amplifier 132, strengthen mutual conductance by the initial time section after startup, make the startup stage loop response speed improve, help setting up fast loop, prevent to give birth to the output overshoot and than poor starting under the low input issuing than high input voltage; Follow-up time section after startup, mutual conductance is reduced to normal mutual conductance gradually.Adopt this scheme, can either be implemented in, can not issue living overshoot than high input voltage again than the quick startup under the low input.
With reference to figure 4, Fig. 4 shows the detailed circuit of transconductance type error amplifier in the present embodiment, comprising: the first triode Q
1, its base stage receives equivalence value Va, and its emitter connects reference current source I via first resistance R 1
0The second triode Q
2, its base stage receives preset reference value V
Ref1, its emitter connects reference current source I via second resistance R 2
0First mirror current source 41, its input connect the first triode Q
1Collector electrode; Second mirror current source 42, its input connect the second triode Q
2Collector electrode; The 3rd mirror current source 43, its input connects the output of first mirror current source 41, and its output connects the output of second mirror current source 42 and as the output of whole transconductance type error amplifier, output error electric current I comp.
As a nonrestrictive example, first mirror current source 41 comprises MOS transistor M
1With MOS transistor M
3, MOS transistor M
1And M
3Source electrode link to each other MOS transistor M
1And M
3Grid link to each other MOS transistor M
1Drain electrode connect the grid of self and connect the first triode Q
1Collector electrode.
Second mirror current source 42 comprises MOS transistor M
2With MOS transistor M
4, MOS transistor M
2And M
4Source electrode link to each other MOS transistor M
2And M
4Grid link to each other MOS transistor M
2Drain electrode connect the grid of self and connect the second triode Q
2Collector electrode.
The 3rd mirror current source 43 comprises MOS transistor M
5With MOS transistor M
6, MOS transistor M
5And M
6Source electrode link to each other MOS transistor M
5And M
6Grid link to each other MOS transistor M
5Drain electrode connect the grid of self and connect MOS transistor M
3Drain electrode, MOS transistor M
6Drain electrode connect MOS transistor M
4Drain electrode.
The image current of supposing second mirror current source 42 is than being K2, and the image current that first mirror current source 41 and the 3rd mirror current source 43 amount to then has: I than for K1
4=K
2I
2, I
6=K
1I
1, I wherein
1For flowing through the first triode Q
1Electric current, I
2For flowing through the second triode Q
2Electric current, therefore, offset current I
CompCan adopt following formula to calculate: I
Comp=I
4-I
6=K
2I
2-K
1I
1
The resistance value of first resistance R 1 is designated as R1, the resistance value of second resistance R 2 is designated as R2, the voltage of equivalence value Va is designated as Va.Usually can suppose K1=K2=K, R1=R2=R, reference current source I
0The electric current of output is enough big, guarantees that I1 and I2 greater than zero, then have following relation:
Be that mutual conductance Gm is:
By above formula as can be known, the size of mutual conductance absolute value is more relevant than K, resistance value R with current mirror.Therefore, can regulate mutual conductance by Control current image ratio K and resistance value R.In the initial time section that starts, current mirror than transferring big and/or resistance value R turns down, just can be improved the mutual conductance that starts the starting stage, thereby the corresponding speed of raising circuit adds the start-up course of fast-circuit.Reduce mutual conductance gradually in the follow-up time section, after starting end, return to normal mutual conductance, can guarantee operate as normal like this, can accelerate start-up course again.
Need to prove, more than first embodiment shown in Figure 3 be that example describes with the current loop, but it will be appreciated by those skilled in the art that for voltage loop, by regulating the multiplication factor of segmentation departure amplifier, also can realize quick startup.
Fig. 5 shows the circuit structure of the Switching Power Supply of second embodiment, and what it adopted is voltage loop, and the constant current control module is replaced with constant voltage control module 151, is used for the output constant voltage value of Switching Power Supply is converted to equivalence value Va.In addition, segmentation departure amplifier 132 changes to and comprises: start time block 133, begin timing during circuit start and produce timing signal; Voltage-type error amplifier 135 carries out the error amplification with equivalence value Va and preset reference value, and the output of this voltage-type error amplifier 135 links to each other with PWM generator 153 as the output of described segmentation departure amplifier 132; Multiplication factor segmentation control module 134, link to each other with voltage-type error amplifier 135 with this startup time block 133, multiplication factor according to described timing signal regulation voltage type error amplifier 135, initial time section multiplication factor behind circuit start is bigger, reduce the multiplication factor of voltage-type error amplifier 135 successively in follow-up one or more time periods, until being reduced to normal multiplication factor.In second embodiment shown in Figure 5, also comprise peak current limit module 154, its input links to each other with first end of sampling resistor Rs, be used to obtain the voltage at sampling resistor Rs two ends, its output links to each other with PWM generator 153, the Voltage Feedback at the sampling resistor Rs two ends that obtain to PWM generator 153, is flow through the electric current of sampling resistor Rs with restriction.The circuit structure of other parts is identical with first embodiment shown in Figure 3 among second embodiment, repeats no more here.
In addition, though first embodiment shown in Figure 3 and second embodiment shown in Figure 5 are that example describes with the inverse-excitation type switch power-supply, but those skilled in the art are to be understood that, switch power controller in the present embodiment goes for various types of Switching Power Supplies, for example positive activation type Switching Power Supply, step down switching regulator, boosted switch power supply or buck Switching Power Supply etc.For various Switching Power Supplies, can adopt the controller of present embodiment to accelerate the response speed of loop, add the process of setting up of fast-circuit, effectively prevent problems such as voltage overshoot in the start-up course and current over pulse.
With reference to figure 6, Fig. 6 shows the circuit structure of the Switching Power Supply of the 3rd embodiment, and it is specially step down switching regulator.Wherein, the structure of controller 130 is identical with controller 130 among first embodiment shown in Figure 3, and difference is that main circuit is the buck structure.In the 3rd embodiment, main circuit specifically comprises: input rectifying bridge 101, alternating current source 102, input filter capacitor 103, starting resistance 104, VCC electric capacity 105, transformer (comprising former limit winding 161 and auxiliary winding 163), diode 162, output capacitance 114, power tube 109, sampling resistor Rs, output light emitting diode 112, output winding power-supply rectifying diode 111, controller 130.
The main circuit that it will be appreciated by those skilled in the art that step down switching regulator shown in Figure 6 only is example, and this controller 130 still can be suitable for when main circuit was done suitable change, and also, controller 130 goes for various types of Switching Power Supplies.
In addition, present embodiment also provides a kind of method of accelerating the Switching Power Supply start-up course, comprises the steps:
Step 2 after startup is timed to default duration, returns to normal multiplication factor or mutual conductance with the multiplication factor or the mutual conductance of error amplifier, makes the circuit operate as normal, the circuit parameter when not influencing the stability of circuit and operate as normal.
Wherein, the multiplication factor that strengthens error amplifier in the step 1 is segmentation control, can be two sections controls or multistage control.
The utility model discloses to have and start the starting stage and strengthen the multiplication factor of error amplifier or mutual conductance to accelerate loop response speed, prevent the structure and the method for output current, output voltage generation overshoot, and describe embodiment of the present utility model and effect with reference to the accompanying drawings.It should be understood that; the foregoing description is just to explanation of the present utility model; rather than to restriction of the present utility model; any utility model that does not exceed in the utility model connotation scope is created; include but not limited to the trsanscondutance amplifier structure, start the change of timing mode local structure, to the replacement of the type or the model of components and parts; and the replacement of other unsubstantialities or modification, all fall within the utility model protection range.
Claims (7)
1. a switch power controller is characterized in that, comprising:
The constant current/constant voltage control module, the output constant current value of sense switch power supply/output constant voltage value is converted to equivalence value with described output constant current value/output constant voltage value;
Segmentation departure amplifier, link to each other with described constant current/constant voltage control module, described equivalence value and preset reference value are carried out the error amplification, and the mutual conductance of described segmentation departure amplifier or multiplication factor two or more continuous time periods behind circuit start reduce successively;
PWM generator links to each other with the output of described segmentation departure amplifier, and determines the duty ratio of drive signal according to the output signal of described segmentation departure amplifier, and described drive signal is used to drive the power tube of described Switching Power Supply.
2. switch power controller according to claim 1 is characterized in that, described segmentation departure amplifier comprises:
Start time block, begin timing during circuit start and produce timing signal;
The transconductance type error amplifier, link to each other with described constant current/constant voltage control module, described equivalence value and preset reference value are carried out the error amplification and convert error current to, and the output of described transconductance type error amplifier links to each other with described PWM generator as the output of described segmentation departure amplifier;
Mutual conductance segmentation control module links to each other with the transconductance type error amplifier with described startup time block, regulates the mutual conductance of described transconductance type error amplifier according to described timing signal.
3. switch power controller according to claim 2 is characterized in that, described transconductance type error amplifier comprises:
First triode, its base stage receives described equivalence value, and its emitter connects reference current source via first resistance;
Second triode, its base stage receives described preset reference value, and its emitter connects described reference current source via second resistance;
First mirror current source, its input connects the collector electrode of described first triode;
Second mirror current source, its input connects the collector electrode of described second triode;
The 3rd mirror current source, its input connects the output of described first mirror current source, and its output connects the output of described second mirror current source and as the output of described transconductance type error amplifier.
4. switch power controller according to claim 3, it is characterized in that, the current mirror that described mutual conductance segmentation control module is regulated described first mirror current source, second mirror current source, the 3rd mirror current source according to described timing signal than and/or the resistance value of described first resistance, second resistance, to regulate the mutual conductance of described transconductance type error amplifier.
5. switch power controller according to claim 1 is characterized in that, described segmentation departure amplifier comprises:
Start time block, begin timing during circuit start and produce timing signal;
The voltage-type error amplifier, link to each other with described constant current/constant voltage control module, described equivalence value and preset reference value are carried out the error amplification, and the output of described voltage-type error amplifier links to each other with described PWM generator as the output of described segmentation departure amplifier;
Multiplication factor segmentation control module links to each other with the voltage-type error amplifier with described startup time block, regulates the multiplication factor of described voltage-type error amplifier according to described timing signal.
6. a Switching Power Supply is characterized in that, comprises each described switch power controller in the claim 1 to 5.
7. Switching Power Supply according to claim 6 is characterized in that, described Switching Power Supply is inverse-excitation type switch power-supply, positive activation type Switching Power Supply, step down switching regulator, boosted switch power supply or buck Switching Power Supply.
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| CN 201320047818 CN203086362U (en) | 2013-01-25 | 2013-01-25 | Switching power supply and controller thereof |
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| CN 201320047818 CN203086362U (en) | 2013-01-25 | 2013-01-25 | Switching power supply and controller thereof |
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Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103051220A (en) * | 2013-01-25 | 2013-04-17 | 杭州士兰微电子股份有限公司 | Switching power supply and controller thereof |
| CN104242623A (en) * | 2014-09-05 | 2014-12-24 | 中南民族大学 | Quick start method and quick start control circuit of switching power supply |
| CN107786087A (en) * | 2016-08-26 | 2018-03-09 | 三星电子株式会社 | Switching regulator and its control circuit and control method |
| CN107947560A (en) * | 2017-12-15 | 2018-04-20 | 杰华特微电子（杭州）有限公司 | On-off circuit control circuit and on-off circuit |
-
2013
- 2013-01-25 CN CN 201320047818 patent/CN203086362U/en not_active Expired - Fee Related
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103051220A (en) * | 2013-01-25 | 2013-04-17 | 杭州士兰微电子股份有限公司 | Switching power supply and controller thereof |
| CN103051220B (en) * | 2013-01-25 | 2015-07-29 | 杭州士兰微电子股份有限公司 | Switching Power Supply and controller thereof |
| CN104242623A (en) * | 2014-09-05 | 2014-12-24 | 中南民族大学 | Quick start method and quick start control circuit of switching power supply |
| CN107786087A (en) * | 2016-08-26 | 2018-03-09 | 三星电子株式会社 | Switching regulator and its control circuit and control method |
| CN107947560A (en) * | 2017-12-15 | 2018-04-20 | 杰华特微电子（杭州）有限公司 | On-off circuit control circuit and on-off circuit |
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