CN107786087A - Switching regulator and its control circuit and control method - Google Patents
Switching regulator and its control circuit and control method Download PDFInfo
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- CN107786087A CN107786087A CN201710411381.6A CN201710411381A CN107786087A CN 107786087 A CN107786087 A CN 107786087A CN 201710411381 A CN201710411381 A CN 201710411381A CN 107786087 A CN107786087 A CN 107786087A
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/1566—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators with means for compensating against rapid load changes, e.g. with auxiliary current source, with dual mode control or with inductance variation
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/157—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators with digital control
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0009—Devices or circuits for detecting current in a converter
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
Disclose switching regulator and its control circuit and control method.A kind of control circuit in switching regulator, the switching regulator include：Inductor；On-off circuit, it is configured to respond to electric current of the control signal control by inductor；The control circuit, it is configured as receiving the feedback voltage of the output voltage of the switching regulator and receives the electric current by inductor as current sensing signal.The control circuit includes：First internal signal maker, it is configured as generating the first internal signal based on feedback voltage and reference voltage；Second internal signal maker, it is configured as generating the second internal signal based on current sensing signal so that the basic level of the second internal signal changes according to feedback voltage and reference voltage；And comparator, it is configured as based on the first internal signal and the second internal signal come output control signal.
Description
This application claims in Korea Spro 10-2016-0109552 for being submitted to Korean Intellectual Property Office on the 26th of August in 2016
The rights and interests of state's patent application, the disclosure of the korean patent application are hereby incorporated by reference in its entirety.
Technical field
Inventive concept is related to switching regulator (such as, the control circuit of switching regulator), and the control of switching regulator
Method processed.
Background technology
Switching regulator can refer to for by turning on/off its device from the equipment of input voltage generation output voltage.Open
The power supply for including such switching regulator can be referred to by closing mode power (SMPS).Switching regulator can provide power efficiency and various
Output voltage, and generate the supply voltage for the component in various systems.
The load of switching regulator can change over time.For example, in computing systems, it may be in response to the request increase of user
Power consumption is to handle bigger amount of calculation.Power consumption can be reduced to operate at low power modes by closing some components.
The content of the invention
It is required to supply switching regulator of the electric power but regardless of the change of load to load stabilization.
Inventive concept be provided for enhancing the switching regulator of transient response, the control circuit of switching regulator with
And the control method of switching regulator.
According to inventive concept, there is provided the control circuit in a kind of switching regulator.The switching regulator may include：Inductance
Device and control signal is configured to respond to control the on-off circuit of the electric current by inductor.The control circuit can by with
It is set to：The feedback voltage of the output voltage of the switching regulator is received, and receives the electric current by inductor as electric current
Sensing signal.The control circuit may include：First internal signal maker, it is configured as being based on feedback voltage and reference voltage
Generate the first internal signal；Second internal signal maker, it is configured as based on feedback voltage, reference voltage and current sense letter
Number generation the second internal signal；Comparator, it is configured as come output control believing based on the first internal signal and the second internal signal
Number.
According to another example embodiment of inventive concept, there is provided a kind of switching regulator.The switching regulator may include：
Inductor；Feedback signal generative circuit, it is configured as generating feedback voltage and base from the output voltage of the switching regulator
In the electric current generation current sensing signal by inductor；Control circuit, it is configured as believing based on feedback voltage and current sense
Number generate control signal；On-off circuit, control signal is configured to respond to control the electric current by inductor.The control
Circuit processed may include：First internal signal maker, it is configured as believing based on feedback voltage and the inside of reference voltage generation first
Number；Second internal signal maker, it is configured as generating in second based on feedback voltage, reference voltage and current sensing signal
Portion's signal；Comparator, it is configured as being based on the first internal signal and the second internal signal output control signal.
According to another example embodiment of inventive concept, there is provided a kind of method for controlling switch voltage-stablizer.The side
Method may include：Feedback voltage is generated from the output voltage of the switching regulator, and electricity is generated from by the electric current of inductor
Flow sensing signal；First internal signal is generated based on feedback voltage and reference voltage；Based on feedback voltage, reference voltage and electric current
Sensing signal generates the second internal signal；Based on the first internal signal and the second internal signal generation control signal.
At least another example embodiment provides a kind of switching regulator, including：Input node, it is configured as receiving inputting and bears
Carry electric current；Output node, it is configured as exporting output load current；Rectifier, it is connected between first node and section point；
On-off circuit, it is configured as based on input load electric current, clock signal and control signal generation pulse signal；And control electricity
Road.The control circuit includes：First internal signal maker, is configurable to generate the first internal signal；Second internal signal
Maker, it is configured as based on feedback voltage and reference voltage generation error signal, wherein, feedback voltage is based at output node
Output voltage, the second internal signal maker be configured as based on error signal and current sensing signal generation second inside believe
Number, wherein, current sensing signal is based on pulse signal and input load electric current；And output circuit, it is configured as being based on first
Internal signal and the second internal signal generate control signal.
Brief description of the drawings
According to following detailed description with the accompanying drawing, the example embodiment of inventive concept will be more clearly understood, wherein：
Fig. 1 is the circuit diagram for schematically showing the switching regulator according to example embodiment；
Fig. 2 is the circuit diagram for schematically showing current mode boost converter；
Fig. 3 is the diagram for the oscillogram for showing the signal in Fig. 2 current mode boost converter；
Fig. 4 A and Fig. 4 B are the diagrams of the example for the control circuit for showing Fig. 1 according to example embodiment；
Fig. 5 is the oscillogram for showing the signal in the switching regulator including control circuit according to example embodiment
Diagram；
Fig. 6 A and Fig. 6 B are the circuit diagrams for the example for schematically showing the summing circuit according to example embodiment；
Fig. 7 A and Fig. 7 B are the diagrams of the example for the control circuit for showing Fig. 1 according to example embodiment；
Fig. 8 A, Fig. 8 B and Fig. 8 C are the diagrams of the example for the control circuit for showing Fig. 1 according to example embodiment；
Fig. 9 A and Fig. 9 B are the diagrams for the result for showing the analog switch voltage-stablizer according to example embodiment；
Figure 10 A and Figure 10 B are to schematically show the switching regulator for including control circuit according to example embodiment
Circuit diagram；
Figure 11 and Figure 12 is to schematically show the switching regulator for including control circuit according to example embodiment
Circuit diagram；
Figure 13 is the flow chart for the control method for showing the switching regulator according to example embodiment；
Figure 14 is the flow chart for the example for showing the step S60 according to Figure 13 of example embodiment；
Figure 15 is the block diagram for showing the system including switching regulator according to example embodiment.
Embodiment
As used herein, when the expression of such as " ... at least one " is when after a column element, modification permutation member
Individual element in element rather than modification list.
Fig. 1 is the circuit diagram for schematically showing the switching regulator 10 according to example embodiment.Switching regulator 10 can
Including multiple devices and sub-circuit, and can be exported by lead-out terminal 12 from the power regulation provided by input terminal 11
Electric power.
As shown in fig. 1, can be direct current (DC)-DC converters according to the switching regulator 10 of example embodiment, and
Can be boost converter (or boost DC-DC converter).In other words, switching regulator 10 can be generated than input voltage V_
Output voltage V_OUT high IN.Switching regulator 10 can be widely used in various applications, such as, audio tweeter driver, just
Take formula mobile device, light emitting diode (LED) driver and liquid crystal display (LCD) biasing circuit.Hereinafter, referring especially to
Example embodiment is described as the switching regulator 10 of boost converter.However, it should be understood that the example embodiment of inventive concept
Not limited to this.
Boost converter (or dc-dc) can pass through the switching sequence (switch of feedback control loop adjusting apparatus
timing).For example, voltage mode control method (or the Duty ratio control side of one of control method as boost converter
Method) it may include a loop, and the change that may be in response to output voltage directly adjusts dutycycle.As boost converter
The Controlled in Current Mode and Based method (either current programming mode control method or current injection control method) of one of control method
Can be include two loops (that is, inner current loops (for example, in Fig. 2 pass through current sensing signal CS ' and summing circuit
320 ' loop) and external voltage loop (for example, loop of the process feedback voltage V _ FB ' and amplifier 310 ' in Fig. 2))
Multi-loop control method.Fixed frequency peak-current mode control method as one of Controlled in Current Mode and Based method can be used solid
Determine slope-compensation ramp signal.In fixed frequency peak-current mode control method, inductor current (example can be directly controlled
Such as, Fig. 2 I_L '), and output voltage can be by current loop indirect control.In this manual, description is based on current-mode
The boost converter of control method control.
Boost converter can be asked to supply electric power, but regardless of the change of load to its load stabilization.For example, referring to Fig. 1,
It can ask boost converter that the overshoot (overshoot) in output voltage V_OUT occurs when load current I_LOAD is changed
Or undershoot (undershoot) minimizes.However, due to RHP (RHP) zero point, boost converter may be by bandwidth
To limitation.Therefore, the response speed of change of the loop to load current I_LOAD can be restricted.In other words, step load
Electric current can cause high overshoot or high undershoot in output voltage V_OUT.As will be described below, opening according to example embodiment
Close voltage-stablizer 10, its control circuit 300 and its control method can be by by the change of switching frequency or electromagnetic interference (EMI)
Minimize or make to provide transient response while its zero change to reduce the overshoot or undershoot in output voltage V_OUT, but regardless of
Load current I_LOAD change (for example, generation of step load electric current).
Reference picture 1, switching regulator 10 may include rectifier 100, on-off circuit 200, control circuit 300 and multiple passive
Device L, C, RC, R1 and R2.Inductor L can have the one end for being connected to the input terminal 11 for receiving input voltage V_IN, and
There can be the other end for being connected to rectifier 100 and on-off circuit 200.On-off circuit 200 can be based on by inductor L electric current
Switching manipulation ground is flowed to by on-off circuit 200, and capacitor C and lead-out terminal 12 can be flowed to by rectifier 100.
Rectifier 100 can have the one end for being connected to inductor L and on-off circuit 200, and can have and be connected to electric capacity
Device C and lead-out terminal 12 other end.Rectifier 100 can prevent electric current from the node for being connected to capacitor C and lead-out terminal 12
Flow to inductor L or on-off circuit 200.
On-off circuit 200, which may be in response to clock signal clk and control signal CTRL, will be connected to inductor L and rectifier
100 node is connected to ground or disconnected.As shown in figure 1, on-off circuit 200 may include impulse generator 210 and switch 220.Arteries and veins
Pulse signal PS can be generated based on the clock signal clk of reception and the control signal CTRL of reception by rushing maker 210.For example,
Impulse generator 210 may be in response to the rising edge of clock signal clk or trailing edge carrys out sensitizing pulse signal PS, and may be in response to
The control signal CTRL of activation and deactivate (deactivate) pulse signal PS.Switch 220 may be in response to the pulse letter of activation
The node for being connected to inductor L and rectifier 100 is connected to ground and (that is, switchs 220 and can be at on-state) by number PS.Switch
The 220 pulse signal PS that may be in response to deactivate, which disconnect the node for being connected to inductor L and rectifier 100 with ground, (that is, to be switched
220 can be at off-state).In other words, switch 220 in an ON state interval can by pulse signal PS dutycycle Lai
It is determined that.
Under the on-state of switch 220, switch can be passed through by inductor L electric current (that is, inductor current I_L)
220 flow to ground.As being spaced in the cycle of clock signal clk in an ON state of switch 220 increases (that is, with pulse
Signal PS dutycycle increase), inductor current I_L level can increase.If switch 220 goes off state, increase
Inductor current I_L capacitor C and lead-out terminal 12 can be flowed to by rectifier 100.In other words, switching regulator 10 can
By adjusting the pulse signal PS via its feedback control loop on/off switch 220, to control output voltage V_OUT so that defeated
Go out voltage V_OUT and keep constant.
Feedback signal generative circuit 400 may include current sensor 420 and divider 410.Current sensor 420 can sense
By the electric current of switch 220, and generate current sensing signal CS.In other words, if switching 220 pulses in response to activation
Signal PS and in an ON state, then current sensing signal CS can have level corresponding with inductor current I_L level.Together
When, if switch is off in response to the pulse signal PS of deactivation, current sensing signal CS can have and zero
Corresponding level.Therefore, current sensing signal CS can have the form for oscillating to switching frequency.Divider 410 can provide feedback
Voltage V_FB.Feedback voltage V _ FB can be the voltage associated with output voltage V_OUT, and as shown in figure 1, can be defeated
Go out voltage V_OUT by resistor R1 and the voltage of resistor R2 partial pressures.
Control circuit 300 can receive feedback voltage V _ FB, reference voltage V_REF and current sensing signal CS.When output electricity
Pressure V_OUT is when it is expected the voltage of level, and reference voltage V_REF can be the level identical electricity of level and feedback voltage V _ FB
Pressure.Control circuit 300 can generate control signal CTRL based on the difference between feedback voltage V _ FB and reference voltage V_REF.
As shown in figure 1, control circuit 300 may include the first internal signal maker 310, the second internal signal maker
320 and comparator 330.First internal signal maker 310 can be based on feedback voltage V _ FB and reference voltage V_REF generations the
One internal signal INT1, the second internal signal maker 320 can be based on feedback voltage V _ FB, reference voltage V_REF and electric current sense
Survey signal CS and generate the second internal signal INT2.Comparator 330 can be by by the first internal signal INT1 and the second internal signal
INT2 is compared to generate control signal CTRL., can be from feedback voltage V _ FB as described in below by reference picture 4A and Fig. 4 B
Difference the first internal signal INT1 of generation between reference voltage V_REF, and can be from feedback voltage V _ FB and reference voltage V_
Difference and current sensing signal CS between REF generate the second internal signal INT2.
According to an example embodiment, because control circuit 300 is also based on feedback voltage V _ FB and reference voltage V_REF
(that is, the difference between feedback voltage V _ FB and reference voltage V_REF) and current sensing signal CS generate the second internal signal
INT2, therefore the transient response characteristic of switching regulator 10 can be improved.In other words, the second internal signal generator 320 can give birth to
Into the second internal signal INT2 so that switch 220 on-interval and increase when load current I_LOAD increases, and to open
The on-interval of pass 220 reduces when load current I_LOAD reduces.Therefore, switching regulator 10 can have the transient state improved to ring
Should, and output voltage V_OUT overshoot and undershoot can be reduced, the change but regardless of load current I_LOAD is (for example, step is born
Current-carrying generation).
Fig. 2 is the circuit diagram for schematically showing boost converter 10 '.Fig. 3 is shown in Fig. 2 boost converter 10 '
Signal oscillogram diagram.Reference picture 2, boost converter 10 ' can be the current-modes of the switching regulator 10 such as Fig. 1
Boost converter, and may include rectifier 100 ', on-off circuit 200 ', amplifier 310 ', summing circuit 320 ', comparator
330 ' and multiple passive device L, C, RC, R1 and R2.
Boost converter 10 ' may include the first loop and the second loop.First loop can be voltage loop, and can make
With the error voltage V_EA ' generated based on the difference between feedback voltage V _ FB ' and reference voltage V_REF '.In addition, the second loop
It can be current loop, and the electric current sense generated by sensing by the electric current of the switch 220 ' of on-off circuit 200 ' can be used
Survey signal CS ' and ramp signal RAMP ' sum CS '+RAMP '.Can be by comparator 330 ' by current sensing signal CS ' and slope
Signal RAMP ' sum CS '+RAMP ' are compared with error voltage V_EA '.Comparator 330 ' can generate corresponding with comparative result
Control signal CTRL '.
The ramp signal RAMP ' to be summed with current sensing signal CS ' can stablize the second loop (that is, current loop),
And noise immunity can be improved.It is if for example, by comparator 330 ' that current sensing signal CS ' and error voltage V_EA ' is straight
Connect and be compared, then in current loop by sub- harmonic oscillation be likely to occur switching frequency peak value (that is, with clock signal
Frequency corresponding to the half of CLK ' frequency).If however, as shown in Fig. 2 by level in switch periods (switching
Period) the saw-tooth ramp signal RAMP ' being increased during (that is, clock signal clk ' cycle) and current sensing signal CS '
Summed, then sub- harmonic oscillation can be died down due to compensation slope, and peak value can be suppressed.
As noted previously, as RHP (RHP) zero point, the responsibility of bandwidth and load current I_LOAD change is in Fig. 2
Boost converter 10 ' in can be limited.If for example, there is change (for example, in the event of step in load current I_LOAD '
Load current), then error voltage V_EA ' can be responded will be relatively slowly.Therefore, output voltage V_OUT ' can undergo high overshoot or high
Undershoot.The transient response of the boost converter 10 ' is described below with reference to Fig. 3 oscillogram.
Reference picture 3, with the power consumption increase of the load for the lead-out terminal 12 ' for being connected to boost converter 10 ', load current
I_LOAD ' can be gradually increasing from original levels I_1 '.Due to load current I_LOAD ' rising, output voltage V_OUT ' can be opened
Begin to decline.Therefore, error voltage V_EA ' can rise.With error voltage V_EA ' rise, Fig. 2 comparator 330 ' it is another defeated
The peak value (that is, current sensing signal CS ' and ramp signal RAMP ' sum CS '+RAMP ' peak value) entered can be higher and higher
Position is formed.Therefore, activation control signal CTRL ' time can gradually be postponed in switch periods, and pulse signal PS '
Dutycycle can increase.In response to the increased pulse signal PS ' of dutycycle, substantial amounts of electric current can be supplied by inductor L.Cause
This, output voltage V_OUT ' can rise again.
As shown in figure 3, the level V_UDS ' of undershoot in output voltage V_OUT ' can be with the electric current supplied by inductor L
Increased velocity correlation connection.In other words, if the electric current supplied by inductor L is not with load current I_LOAD ' increases
And increase, then the level V_UDS ' of the undershoot in output voltage V_OUT can increase.Therefore, because boost converter 10 ' is slow
Transient response output voltage V_OUT ' in high undershoot can cause load (that is, the Rreceive output voltage of boost converter 10 '
Each component in V_OUT ' component, for example, processor, storage device, modem, input/output (I/O) device etc.
In it is each) error operation.
Fig. 4 A and Fig. 4 B are the diagrams for the example for showing the control circuit 300 according to Fig. 1 of example embodiment.As joined above
According to described in Fig. 1, each in control circuit 300a and control circuit 300b can receive feedback voltage V _ FB, reference voltage V_
REF and current sensing signal CS, and exportable control signal CTRL.Hereinafter, Fig. 4 A control circuit 300a description
It is also applied for Fig. 4 B control circuit 300b.
Reference picture 4A, control circuit 300a may include the first internal signal maker 310a, the second internal signal maker
320a and comparator 330a.First internal signal maker 310a may include the first amplifier 311a.First amplifier 311a can
With the reversed input terminal for receiving feedback voltage V _ FB and reception reference voltage V_REF non-inverting input terminal.Therefore,
One internal signal maker 310a can be generated with the poor proportional electricity between reference voltage V_REF and feedback voltage V _ FB
The first flat internal signal INT1.
Second internal signal maker 320a may include the second amplifier 321a and summing circuit 322a.As shown in Figure 4 A,
Second amplifier 321a can have the reversed input terminal for receiving reference voltage V_REF and receive the noninverting of feedback voltage V _ FB
Input terminal.Therefore, the second amplifier 321a can generate between feedback voltage V _ FB and reference voltage V_REF difference into
The error signal ERR of the level of ratio.In other words, the first amplifier 311a as the first internal signal maker 310a
Output the first internal signal INT1 and as the second amplifier 321a output error signal ERR can based on feedback voltage V _
Between FB and reference voltage V_REF difference and there is different polarity.
According to an example embodiment, generate the first internal signal INT1 the first amplifier 311a and generate error signal
ERR the second amplifier 321a can have different characteristics.For example, the first internal signal maker 310a the first amplifier
311a can have a relatively high precision (for example, low input offset or high linearity), and the second internal signal maker 320a
Second amplifier 321a can have relatively fast responsiveness (for example, high bandwidth).
Second internal signal maker 320a summing circuit 322a may include the first summation sub-circuit 322a_1 and second
Sum sub-circuit 322a_2.First summation sub-circuit 322a_1 can be asked current sensing signal CS and offset signal BIAS
With.Second summation sub-circuit 322a_2 can be asked by the output to the first summation sub-circuit 322a_1 with error signal ERR
With generate the second internal signal INT2.Offset signal BIAS may move (for example, being raised and lowered) current sensing signal CS's
Basic level so that error signal ERR is reflected in the second internal signal INT2.Therefore, the second internal signal INT2 can be corresponded to
In such signal, the signal, which has, oscillates to the current sensing signal CS's based on the error signal ERR switching frequencies changed
Basic level.As shown in Figure 4 A, the first internal signal INT1 is provided to comparator 330a non-inverting input terminal, and second
Internal signal INT2 is provided to comparator 330a reversed input terminal.In other words, compared with the example shown in Fig. 2,
The corresponding error signal ERR of difference between feedback voltage V _ FB and reference voltage V_REF can be with the current sensing signal of biasing
CS is summed, and with described and corresponding second internal signal INT2 can be compared with the first internal signal INT1.Cause
This, Fig. 1 switching regulator 10 may also include the poor further loop of tracking feedback voltage V _ between FB and reference voltage V_REF
And the voltage loop according to feedback voltage V _ FB and the current loop according to current sensing signal CS.According to error signal ERR
Such further loop be referred to alternatively as quick cor-rection loop.Due to quick cor-rection loop, switching regulator is (for example, Fig. 1's opens
Close voltage-stablizer 10) there can be quick transient response relative to other switching regulators.
Reference picture 4B, control circuit 300b may include the first internal signal maker 310b, the second internal signal maker
320b and comparator 330b.Compared with Fig. 4 A control circuit 300a, Fig. 4 B control circuit 300b the second internal signal life
The 320b that grows up to be a useful person can also receive ramp signal RAMP in addition to current sensing signal CS.As described above with reference to Figure 2, ramp signal
RAMP can be the serrated signal risen during switch periods.Switching regulator (for example, Fig. 1 switching regulator 10) can be steady
Determine current loop, and can be by being summed ramp signal RAMP and current sensing signal CS to improve noise immunity.
Second internal signal maker 320b summing circuit 322b may include the first summation sub-circuit 322b_1 to the 3rd
Sum sub-circuit 322b_3.First summation sub-circuit 322b_1 can sum to ramp signal RAMP and offset signal BIAS.Second
Summation sub-circuit 322b_2 can sum to current sensing signal CS and the first summation sub-circuit 322b_1 output.In addition,
3rd summation sub-circuit 322b_3 can be summed by the output to the second summation sub-circuit 322b_2 and error signal ERR come
Generate the second internal signal INT2.In other words, compared with the example shown in Fig. 4 A, offset signal BIAS can be with ramp signal
RAMP is summed.Therefore, as described in below by reference picture 5, due to offset signal BIAS, current sensing signal CS and slope
The basic level of signal RAMP sums can be by the certain skew of movement.
According to an example embodiment, compared with the example shown in Fig. 4 B, the second internal signal maker may include to ask
And circuit, each summing circuit are summed to offset signal and current sensing signal CS and ramp signal RAMP respectively.In this feelings
Under condition, the skew of current sensing signal CS and ramp signal RAMP sums can be believed by the biasing summed with current sensing signal CS
Number and determined with the offset signal of ramp signal RAMP summation.
Fig. 5 is that the oscillogram for showing signal in the switching regulator including control circuit according to example embodiment is shown
Figure.In detail, Fig. 5 is shown if Fig. 1 switching regulator 10 includes Fig. 4 B control circuit 300b (if, utilized
Fig. 4 B control circuit 300b implements Fig. 1 control circuit 300) signal oscillogram diagram.In addition, in order to Fig. 2
Boost converter 10 ' be compared, Fig. 5 is the diagram for the waveform for showing the signal shown in Fig. 2.Hereinafter, by reference picture 1
Description is provided with Fig. 4 B.
Reference picture 5, with the power consumption increase of the load for the lead-out terminal 12 for being connected to switching regulator 10, load current I_
LOAD can be gradually increasing from original levels I_1.Under output voltage V_OUT can start due to load current I_LOAD rising
Drop.Therefore, the first internal signal INT1 can rise, and error signal ERR can change on the contrary with the first internal signal INT1.Change
Word says, second internal signal INT2's corresponding with current sensing signal CS, ramp signal RAMP and error signal ERR sums
Basic level can decline from initial offset.Therefore, as shown in figure 5, the second internal signal INT2 peak value can be in switch periods
Formed at the time of error voltage V_EA ' more long delays than Fig. 3.Pulse signal PS can have the pulse signal PS's ' than Fig. 3
Effective pulse width (that is, dutycycle) broader effective pulse width.
As shown in figure 5, the level V_UDS of the undershoot in output voltage V_OUT can be less than the level V_ of Fig. 3 undershoot
UDS’.In other words, the electric current supplied by inductor L can have increased dutycycle to increase due to pulse signal PS.It is defeated
Going out voltage V_OUT decline width can reduce.Therefore, switching regulator 10 can provide quick relative to other switching regulators
Transient response.
As shown in figure 5, in order to reflect the error signal ERR in the second internal signal INT2, the second internal signal INT2 can
With skew OFFSET.For example, current sensing signal CS basic level may include to offset OFFSET, or ramp signal RAMP
Basic level may include offset OFFSET.Can by the skew to including in current sensing signal CS basic level with
Summed in the skew that ramp signal RAMP basic level includes to form skew OFFSET.In addition, error signal ERR
It may include to offset OFFSET.As described in by reference picture 7A and Fig. 7 B, offset signal can further be summed.Offseting OFFSET can
With appropriate level so that current sensing signal CS, ramp signal RAMP and error signal ERR sums (or Fig. 4 A show
Current sensing signal CS and error signal ERR sums in example) in Fig. 4 B comparator 330b input range.
Fig. 5 shows the increase due to load current I_LOAD and the example of undershoot occurs in output voltage V_OUT.So
And, it should be appreciated that when the reduction due to load current I_LOAD overshoots in output voltage V_OUT, occur relatively low
The overshoot of level.In other words, as the lower power consumption of load, load current I_LOAD can reduce.Output voltage V_OUT can be by
Rise in the load current I_LOAD of reduction.First internal signal INT1 declines due to the output voltage V_OUT of rising, and
Error signal ERR can change on the contrary with the first internal signal INT1, and the second internal signal INT2 basic level can on
Rise (for example, skew OFFSET from Fig. 5).Therefore, the second internal signal INT2 peak value can be formed with the relatively short time,
And pulse signal PS can have the narrow effective pulse widths (that is, dutycycle) of the pulse signal PS ' than Fig. 3.As a result, output electricity
Pressure V_OUT can be reduced again due to the electric current of the reduction by inductor L in some time, and can be occurred relatively low-level
Overshoot.
Fig. 6 A and Fig. 6 B are the circuit diagrams for the example for schematically showing the summing circuit according to example embodiment.In detail
Say, Fig. 6 A show the circuit 6a for being summed to two or more voltages.Fig. 6 B show to be used for two or more
The circuit 6b that electric current is summed.It should be understood that the summing circuit 6b shown in summing circuit 6a and Fig. 6 B shown in Fig. 6 A is only
It is example, and the various summing circuits not shown in Fig. 6 A and Fig. 6 B can be used for the switching regulator according to example embodiment
In (or control circuit).The summing circuit 6b shown in summing circuit 6a and Fig. 6 B shown in Fig. 6 A can be carried out to three inputs
Summation.However, it should be understood that the summing circuit of modification can sum to two inputs or three or more inputs.
Each referring again to Fig. 4 A and Fig. 4 B, in summing circuit 322a and 322b input signal CS, RAMP and ERR
It may correspond to the electric current of level change and the voltage of level change.For example, current sensing signal CS can be the level of electric current
The signal of change, and can be level of the level of voltage based on the electric current of sensing and the signal that changes.Therefore, summing circuit
Each in 322a and summing circuit 322b can be that voltage summing circuit (for example, Fig. 6 A summing circuit 6a), electric current are asked
With circuit (for example, Fig. 6 B summing circuit 6b) or the shape based on input signal voltage/current summing circuit.
Reference picture 6A, voltage summing circuit 6a can be noninverting summing circuits, it may include operational amplifier X1 and multiple
Resistor R11 to R15, and voltage summing circuit 6a can be by using same or different weighted value to three input voltages
V1 to V3 is summed to generate output voltage V4.It can be determined by resistor R11 to R13 for input voltage V1 to V3's
Weighted value.In other words, following equation 1 can be used to determine output voltage V4.
[equation 1]
For example, if connected to resistor R11 to the R13 of operational amplifier X1 non-inverting input terminal value and connection
The value of resistor R14 between operational amplifier X1 reversed input terminal and ground is identical, and if feedback resistor R15
Two times of value with resistor R14 are (i.e.,), then output voltage V4 can be equal to input
Voltage V1 is to V3 sums (i.e. V4=V1+V2+V3).
Reference picture 6B, electric current summing circuit 6b can be noninverting summing circuits, it may include operational amplifier X2 and multiple
Resistor R21 to R24, and electric current summing circuit 6b can be by using identical or different weighted value to three input current I1
Summed to I3 to generate output current I4.Input current I1 to I3 weight can be determined by resistor R21 to R23
Value.In other words, following equation 2 can be used to determine output current I4.
[equation 2]
Fig. 7 A and Fig. 7 B are the diagrams for the example for showing the control circuit 300 according to Fig. 1 of example embodiment.In detail
Say, Fig. 7 A and Fig. 7 B show the control circuit 300c for including the second internal signal maker 320c and given birth to including the second internal signal
Grow up to be a useful person 320d control circuit 300d, and each second internal signal maker will offset OFFSET using offset signal BIAS respectively
It is added to the second internal signal INT2.As explained above with Fig. 4 A and Fig. 4 B descriptions, the second internal signal maker 320c and second
Each in internal signal maker 320d can give birth to from feedback signal V_FB, reference voltage V_REF and current sensing signal CS
Into the second internal signal INT2.
As shown in figures 7 a and 7b, control circuit 300c may include that the first internal signal maker 310c, the second inside believe
Number maker 320c and comparator 330c, control circuit 300d may include that the first internal signal maker 310d, the second inside believe
Number maker 320d and comparator 330d.First internal signal maker 310c and 310d can include the first amplifier 311c respectively
And 311d, each first amplifier export the first internal signal INT1.Second internal signal generator 320c may include that output misses
Difference signal ERR the second amplifier 321c and summing circuit 322c, the second internal signal generator 320d may include output error
Signal ERR the second amplifier 321d and summing circuit 322d.Hereinafter, Fig. 7 A control circuit 300c and Fig. 7 B control
In circuit 300d processed description, it will not provide by Fig. 4 A control circuit 300a and Fig. 4 B control circuit 300b description repetition
Description.
Reference picture 7A, according to an example embodiment, summing circuit 322c may include the first summation sub-circuit 322c_1 and
Second summation sub-circuit 322c_2.First summation sub-circuit 322c_1 can be asked error signal ERR and offset signal BIAS
With.Second summation sub-circuit 322c_2 can ask the first summation sub-circuit 322c_1 output with current sensing signal CS
With.As described with reference to Figure 5, the second internal signal INT2 can have skew OFFSET to reflect error signal ERR.Scheming
In 7A control circuit 300c, the second input signal INT2 can be formed by being used as the offset signal BIAS of direct current (DC) signal
Skew OFFSET at least a portion.Therefore, summing circuit 322c can be by entering to offset signal BIAS and error signal ERR
Row is summed to generate the second internal signal INT2.
Reference picture 7B, according to an example embodiment, summing circuit 322d may include the first summation sub-circuit 322d_1 extremely
3rd summation sub-circuit 322d_3.First summation sub-circuit 322d_1 can be carried out to current sensing signal CS and ramp signal RAMP
Summation.Second summation sub-circuit 322d_2 can ask the first summation sub-circuit 322d_1 output with offset signal BIAS
With.In addition, the 3rd summation sub-circuit 322d_3 can be entered by the output to the second summation sub-circuit 322d_2 with error signal ERR
Row is summed to generate the second internal signal INT2.As described in reference picture 2, ramp signal RAMP can be during switch periods
The serrated signal of rising.Switching regulator (for example, Fig. 1 switching regulator 10) can stabling current loop, and can be by right
Ramp signal RAMP and current sensing signal CS is summed to improve noise immunity.Therefore, summing circuit 322d can by
Carried out in the offset signal BIAS and current sensing signal CS and ramp signal RAMP sums of the second internal signal INT2 skew
Summation, to be summed to four signals CS, RAMP, ERR and BIAS.
Fig. 8 A to Fig. 8 C are the diagrams for the example for showing the control circuit 300 according to Fig. 1 of example embodiment.In detail
Say, Fig. 8 A to Fig. 8 C show the control circuit 300e, 300f for including second internal signal maker 320e, 320f and 320g respectively
And 300g, wherein, second internal signal maker 320e, 320f and 320g uses level shifter 322e_2,322f_3 respectively
Skew is added to the second internal signal INT2 with 323g.As described in reference picture 4A and Fig. 4 B, the second internal signal maker
Each in 320e, 320f and 320g can generate from feedback voltage V _ FB, reference voltage V_REF and current sensing signal CS
Second internal signal INT2.
As shown in Fig. 8 A to Fig. 8 C, control circuit 300e may include that the first internal signal maker 310e, the second inside believe
Number maker 320e and comparator 330e；Control circuit 300f may include that the first internal signal maker 310f, the second inside believe
Number maker 320f and comparator 330f；Control circuit 300g may include that the first internal signal maker 310g, the second inside believe
Number maker 320g and comparator 330g.First internal signal maker 310e to 310g, which can include the inside of output first respectively, to be believed
Number INT1 the first amplifier 311e to 311g.Second internal signal maker 320e to 320g, which can include output error respectively, to be believed
Number ERR the second amplifier 321e is carried out to 321g and to current sensing signal CS, ramp signal RAMP and error signal ERR
The summing circuit 322e to 322g of summation.Hereinafter, will in Fig. 8 A to Fig. 8 C control circuit 300e to 300g description
Do not there is provided by Fig. 4 A control circuit 300a and Fig. 4 B control circuit 300b description repetitive description.
Reference picture 8A, summing circuit 322e may include the first summation sub-circuit 322e_1, the second summation sub-circuit 322e_3
With level shifter 322e_2.First summation sub-circuit 322e_1 can be asked current sensing signal CS and ramp signal RAMP
With.Level shifter 322e_2 can be shifted the level of the first summation sub-circuit 322e_1 output signal.In other words,
Level shifter 322e_2 can carry out shape by the way that current sensing signal CS and ramp signal RAMP sums DC level are shifted
Into the skew OFFSET of the change for reflecting the error signal ERR in the second internal signal INT2 at least a portion.Second
Summation sub-circuit 322e_3 can be to level shifter 322e_2 output summed with error signal ERR.
Reference picture 8B, summing circuit 322f may include the summation sub-circuits of the first summation sub-circuit 322f_1 and second 322f_
4th, current-voltage (I-V) converter 322f_2 and level shifter 322f_3.In Fig. 8 B example, current sensing signal CS
There can be the electric current of level change with each in ramp signal RAMP.Therefore, the first summation sub-circuit 322f_1 can be
Electric current summing circuit (for example, Fig. 6 B summing circuit), and it is exportable have and current sensing signal CS and ramp signal
The electric current of level corresponding to RAMP sums.The electric current that I-V converters 322f_2 will can export from the first summation sub-circuit 322f_1
Be converted to voltage.Level shifter 322f_3 can be shifted the DC level of the voltage exported from I-V converters 322f_2.The
Two summation sub-circuit 322f_4 can be to level shifter 322f_3 output summed with error signal ERR.
Reference picture 8C, the second internal signal maker 320g may include for error signal ERR to be carried out into level shift
Level shifter 323g.Summing circuit 322g may include the summation sub-circuit 322g_2 of the first summation sub-circuit 322g_1 and second,
Wherein, the first summation sub-circuit 322g_1 is used to sum to current sensing signal CS and ramp signal RAMP, the second summation
The error signal ERR that sub-circuit 322g_2 is used for output and level shift to the first summation sub-circuit 322g_1 sums.
In other words, level shifter 323g can be used to reflect second by the way that error signal ERR DC level is shifted to be formed
The skew OFFSET of the change of error signal ERR in internal signal INT2 at least a portion.
According to an example embodiment, compared with Fig. 8 A to the example shown in 8C, the second internal signal maker may include
Two or more level shifters.For example, the second internal signal maker may include to be used for by current sensing signal CS or
Current sensing signal CS and ramp signal RAMP sums carry out the first level shifter of level shift, for error signal
The summation electricity that ERR carries out the second electrical level shift unit of level shift and summed for two signals to level shift
Road.
Fig. 9 A and Fig. 9 B are the diagrams for the result for showing the analog switch voltage-stablizer according to example embodiment.In detail,
Fig. 9 A show to simulate the boosting of the switching regulator and simulation drawing 2 of the control circuit 300b including Fig. 4 B under the same conditions
The result of converter 10 '.Fig. 9 B show that Fig. 9 A t1-t2 intervals are exaggerated.As will be described below, Fig. 9 A and 9B simulation
As a result the transient response of switching regulator according to example embodiment is shown.
Reference picture 9A and Fig. 9 B, load current I_LOAD can be begun to ramp up at time t1.With load current I_LOAD
Rising, Fig. 2 current sensing signal CS ' and ramp signal RAMP ' sum CS '+RAMP ' can significantly vibrate from basic level, and
Second internal signal INT2 basic level can decline.Therefore, the inductor current I_L ' that inductor current I_L can be than Fig. 2
Quickly increase.As a result, output voltage V_OUT can drop below Fig. 2 output voltage V_OUT '.In other words, output electricity
The lower level of the output voltage V_OUT ' undershoots than Fig. 2 can be had by pressing V_OUT undershoot.Analog result shows, output voltage
V_OUT undershoot have leapt high under output voltage V_OUT' than Fig. 2 about 1/3 level.
In addition, reference picture 9A, load current I_LOAD can be begun to decline at time t3.With under load current I_LOAD
Drop, Fig. 2 current sensing signal CS ' and ramp signal RAMP ' sum CS '+RAMP ' can significantly vibrate from basic level, and the
Two internal signal INT2 basic level can rise.Therefore, inductor current I_Ls ' of the inductor current I_L than Fig. 2 be faster
Ground reduces.As a result, output voltage V_OUT can rise to below Fig. 2 output voltage V_OUT '.In other words, output voltage V_
OUT overshoot can have the lower level of the overshoot of the output voltage V_OUT ' than Fig. 2.Analog result can show output voltage V_
OUT overshoot has about 1/3 level lower than output voltage V_OUT ' overshoot.
Figure 10 A and Figure 10 B are to schematically show the switching regulator for including the control circuit according to example embodiment
Circuit diagram.In detail, Figure 10 A and 10B are shown respectively including the control circuit 23a and control circuit according to example embodiment
23b boost DC-DC converter.
Reference picture 10A and Figure 10 B, switching regulator 20a may include rectifier 21a, on-off circuit 22a, control circuit
23a, feedback signal generative circuit 24a and multiple passive device L, C, RC, R1 and R2, switching regulator 20b may include rectification
Device 21b, on-off circuit 22b, control circuit 23b, feedback signal generative circuit 24b and multiple passive device L, C, RC, R1 and
R2.As described above, rectifier 21a can block the electricity that inductor L or on-off circuit 22a are flowed to from capacitor C and lead-out terminal 26
Stream, rectifier 21b can block the electric current that inductor L or on-off circuit 22b are flowed to from capacitor C and lead-out terminal 26.Feedback letter
Each offer in number generative circuit 24a and feedback signal generative circuit 24b is given birth to by divider 24a_1 and divider 24b_1
Into feedback voltage V _ FB and the current sensing signal CS that is generated by current sensor 24a_2 and current sensor 24b_2.Control
Each in circuit 23a and control circuit 23b processed can be based on feedback voltage V _ FB, reference voltage V_REF and current sense letter
Number CS generates control signal CTRL.Hereinafter, the identical description on Fig. 1 switching regulator 10 is applied to Figure 10 A
Switching regulator 20a and Figure 10 B switching regulator 20b, therefore will be omitted.
Reference picture 10A, rectifier 21a may include diode.On-off circuit 22a may include impulse generator 22a_1 and crystalline substance
Body pipe 22a_2.Impulse generator 22a_1 may be in response to control signal CTRL and clock signal clk and be used to control crystal to generate
Pipe 22a_2 first grid signal NG.For example, impulse generator 22a_1 can swash in the rising edge or trailing edge of clock signal clk
First grid signal NG living, i.e. high voltage can be supplied to transistor 22a_2 grid.When the control signal is activated, pulse is given birth to
The 22a_1 that grows up to be a useful person can deactivate first grid signal NG, i.e. can supply low-voltage (for example, ground to transistor 22a_2 grid
Potential).
Reference picture 10B, rectifier 21b may include transistor.On-off circuit 22b may include impulse generator 22b_1 and crystalline substance
Body pipe 22b_2.Impulse generator 22b_1 may be in response to control signal CTRL and clock signal clk, be used to control crystal to generate
Pipe 22b_2 first grid signal NG and the transistor for controlling rectifier 21b second grid signal PG.In other words
Say, transistor 22b_2 may be in response to first grid signal NG and be used as first switch, and rectifier 21b transistor may be in response to
Second grid signal PG and be used as second switch.As shown in Figure 10 B, including the transistor of second grid signal PG control is passed through
Rectifier 21b is referred to alternatively as synchronous rectifier.
Impulse generator 22b_1 can generate the first grid signal NG similar to Figure 10 A impulse generator 22a_1, and
And the second grid signal PG synchronous with first grid signal NG can be generated.In other words, impulse generator 22b_1 can generate that
This synchronous first grid signal NG and second grid signal PG so that by inductor L electric current by on-off circuit 22b's
Transistor 22b_2 or rectifier 21b transistor.For example, as shown in Figure 10 B, if on-off circuit 22b transistor 22b_
2 be N-channel metal-oxide semiconductor (MOS) nmos pass transistor, and if rectifier 21b transistor is P-channel metal oxide
Transistor PMOS transistor, then first grid signal NG and second grid signal PG can be substantially identical.
Figure 11 and Figure 12 is to schematically show the switching regulator for including the control circuit according to example embodiment
Circuit diagram.In detail, Figure 11 shows to include (or the decompression of buck converter 30 of the control circuit 33 according to example embodiment
Dc-dc).Figure 12 shows to include (or the drop of bust-boost converter 40 of the control circuit 43 according to example embodiment
Pressure-boost DC-DC converter).It is controllable except Figure 11 and figure according to the control circuit of the switching regulator of exemplary embodiment
Various switching regulators outside switching regulator shown in 12.Furthermore, it is to be understood that can be from the position shown in Figure 11 and Figure 12
Different positions senses electric current to generate the current sensing signal CS4 in current sensing signal CS3 and Figure 12 in Figure 11.
Reference picture 11, buck converter 30 may include on-off circuit 32, control circuit 33, the and of feedback signal generative circuit 34
Multiple passive device L3, D3, C3, RC3, R31 and R32, it can be exported from being supplied to the input voltage V_IN3 of input terminal 35 to generate
Voltage V_OUT3, and the output voltage V_OUT3 of generation can be exported by input terminal 36.Feedback signal generative circuit 34 can
Including generating current sensing signal CS3 current sensor 34_2 and generating feedback voltage V _ FB3 divider 34_1.According to
One example embodiment, control circuit 33 can be based on feedback voltage V _ FB3, reference voltage V_REF3 and current sensing signal CS3
To generate control signal CTRL3.For example, control circuit 33 can be by will give birth to from feedback voltage V _ FB3 and reference voltage V_REF3
Into the first internal signal with from feedback voltage V _ FB3, reference voltage V_REF3 and current sensing signal CS3 generation second in
Portion's signal is compared, to generate control signal CTRL3.
On-off circuit 32 may include impulse generator 32_1 and switch 32_2.Impulse generator 32_1 may be in response to from control
The control signal CTRL3 and clock signal clk 3 that circuit 33 receives generate pulse signal PS3.Switch 32_2 may be in response to pulse
Signal PS3 and turn on/off.
Reference picture 12, bust-boost converter 40 may include on-off circuit 42, control circuit 43, feedback signal generation electricity
Road 44 and multiple passive device L4, D4, C4, RC4, R41 and R42, can be from being supplied to the input voltage V_IN4 of input terminal 45 to give birth to
Into output voltage V_OUT4, and the output voltage V_OUT4 of generation can be exported by lead-out terminal 46.Feedback signal generation electricity
Road 44 may include the current sensor 44_2 for the generating current sensing signal CS4 and divider 44_ for generating feedback voltage V _ FB4
1.According to an example embodiment, control circuit 43 can be based on feedback voltage V _ FB4, reference voltage V_REF4 and current sense is believed
Number CS4 generates control signal CTRL4.For example, control circuit 43 can be by will be from feedback voltage V _ FB4 and reference voltage V_
REF4 generation the first internal signal with from feedback voltage V _ FB4, reference voltage V_REF4 and current sensing signal CS4 generation
Second internal signal is compared, to generate control signal CTRL4.
On-off circuit 42 may include impulse generator 42_1 and switch 42_2.Impulse generator 42_1 may be in response to from control
The control signal CTRL4 and clock signal clk 4 that circuit 43 receives generate pulse signal PS4.Switch 42_2 may be in response to pulse
Signal PS4 and turn on/off.
Figure 13 is the flow chart for the control method for showing the switching regulator according to example embodiment.As shown in figure 13, open
Closing the control method of voltage-stablizer may include step S20 to step S80.Hereinafter, Figure 13 is described into reference picture 1.
In step S20, it can perform and generate feedback voltage from the output voltage of switching regulator and given birth to from inductor current
Into the operation of current sensing signal.For example, as shown in figure 1, partial pressure can be carried out to output voltage V_OUT by resistor R1 and R2
To generate feedback voltage V _ FB.In addition, the electric current for switching 220 can be flowed through to generate current sensing signal CS by sensing.
In step s 40, it can perform the operation that the first internal signal is generated based on feedback voltage and reference voltage.For example,
As shown in figure 1, the first internal signal maker 310 of control circuit 300 can give birth to from feedback voltage V _ FB and reference voltage V_REF
Into the first internal signal INT1.In one embodiment, as shown in Figure 4 A, feedback voltage V _ FB can be supplied to the first amplifier
311a reversed input terminal, reference voltage V_REF can be supplied to the first amplifier 311a non-inverting input terminal.First
Internal signal INT1 can be the first amplifier 311a output, and can have and feedback voltage V _ FB and reference voltage V_
The level of difference corresponding (or proportional) between REF.
In step S60, it can perform and the second internal signal is generated based on feedback voltage, reference voltage and current sensing signal
Operation.For example, as shown in figure 1, the second internal signal maker 320 of control circuit 300 can be from feedback voltage V _ FB, reference
Voltage V_REF and current sensing signal CS generates the second internal signal INT2.Second internal signal INT2 can have oscillator signal
Form, its basic level according between feedback voltage V _ FB and reference voltage V_REF difference and change.Below with reference to Figure 14
Step S60 detailed content is described.
It is executable by being compared to the first internal signal and the second internal signal to generate control in step S80
The operation of signal.For example, as shown in figure 1, the comparator 330 of control circuit 300 can by its non-inverting input terminal and it
Reversed input terminal receive the first control signal INT1 and the second control signal INT2, and exportable control signal
CTRL.Control signal CTRL can be used for the switching sequence for determining switching regulator.Control signal CTRL can be used for passing through base
The change that is loaded caused by the characteristic due to the second internal signal generated in step S60 and increase or decrease and flow through inductor
L electric current, to reduce the undershoot of output voltage V_OUT level or overshoot.In other words, the control method phase of switching regulator
The fast transient response of switching regulator can be provided for other control methods.
Figure 14 is the flow chart for the example for showing the step S60 according to Figure 13 of example embodiment.As explained above with Figure 13
Description, it can perform in step S60 and the second internal signal generated based on feedback voltage, reference voltage and current sensing signal
Operation.
Reference picture 14, in step S62, it can perform generation and the poor proportional mistake between feedback voltage and reference voltage
The operation of difference signal.For example, as shown in Figure 4 A, reference voltage V_REF can be supplied to the second amplifier 321a inverting input
Son, feedback voltage V _ FB can be supplied to the second amplifier 321a non-inverting input terminal.Second amplifier 321a it is exportable with
Error signal ERR corresponding to difference between feedback voltage V _ FB and reference voltage V_REF.
In step S64, the executable operation summed to current sensing signal and error signal.For example, such as Fig. 4 A
It is shown, the error signal ERR for the output for being used as the second amplifier 321a and current signal CS can be entered by summing circuit 322a
Row summation.Second internal signal INT2 can be oscillator signal, and its basic level is according to the output as summing circuit 322a
Error signal ERR changes.
According to an example embodiment, in step S64, it can perform and current sensing signal, error signal and slope are believed
Number operation summed.For example, ramp signal can be serrated signal, its level increases during switch periods.Such as Fig. 4 B
Shown, summing circuit 322b can be by carrying out summation next life to current sensing signal CS, ramp signal RAMP and error signal ERR
Into the second internal signal INT2.Now, it is at least one in current sensing signal CS, ramp signal RAMP and error signal ERR
Skew OFFSET can be formed in the second internal signal INT2 so that input ranges of the second internal signal INT2 in comparator
It is interior, but regardless of error signal ERR change.
According to an example embodiment, in step S64, it can perform and current sensing signal, error signal and biasing are believed
Number operation summed.For example, as shown in Figure 7 A, offset signal BIAS can be the skew to form the second internal signal INT2
OFFSET DC signals.Summing circuit 322c can be by entering to current sensing signal CS, error signal ERR and offset signal BIAS
Row is summed to generate the second internal signal INT2.In addition, as shown in Figure 7 B, can to current sensing signal CS, error signal ERR,
Ramp signal RAMP and offset signal BIAS are summed.
It is executable that current sensing signal or error signal are entered into line level in step S64 according to an example embodiment
Displacement, and to operation that the signal of level shift is summed with current sensing signal or error signal.For example, Fig. 4 A's shows
Current sensing signal CS in example can be before summing circuit 322a be input to by level shift.As shown in Figure 8 A, can be by electric current
Sensing signal CS and ramp signal RAMP sums carry out level shift.As shown in Figure 8 C, error signal ERR can be entered to line level shifting
Position.
Figure 15 is the block diagram for showing to include the system 1000 according to the switching regulator of example embodiment.As shown in figure 15,
System 1000 may include power supply 1100, processor 1200, memory sub-system 1300, memory 1400, input/output (I/O)
Device 1500 and display device 1600.
The executable calculating of processor 1200 or task.For example, processor 1200 can be microprocessor, central processing unit
(CPU) etc..Processor 1200 can be communicated by bus with the other assemblies of system 1000.Memory sub-system 1300 and deposit
Reservoir 1400 can be needed for the operation of storage system 1000 data.For example, memory sub-system 1300 may include volatile storage
Device device (such as, dynamic random access memory (DRAM), static RAM (SRAM) and mobile DRAM), and may include non-easy
The property lost storage arrangement (such as, flash memory, Electrically Erasable Read Only Memory (EEPROM), phase transformation RAM (PRAM), resistance
RAM (RRAM), magnetic resistance RAM (MRAM) and ferroelectric RAM (FRAM)).Memory 1400 may also include non-volatile memory device,
And it may include the storage medium of such as solid-state drive (SSD), hard disk drive (HDD) and CD-ROM (CD-ROM).I/O
Device 1500 may include input unit (such as, keyboard, button, touch pad, touch-screen and mouse), and may include output device
(such as, loudspeaker and printer).Display device 1600 may include liquid crystal display (LCD) device, organic light emitting display (OLED)
Device etc..
Power supply 1100 can be based on external voltage V_EXT and generate supply voltage V1 to V5, and can be by the supply voltage of generation
V1 to V5 is supplied to other assemblies (that is, processor 1200, memory sub-system 1300, memory 1400, the I/O of system 1000
Device 1500 and display device 1600).For example, system 1000 may include battery.The voltage for being supplied to power supply 1100 can be from
The cell voltage of battery supplied.Alternatively, in another example, system 1000 can be by power line from power from outside.Outside
Portion voltage V-EXT can be the voltage from the electric power generation supplied by power line.In other words, external voltage V_EXT can be with
It is the voltage of power line, and can is the DC electricity that rectification generation is carried out by exchange (AC) voltage to being supplied from power line
Pressure.
Power supply 1100 may include the switching regulator according to example embodiment, wherein, switching regulator generation supply voltage
It is at least one in V1 to V5.In other words, the switching regulator included in power supply 1100 may include quick cor-rection loop with
And voltage loop and current loop, and the quick transient response relative to other switching regulators can be provided.Therefore, system
1000 other assemblies can stably receive electric power from power supply 1100.
Although the embodiment with reference to present inventive concept specifically illustrates and describes inventive concept, it will be understood that,
In the case of not departing from spirit and scope by the claims, various changes can be carried out in form and details.
Claims (25)
1. the control circuit in a kind of switching regulator, the switching regulator includes inductor and is configured to believe in response to control
Number control the on-off circuit of the electric current by inductor, the control circuit is configured as receiving the output electricity of switching regulator
The feedback voltage of pressure and the electric current by inductor is received as current sensing signal, wherein, the control circuit includes：
First internal signal maker, it is configured as generating the first internal signal based on feedback voltage and reference voltage；
Second internal signal maker, it is configured as generating the second internal signal based on current sensing signal to cause inside second
The basic level of signal changes according to feedback voltage and reference voltage；
Comparator, it is configured as based on the first internal signal and the second internal signal come output control signal.
2. control circuit according to claim 1, wherein, the first internal signal maker includes：
Amplifier, there is the reversed input terminal for being configured as receiving feedback voltage and be configured as receiving the non-anti- of reference voltage
Phase input terminal, the amplifier are configured as exporting the first internal signal based on feedback voltage and reference voltage.
3. control circuit according to claim 1, wherein, the second internal signal maker includes：
Amplifier, there is the non-inverting input terminal for being configured as receiving feedback voltage and be configured as receiving the anti-of reference voltage
Phase input terminal, the amplifier are configured as being based on feedback voltage and reference voltage output error signal；
Summing circuit, it is configured as by being summed current sensing signal and error signal to generate the second internal signal.
4. control circuit according to claim 3, wherein,
Summing circuit is configured as：By being summed current sensing signal, error signal and DC bias signal to generate
Second internal signal so that DC bias signal, current sensing signal and error signal sum are in the input range of comparator.
5. control circuit according to claim 3, wherein, summing circuit is configured as：To current sensing signal, error letter
Number and saw-tooth ramp signal summed, wherein, the level of saw-tooth ramp signal increases during the switch periods of on-off circuit.
6. control circuit according to claim 5, wherein, saw-tooth ramp signal has direct current offset so that current sense
Signal, saw-tooth ramp signal and error signal sum are in the input range of comparator.
7. control circuit according to claim 5, wherein, summing circuit includes：
First summation sub-circuit, is configured as：Current sensing signal and saw-tooth ramp signal are summed；
Level shifter, it is configured as：The DC level of the output signal of first summation sub-circuit is shifted so that first
The output signal of summation sub-circuit is with error signal sum in the input range of comparator；
Second summation sub-circuit, is configured as：Summation next life is carried out by the output signal to level shifter and error signal
Into the second internal signal.
8. control circuit according to claim 7, wherein,
First summation sub-circuit is electric current summation sub-circuit,
Summing circuit also includes：
Current-voltage converter, it is configured as the electric current of the output signal of the first summation sub-circuit being converted into voltage；
Level shifter, it is configured as being shifted the DC level of the output signal of current-voltage converter.
9. control circuit according to claim 3, wherein, the second internal signal maker also includes：
Level shifter, it is configured as：The DC level of error signal is shifted so that current sensing signal is believed with error
Number sum in the input range of comparator,
Wherein, summing circuit is configured as summing to the output signal of current sensing signal and level shifter.
10. control circuit according to claim 1, wherein,
Inductor, which has, is configured as the first end for receiving input voltage and the second end for being connected to on-off circuit,
The switching regulator is boost converter and the switching regulator also includes：
Rectifier, there is the first end at the second end for being connected to inductor and be configured as exporting the second end of output voltage,
Capacitor and resistor, it is connected in series between the second end of rectifier and ground.
11. a kind of switching regulator, including：
Inductor；
Feedback signal generative circuit, is configured as：Feedback voltage is generated from the output voltage of the switching regulator, and is based on
Current sensing signal is generated by the electric current of inductor；
Control circuit, it is configured as generating control signal based on feedback voltage and current sensing signal；
On-off circuit, control signal is configured to respond to control the electric current by inductor,
Wherein, control circuit includes：
First internal signal maker, it is configured as generating the first internal signal based on feedback voltage and reference voltage,
Second internal signal maker, is configured as：Second internal signal is generated based on current sensing signal so that in second
The basic level of portion's signal changes according to feedback voltage and reference voltage,
Comparator, it is configured as being based on the first internal signal and the second internal signal output control signal.
12. switching regulator according to claim 11, wherein, the first internal signal maker is configured as：Passing through will
Difference between reference voltage and feedback voltage is amplified, to export the first internal signal.
13. switching regulator according to claim 11, wherein, the second internal signal maker is configured as：By right
Error signal is summed to generate the second internal signal with current sensing signal, wherein, error signal is the feedback electricity of amplification
Difference between pressure and reference voltage.
14. switching regulator according to claim 13, wherein,
Second internal signal maker is configured as：Error signal and current sensing signal are asked with DC bias signal
With so that DC bias signal, current sensing signal and error signal sum are in the input range of comparator.
15. switching regulator according to claim 13, wherein, the second internal signal maker is configured as：To error
Signal and current sensing signal are summed with saw-tooth ramp signal, wherein, the level of saw-tooth ramp signal is in on-off circuit
Increase during switch periods.
16. switching regulator according to claim 15, wherein, saw-tooth ramp signal has direct current offset so that electric current
Sensing signal, saw-tooth ramp signal and error signal sum are in the input range of comparator.
17. switching regulator according to claim 15, wherein, the second internal signal maker is configured as：To electric current
Sensing signal and saw-tooth ramp signal are summed, and the DC level of the signal after summation is shifted, and to level
The signal of displacement is summed with error signal so that the second internal signal is in the input range of comparator.
18. switching regulator according to claim 13, wherein, the second internal signal maker is configured as：Passing through will
The DC level of error signal is shifted to generate the second internal signal so that input model of second internal signal in comparator
In enclosing, and the signal and current sensing signal of level shift are summed.
19. a kind of control method of switching regulator, wherein, the switching regulator includes inductor and is configured to respond to
The on-off circuit of the electric current of inductor is passed through in control signal control, and the control method includes：
Feedback voltage is generated from the output voltage of the switching regulator；
Current sensing signal is generated from by the electric current of inductor；
First internal signal is generated based on feedback voltage and reference voltage；
Second internal signal is generated based on current sensing signal, the basic level of current sensing signal is according to feedback voltage and reference
Voltage change；
Based on the first internal signal and the second internal signal generation control signal.
20. control method according to claim 19, wherein, the step of generating the first internal signal, includes：
The first poor internal signal that generation corresponds between reference voltage and feedback voltage.
21. control method according to claim 19, wherein, the step of generating the second internal signal, includes：
Generation and the poor proportional error signal between feedback voltage and reference voltage；
Current sensing signal and error signal are summed.
22. control method according to claim 21, wherein, the step summed to current sensing signal and error signal
Suddenly include：
Current sensing signal and error signal are summed with saw-tooth ramp signal, wherein, the level of saw-tooth ramp signal exists
Increase during the switch periods of on-off circuit.
23. control method according to claim 21, wherein, the step summed to current sensing signal and error signal
Suddenly include：
Current sensing signal and error signal are summed with offset signal, by current sensing signal and error signal sum
DC level shifted.
24. a kind of switching regulator, including：
Input node, it is configured as receiving input load electric current；
Output node, it is configured as exporting output load current；
Rectifier, it is connected between first node and section point；
On-off circuit, it is configured as：Pulse signal is generated based on input load electric current, clock signal and control signal；
Control circuit, including：
First internal signal maker, is configurable to generate the first internal signal,
Second internal signal maker, is configured as：Based on feedback voltage and reference voltage generation error signal, wherein, feedback
Based on the output voltage at output node, the second internal signal maker is configured as being based on error signal and current sense voltage
The internal signal of signal generation second, wherein, current sensing signal is based on pulse signal and input load electric current,
Output circuit, it is configured as：Control signal is generated based on the first internal signal and the second internal signal.
25. switching regulator according to claim 24, wherein, on-off circuit is configured as changing arteries and veins based on control signal
Rush the dutycycle of signal.
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| KR10-2016-0109552 | 2016-08-26 | ||
| KR1020160109552A KR102697926B1 (en) | 2016-08-26 | 2016-08-26 | Switching regulator and control circuit thereof |
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| US10211729B2 (en) | 2019-02-19 |
| KR20180023742A (en) | 2018-03-07 |
| KR102697926B1 (en) | 2024-08-22 |
| US20180062509A1 (en) | 2018-03-01 |
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