CN105490534A - Current-mode control DCDC boost converter and pulse frequency modulation method thereof - Google Patents
Current-mode control DCDC boost converter and pulse frequency modulation method thereof Download PDFInfo
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- CN105490534A CN105490534A CN201510981932.3A CN201510981932A CN105490534A CN 105490534 A CN105490534 A CN 105490534A CN 201510981932 A CN201510981932 A CN 201510981932A CN 105490534 A CN105490534 A CN 105490534A
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- HEZMWWAKWCSUCB-PHDIDXHHSA-N (3R,4R)-3,4-dihydroxycyclohexa-1,5-diene-1-carboxylic acid Chemical compound O[C@@H]1C=CC(C(O)=O)=C[C@H]1O HEZMWWAKWCSUCB-PHDIDXHHSA-N 0.000 title claims abstract description 57
- 238000000034 method Methods 0.000 title claims abstract description 12
- 230000001939 inductive effect Effects 0.000 claims description 95
- 230000003247 decreasing effect Effects 0.000 claims description 16
- 239000003990 capacitor Substances 0.000 claims description 4
- 238000004519 manufacturing process Methods 0.000 claims description 2
- 230000008859 change Effects 0.000 abstract description 7
- 230000010354 integration Effects 0.000 abstract description 3
- 230000008569 process Effects 0.000 abstract description 3
- 230000004044 response Effects 0.000 abstract description 2
- 238000010586 diagram Methods 0.000 description 13
- 230000006872 improvement Effects 0.000 description 3
- 230000001276 controlling effect Effects 0.000 description 2
- 238000004088 simulation Methods 0.000 description 2
- 230000009471 action Effects 0.000 description 1
- 230000007547 defect Effects 0.000 description 1
- 230000003111 delayed effect Effects 0.000 description 1
- 238000012423 maintenance Methods 0.000 description 1
- 230000001105 regulatory effect Effects 0.000 description 1
- 230000006641 stabilisation Effects 0.000 description 1
- 238000011105 stabilization Methods 0.000 description 1
- 230000009897 systematic effect Effects 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/1566—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators with means for compensating against rapid load changes, e.g. with auxiliary current source, with dual mode control or with inductance variation
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The invention provides a current-mode control DCDC boost converter and a pulse frequency modulation method thereof. The current-mode control DCDC boost converter is fabricated by an integrated circuit device; a control circuit of the DCDC boost converter comprises a control unit, an inductor current keeping unit and an output voltage comparison unit; when the inductor current keeping unit detects that an inductor current I<L> is gradually reduced to 0 and the output voltage comparison unit detects that an output voltage V<O> is reduced to V<ref>, a master switch SW1 is connected and a secondary switch SW2 is disconnected, so that the I<L> gradually rises; when the I<L> rises to a reference current I<ref>, the master switch SW1 is disconnected and the secondary switch SW2 is connected; the working process is continuous in cycles; and the output voltage V<O> is stabilized close to a reference voltage V<ref>. The system structure is effectively simplified; the system integration difficulty is lowered; aiming at the change of a load current, the system can quickly make a response; and ripples of the output voltage V<O> when the load current changes are effectively reduced.
Description
Technical field
The invention belongs to the switch power technology field in analog integrated circuit, particularly relate to a kind of current-mode control DCDC boosting variator and pulse frequency modulated method thereof.
Background technology
DC-DC is the abbreviation of English direct current inversion of direct current, and DCDC boosting variator comprises one and DC low-voltage is transformed to the circuit of DC high voltage and corresponding control circuit.This circuit generally adopts current-mode pulse width modulation to carry out DCDC boosting.
Please refer to Figure 1A and be depicted as conventional current mould pulse width modulation: the oscillator (oscillator) of a fixed frequency produces a clock signal clk, CLK signal controls to make main switch SW1 conducting in each switch periods, makes to disconnect from interrupteur SW 2.Meanwhile, error amplifier EA is by output voltage V
owith reference voltage V
refbetween error carry out amplifying rear generation error signal V
c; Systems axiol-ogy inductive current I on the other hand
l, and be superimposed with a slope current I
slopeafter, flow on resistance Rs and produce voltage Vs, Vs and V
csignal compares, when it is greater than V
ctime, main switch SW1 disconnects by pwm comparator (PWMcomparator) by output pwm signal, will from interrupteur SW 2 conducting.When next CLK signal arrives, repeat above process.Therefore, the size of system by regulating the size of VC to control inductive current, to make output voltage V
osubstantially reference voltage V is equaled
ref.
ON time and the ratio of CLK signal period of interrupteur SW 1 are called duty ratio D, D=T
on, sw1/ T
cLK.Ideally, system when stable state continuous conduction mode, output voltage Vo=V
bat/ (1-D).Because the duty ratio D of DCDC boosting variator is less than 1, so Vo > V
bat, reach boosting object.
In traditional current-mode control mode, in order to make system stability work, need to connect larger electric capacity Cc, resistance Rz and an electric capacity Cp at the output of error amplifier and compensate, bulky capacitor is not only difficult to integrated, and makes V
creaction speed when signal pin changes load current is slack-off, causes when load current changes, output voltage V
olarger ripple will be produced.As shown in Figure 1B, t is worked as
1moment load current I
loadwhen unexpected change is large, due to the delayed action of electric capacity Cc, cause V
cwill postpone (delay) time reacts, because inductive current mean value will be less than load current I within this period of time of delay
load, therefore output voltage V
oto reduce, produce lower than reference voltage V
reflarger ripple Δ V
o.Otherwise, when load current diminishes suddenly, output voltage V
oto produce higher than reference voltage V
reflarger ripple.
Summary of the invention
The object of the invention is the defect overcoming prior art, provide that a kind of integrated level is high, the DCDC of output voltage stabilization boosts variator and pulse frequency modulated control method thereof.
For achieving the above object, the present invention proposes a kind of current-mode control DCDC boosting variator, described DCDC boosting variator comprises a DCDC booster circuit and coupled control circuit; Described booster circuit comprises DC power supply, inductance, load, main switch SW1 and from interrupteur SW 2; Described control circuit comprises control unit, inductive current holding unit and output voltage comparing unit; Wherein:
Described control unit receives the signal that described inductive current holding unit and described output voltage comparing unit are sent, and to boost variator main switch SW1 and send the control signal be turned on or off from interrupteur SW 2 to DCDC, to ensure that DCDC boosts the normal work of variator;
Described inductive current holding unit, controls the ON time of main switch SW1 in each work period so that by described inductive current I
lremain on 0 ~ I
refbetween, wherein I
reffor reference current; Also I detected simultaneously
lwhen being decreased to 0, sending signal to described control unit and make to disconnect from interrupteur SW 2, prevent inductive current from oppositely causing loss of charge from load flow to power supply;
Described output voltage comparing unit, compares output voltage V
owith reference voltage V
refsize, and comparison signal is exported to described control unit;
Above-mentioned three unit collaborative works, in the beginning of a work period, main switch SW1 disconnects from interrupteur SW 2 conducting, when described inductive current holding unit detects I
lbe decreased to 0 gradually and described output voltage comparing unit detects output voltage V
obe reduced to V
reftime, main switch SW1 conducting disconnects from interrupteur SW 2 and makes I
lgo up gradually; When described inductive current holding unit detects I
lrise to I
reftime, main switch SW1 disconnects, and from interrupteur SW 2 conducting, the above course of work is gone round and begun again and constantly continued, by output voltage V
obe stabilized in reference voltage V
refnear.
In one embodiment, described output voltage comparing unit at least comprises an output voltage comparator, for comparing output voltage V
owith reference voltage V
refsize.
In one embodiment, described output voltage comparing unit also comprises an error amplifier and a building-out capacitor, to make V
oaccurately equal V
ref.
In one embodiment, described inductive current holding unit comprises an inductive current comparator and an inductive current zero-crossing comparator, and described inductive current comparator compares inductive current I
lwith reference current I
refsize, and comparison signal is exported to described control unit; Described inductive current zero-crossing comparator is once inductive current I be detected
lbe decreased to 0, then send signal to described control unit and make to disconnect from interrupteur SW 2, to prevent inductive current oppositely from V
oflow to V
bATthus cause loss of charge.
In one embodiment, described inductive current holding unit comprises a current comparator with two interrupteur SW 3 and SW4, and wherein SW3 is connected with 0 electric current, SW4 and reference current I
refbe connected, compare inductive current I by the on-off of SW3 and SW4
lwith reference current I
refsize and comparison signal exported to described control unit and detect inductive current I
lwhen dropping to 0, send signal to described control unit and make to disconnect from interrupteur SW 2, to prevent inductive current oppositely from V
oflow to V
bATthus cause loss of charge.
In one embodiment, described inductive current holding unit comprises a fixing ON time timer and an inductive current zero-crossing comparator, described fixing ON time timer controls the ON time of main switch SW1 in each work period, to keep described inductive current; Described inductive current zero-crossing comparator is once I detected
lwhen being decreased to 0, sending signal to described control unit and make to disconnect from interrupteur SW 2, prevent inductive current from oppositely causing loss of charge from load flow to power supply.
The wherein ON time T of main switch SW1
on, sw1with reference current I
refbetween have following relation: I
ref=V
bat* T
on, sw1/ L
Wherein I
reffor reference current, V
batfor input voltage, T
on, sw1for the ON time of main switch SW1, L is inductance value;
Reference current I
refwith the electric current I flowing through load
loadrelation need meet:
I
ref>2*I
load*V
o/V
bat；
The operating frequency of system is:
Each unit of control circuit of the present invention all adopts production of integrated circuits.
In addition, the invention allows for the pulse frequency modulated method of a kind of current-mode control DCDC boosting variator, adopt above-mentioned current-mode control DCDC boosting variator, in the beginning of a work period, main switch SW1 disconnects from interrupteur SW 2 conducting, when described inductive current holding unit detects I
lbe decreased to 0 gradually and described output voltage comparing unit detects output voltage V
obe reduced to V
reftime, main switch SW1 conducting disconnects from interrupteur SW 2 and makes I
lgo up gradually; When described inductive current holding unit detects I
lrise to I
reftime, main switch SW1 disconnects, and from interrupteur SW 2 conducting, the above course of work is gone round and begun again and constantly continued, by output voltage V
obe stabilized in reference voltage V
refnear; In the above-mentioned course of work, described inductive current holding unit is once I be detected
lwhen being decreased to 0, namely sending signal to described control unit and make to disconnect from interrupteur SW 2, prevent inductive current from oppositely causing loss of charge from load flow to power supply.
DCDC boosting variator of the present invention adopts integrated circuit (IC)-components to make, and compared to traditional control model, effectively simplifies system configuration, reduces system integration difficulty; For the change of load current, system can be made rapidly corresponding, effectively reduces output voltage V
oripple size when load current changes.
Accompanying drawing explanation
Figure 1A is depicted as traditional DCDC boosting variator and current-mode pulse-width modulation method thereof.
Figure 1B is depicted as the current-mode pulse width modulation working waveform figure of the DCDC boosting variator of Figure 1A.
Fig. 2 A is the circuit diagram of the embodiment 1 of DCDC of the present invention boosting variator.
Fig. 2 B is depicted as the current-mode pulse width modulation working waveform figure of the DCDC boosting variator of Fig. 2 A.
Fig. 3 is the circuit diagram of the embodiment 2 of DCDC of the present invention boosting variator.
Fig. 4 is the circuit diagram of the embodiment 3 of DCDC of the present invention boosting variator.
Fig. 5 is the circuit diagram of the embodiment 4 of DCDC of the present invention boosting variator.
Fig. 6 is current-mode pulse width modulation and the traditional mode simulation result comparison diagram of DCDC of the present invention boosting variator.
Fig. 7 is that DCDC of the present invention boosts the circuit diagram of an embodiment of the peak current comparator in variator.
Fig. 8 is that DCDC of the present invention boosts the circuit diagram of an embodiment of the current over-zero comparator in variator.
Fig. 9 is that DCDC of the present invention boosts the circuit diagram of an embodiment of the output voltage comparator in variator.
Embodiment
Below in conjunction with accompanying drawing and for embodiment, the present invention is described in detail.But those skilled in the art should know, the invention is not restricted to listed embodiment, as long as spirit according to the invention, all should be included in protection scope of the present invention.
DCDC boosting variator of the present invention adopts integrated circuit (IC)-components to make, and embodiment is as follows:
embodiment 1
Be the circuit diagram of the embodiment 1 of DCDC boosting variator of the present invention as shown in Figure 2 A.Wherein DCDC boosting variator comprises a DCDC booster circuit and control circuit thereof.
Identical with general DCDC booster circuit general structure, booster circuit critical piece of the present invention has: direct current power source voltage is V
bAT, load end output voltage is V
o, main switch is SW1, be SW2, L from switch be inductance, RL is load resistance.
Be the control circuit of DCDC of the present invention boosting variator in dotted line frame, comprise control unit 210, inductive current holding unit 220 and output voltage comparing unit 230 totally three unit.Each Elementary Function and structure as follows:
Control unit 210, the signal that receiving inductance electric current holding unit 220 and output voltage comparing unit 230 are sent, be responsible for DCDC boosting variator main switch SW1 and send the control signal be turned on or off from interrupteur SW 2, to ensure the normal work of DCDC boosting variator.
Inductive current holding unit 220, is responsible for controlling the ON time of SW1 in each work period so that by inductive current I
lremain between 0 ~ Iref.
In the present embodiment, inductive current holding unit 220 comprises an inductive current zero-crossing comparator (ZCDcomparator) 221 and an inductive current comparator (PeakCurrentComparator) 222.Inductive current zero-crossing comparator 221 is responsible for detecting inductive current I
lwhether be 0, if inductive current I detected
lwhen being decreased to 0, then sending signal to control unit 210 and make to disconnect from interrupteur SW 2, prevent inductive current oppositely from V
oflow to V
bATthus cause loss of charge.Inductive current comparator 222 is responsible for comparing inductive current I
lwith reference current I
refsize, work as I
lby main switch SW1 conducting time too low, work as I
lrise to I
reftime, send signal to control unit 210 and interrupteur SW 1 is disconnected, SW2 conducting, so that by inductive current I
lremain on more than certain numerical value.
Output voltage comparing unit 230, is responsible for comparing output voltage V
owith reference voltage V
refsize, and comparison signal is exported to control unit 210.
Comprise an output voltage comparator (V
ocomparator) 231, for comparing output voltage V
owith reference voltage V
refsize.
Above-mentioned three unit collaborative works, in the beginning of a work period, main switch SW1 disconnects from interrupteur SW 2 conducting, and when described inductive current holding unit 220 detects inductive current I
lbe decreased to 0 gradually and output voltage comparing unit 230 detects output voltage V
obe reduced to V
reftime, main switch SW1 conducting disconnects from interrupteur SW 2 and makes I
lgo up gradually; At this moment input voltage V
bATbe added on inductance, inductive current I
lrise gradually, when inductive current holding unit detects that 230 detect inductive current I
lrise to I
reftime, main switch SW1 disconnects, from interrupteur SW 2 conducting.
In the process, inductive current I is run into
lwhen being decreased to 0 (or close to 0), then disconnect from interrupteur SW 2, prevent inductive current oppositely from V
oend flows to V
bAThold thus cause loss of charge.
The above course of work is gone round and begun again and is constantly continued, by output voltage V
obe stabilized in reference voltage V
refnear.
The wherein ON time T of main switch SW1
on, sw1with reference current I
refbetween have following relation: I
ref=V
bat* T
on, sw1/ L
Wherein I
ref=be reference current, V
batfor input voltage, T
on, sw1for the ON time of main switch SW1, L is inductance value.
In order to the ability making system have enough driving loads, require reference current I
refwith the electric current I flowing through load RL
loadrelation need meet:
I
ref>2*I
load*V
o/V
bat；
The operating frequency of system is:
In a preferred embodiment, each parameter in above-mentioned formula is as follows: V
bAT=0.9V, V
o=1.4V, I
load=10mA, I
ref=100mA, L=2.2uH, f=454.5kHz
Fig. 2 B is depicted as the current-mode pulse width modulation working waveform figure of the present embodiment DCDC boosting variator.As load current I
loadwhen the t1 moment becomes large suddenly, output voltage comparator 231 can detect the change of output voltage immediately, as output voltage V
obe less than reference voltage V
reftime, will high level be exported, and produce control signal by control unit 210 and make SW1 conducting, thus accelerate the switching frequency of SW1, SW2, make inductive current I
lmean value follow load current I
loadchange.Therefore output voltage V
olarger ripple voltage can not be produced.
The present invention, compared to traditional control model, effectively simplifies system configuration, reduces system integration difficulty; For the change of load current, system can be made rapidly corresponding, effectively reduces output voltage V
oripple size when load current changes.
embodiment 2
Be illustrated in figure 3 the circuit diagram of the embodiment 2 of DCDC of the present invention boosting variator.From Fig. 2 B, the output voltage V of the DCDC boosting variator of the basic structure of embodiment 1
owith reference voltage V
ref(this deviation is less than V during systematic steady state to there is deviation slightly
oripple).To ask V
oaccurately equal V
ref, can make further improvements on the basis of embodiment 1, add error amplifier (ErrorAmplifier2) 232 and building-out capacitor Cc at output voltage comparing unit 230.Utilize the high-gain of error amplifier and the negative feedback structure of whole system, output voltage Vo can be set to and accurately equal V
ref.Electric capacity Cc is used for increasing the stability of converter feedback loop.The present embodiment is applicable to need V
oaccurately equal V
refoccasion.
embodiment 3
Fig. 4 is the circuit diagram of the embodiment 3 of DCDC of the present invention boosting variator.
The present embodiment has done further improvement on the basis of embodiment 1, have employed a current comparator 223 replace the inductive current comparator 222 of embodiment 1 and zero-crossing comparator 221 at inductive current holding unit 220.This current comparator 223 is with two interrupteur SW 3 and SW4, and wherein SW3 is connected with 0 electric current, SW4 and reference current I
refbe connected.By SW3 and SW4 on-off, compare inductive current I
lwith reference current I
refsize, or detect inductive current I
lwhether drop to 0.
When SW1 conducting, when SW2 disconnects, control unit 210 output signal makes control switch SW4 conducting, and SW3 disconnects, and current comparator 220 compares inductive current I
lwith reference current I
refsize, work as I
lequal I
reftime, control SW1 disconnects, SW2 conducting; When SW1 disconnects, during SW2 conducting, control unit 210 exports control signal and makes interrupteur SW 3 conducting, and SW4 disconnects, and now whether comparator drops to 0 for detecting inductive current, works as V
olower than V
ref, and I
lwhen dropping to 0, control SW1 conducting, SW2 disconnects.
embodiment 4
Fig. 5 is the circuit diagram of the embodiment 4 of DCDC of the present invention boosting variator.
The present embodiment has done further improvement on the basis of embodiment 1, inductive current comparator 222 is replaced with a fixing ON time Constantontime timer 224, timer 224 is used for controlling the ON time of SW1 in each work period, to keep inductive current.
The ON time of SW1 and foregoing I
refbetween have following relation: I
ref=V
bat* T
on, sw1/ L
The function of the inductive current zero-crossing comparator 221 in embodiment 4 remains to be responsible for detecting inductive current I
lwhether be 0, if inductive current I detected
lwhen being decreased to 0, then sending signal to control unit 210 and make to disconnect from interrupteur SW 2, prevent inductive current oppositely from V
oflow to V
bATthus cause loss of charge.
The each unit of control circuit of the present invention all adopts integrated circuit (IC)-components to make, greatly can reduce assembling and maintenance cost, compared to traditional control model, effectively simplify system configuration, for the change of load current, can make rapidly corresponding, effectively reduce the ripple size of output voltage VO when load current changes.
As current-mode pulse width modulation and traditional mode simulation result comparison diagram that Fig. 6 is DCDC of the present invention boosting variator.Visible in Fig. 6, load current in the 600us moment from 1mA saltus step to 10mA, traditional mode due to system response speed slower, cause ripple voltage output voltage creating about 100mV, and the present invention can detect rapidly the output voltage change caused due to load current saltus step, and then adjustment switching frequency makes the mean value of inductive current follow load current saltus step immediately, thus output voltage is made to there is no the generation of obvious ripple voltage.
About the peak current comparator adopted in the embodiment of the present invention, current over-zero comparator and output voltage comparator, it can shown in Figure 7ly be a kind of embodiment of peak current comparator PeakCurrentComparator, it adopts three grades of comparator cascade structures, the gain in order to optimize comparator and speed, wherein V
dDfor the supply voltage of system, GND is earth terminal, V
bfor internal system bias voltage, I
reffor reference current input, I
lfor inductive current input, Vo is the output voltage of comparator.Be illustrated in figure 8 a kind of embodiment of current over-zero comparator ZCDComparator, wherein I
reffor reference current input, the another one input end grounding of comparator, Vo is the output voltage of comparator.Be illustrated in figure 9 a kind of embodiment of output voltage comparator VoComparator, wherein V
reffor reference voltage input terminal, Vo is the output voltage of converter, and Voc is the output voltage of comparator.
It should be noted that above-described embodiment is example and unrestricted the present invention; in such as above-described embodiment; free matched combined is carried out in the restriction that the different structure of inductive current holding unit 220 and output voltage comparing unit 230 can break through above embodiment; as long as object of the present invention can be realized, all should in scope.
Claims (10)
1. a current-mode control DCDC boosting variator, adopts integrated circuit (IC)-components to make, it is characterized in that: described DCDC boosting variator comprises a DCDC booster circuit and coupled control circuit; Described booster circuit comprises DC power supply, inductance, load, main switch SW1 and from interrupteur SW 2; Described control circuit comprises control unit, inductive current holding unit and output voltage comparing unit; Wherein:
Described control unit receives the signal that described inductive current holding unit and described output voltage comparing unit are sent, and to boost variator main switch SW1 and send the control signal be turned on or off from interrupteur SW 2 to DCDC, to ensure that DCDC boosts the normal work of variator;
Described inductive current holding unit, controls the ON time of main switch SW1 in each work period so that by described inductive current I
lremain on 0 ~ I
refbetween, wherein I
reffor reference current; Also I detected simultaneously
lwhen being decreased to 0, sending signal to described control unit and make to disconnect from interrupteur SW 2, prevent inductive current from oppositely causing loss of charge from load flow to power supply;
Described output voltage comparing unit, compares output voltage V
owith reference voltage V
refsize, and comparison signal is exported to described control unit;
Above-mentioned three unit collaborative works, in the beginning of a work period, main switch SW1 disconnects from interrupteur SW 2 conducting, when described inductive current holding unit detects I
lbe decreased to 0 gradually and described output voltage comparing unit detects output voltage V
obe reduced to V
reftime, main switch SW1 conducting disconnects from interrupteur SW 2 and makes I
lgo up gradually; When described inductive current holding unit detects I
lrise to I
reftime, main switch SW1 disconnects, and from interrupteur SW 2 conducting, the above course of work is gone round and begun again and constantly continued, by output voltage V
obe stabilized in reference voltage V
refnear.
2. current-mode control DCDC boosting variator as claimed in claim 1, is characterized in that: described output voltage comparing unit at least comprises an output voltage comparator, for comparing output voltage V
owith reference voltage V
refsize.
3. current-mode control DCDC boosting variator as claimed in claim 2, is characterized in that: described output voltage comparing unit also comprises an error amplifier and a building-out capacitor, to make V
oaccurately equal V
ref.
4. current-mode control DCDC boosting variator as claimed in claim 2 or claim 3, is characterized in that: described inductive current holding unit comprises an inductive current comparator and an inductive current zero-crossing comparator, and described inductive current comparator compares inductive current I
lwith reference current I
refsize, and comparison signal is exported to described control unit; Described inductive current zero-crossing comparator is once inductive current I be detected
lbe decreased to 0, then send signal to described control unit and make to disconnect from interrupteur SW 2, to prevent inductive current oppositely from V
oflow to V
bATthus cause loss of charge.
5. as claimed in claim 2 or claim 3 current-mode controls DCDC boosting variator, is characterized in that: described inductive current holding unit comprises a current comparator with two interrupteur SW 3 and SW4, and wherein SW3 is connected with 0 electric current, SW4 and reference current I
refbe connected, compare inductive current I by the on-off of SW3 and SW4
lwith reference current I
refsize and comparison signal exported to described control unit and detect inductive current I
lwhen dropping to 0, send signal to described control unit and make to disconnect from interrupteur SW 2, to prevent inductive current oppositely from V
oflow to V
bATthus cause loss of charge.
6. current-mode control DCDC boosting variator as claimed in claim 2 or claim 3, it is characterized in that: described inductive current holding unit comprises a fixing ON time timer and an inductive current zero-crossing comparator, described fixing ON time timer controls the ON time of main switch SW1 in each work period, to keep described inductive current; Described inductive current zero-crossing comparator is once I detected
lwhen being decreased to 0, sending signal to described control unit and make to disconnect from interrupteur SW 2, prevent inductive current from oppositely causing loss of charge from load flow to power supply.
7. current-mode control DCDC boosting variator as claimed in claim 1, is characterized in that: the ON time T of main switch SW1
on, sw1with reference current I
refbetween have following relation: I
ref=V
bat* T
on, sw1/ L
Wherein I
reffor reference current, V
batfor input voltage, T
on, sw1for the ON time of main switch SW1, L is inductance value;
Reference current I
refwith the electric current I flowing through load
loadrelation need meet:
I
ref>2*I
load*V
o/V
bat；
The operating frequency of system is:
8. current-mode control DCDC boosting variator as claimed in claim 1, is characterized in that: each unit of described control circuit all adopts production of integrated circuits.
9. a pulse frequency modulated method for current-mode control DCDC boosting variator, adopts the current-mode control DCDC boosting variator as described in claim 1 to 8, it is characterized in that:
In the beginning of a work period, main switch SW1 disconnects from interrupteur SW 2 conducting, when described inductive current holding unit detects I
lbe decreased to 0 gradually and described output voltage comparing unit detects output voltage V
obe reduced to V
reftime, main switch SW1 conducting disconnects from interrupteur SW 2 and makes I
lgo up gradually; When described inductive current holding unit detects I
lrise to I
reftime, main switch SW1 disconnects, and from interrupteur SW 2 conducting, the above course of work is gone round and begun again and constantly continued, by output voltage V
obe stabilized in reference voltage V
refnear;
In the above-mentioned course of work, described inductive current holding unit is once I be detected
lwhen being decreased to 0, namely sending signal to described control unit and make to disconnect from interrupteur SW 2, prevent inductive current from oppositely causing loss of charge from load flow to power supply.
10. method as claimed in claim 9, is characterized in that: the ON time T of main switch SW1
on, sw1with reference current I
refbetween have following relation: I
ref=V
bat* T
on, sw1/ L
Wherein I
reffor reference current, V
batfor input voltage, T
on, sw1for the ON time of main switch SW1, L is inductance value;
Reference current I
refwith the electric current I flowing through load
loadrelation need meet:
I
ref>2*I
load*V
o/V
bat；
The operating frequency of system is:
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| CN110212902A (en) * | 2019-06-28 | 2019-09-06 | 成都信息工程大学 | A kind of electrification reset circuit |
| CN111788767A (en) * | 2018-03-30 | 2020-10-16 | 德克萨斯仪器股份有限公司 | Timer for creating a stable on-time |
| CN114726208A (en) * | 2022-05-07 | 2022-07-08 | 电子科技大学 | PWM control circuit of peak current mode buck converter |
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| Publication number | Publication date |
|---|---|
| CN105490534B (en) | 2018-08-21 |
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