CN202818138U - Inverter device for prolonging service life of DC distributed power supply - Google Patents
Inverter device for prolonging service life of DC distributed power supply Download PDFInfo
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- CN202818138U CN202818138U CN 201220403033 CN201220403033U CN202818138U CN 202818138 U CN202818138 U CN 202818138U CN 201220403033 CN201220403033 CN 201220403033 CN 201220403033 U CN201220403033 U CN 201220403033U CN 202818138 U CN202818138 U CN 202818138U
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Abstract
The utility model provides an inverter device for prolonging the service life of a DC distributed power supply, which comprises a DC distributed power supply, a differential inverter, a controller, a first converter control module, a second converter control module and an anti-DC magnetic bias module, wherein the controller inputs output voltage, output current and capacitance of a first differential capacitor and a second differential capacitor, and outputs reference values of the first differential capacitor voltage and the second differential capacitor voltage and a direct current part reference value of the output current; the anti-DC magnetic bias module inputs the direct current part reference value of the output current and the output current; the first converter control module inputs the first reference value of the first differential capacitor voltage, the first differential capacitor voltage, first inductive current, and output signals of the anti-DC magnetic bias module; an output end of the first converter control module is connected to a switching transistor driving circuit of a first converter; and the structure of the second converter control module corresponds to that of the first converter control module. According to the utility model, the differential inverter is adopted, and the effect of prolonging the service life of the power supply is achieved through restraining low frequency current ripples.
Description
Technical field
The utility model belongs to the direct-current-alternating-current converter technical field in the electrical energy changer, is specifically related to a kind of inverter that prolongs direct current distributed electrical source service life.
Background technology
The direct current such as solar energy and fuel cell distributed power source is widely used in portable set, electric automobile and the distributed generation systems such as notebook.Belong to direct current supply to powering portable devices, and be applied to electric automobile or distributed generation system belongs to ac power supply system.When being applied to ac power supply system, the alternating current of 50Hz can produce in the output dc terminal of distributed power source the ripple of 100Hz, and this ripple can cause system's output characteristic hysteresis phenomenon to occur, threatens the safe operation of direct current distributed power source.Meanwhile, the low-frequency ripple electric current of 100Hz also can cause its power supplying efficiency low.Therefore, suppressing the low-frequency ripple electric current is an important research direction that prolongs direct current distributed electrical source service life.
Direct voltage wider range of direct current distributed power source output, as adopt traditional single stage semi-bridge or full-bridge inverter directly to realize power conversion, although its mapped structure is succinct, power output end low-frequency current ripple is large.In order to suppress the low-frequency ripple electric current, need to be at distributed electrical source output terminal jumbo electrochemical capacitor in parallel, storage battery or access active filter, although establishment the low-frequency ripple electric current, electrochemical capacitor, storage battery and active filter can increase system cost.In addition, use in a large number electrochemical capacitor also can affect the useful life of system.Because lower grade of direct current distributed power source output voltage, need to add the duplex frequency boostering transformer of volume heaviness based on the electric power system of single-stage inverter.In order to save Industrial Frequency Transformer, can add one-level DC/DC converter at its output.The direct current that the DC/DC converter is exported power supply boosts and is stabilized in rational magnitude of voltage, and the rear class inverter is high-quality alternating current with this voltage transitions.Although adopt the electric power system of two-stage type to simplify the control of inverter, the low-frequency ripple electric current of direct current distributed electrical source output terminal does not improve, and still need to suppress the low-frequency ripple electric current by means of electrochemical capacitor, storage battery or active filter.Also the someone proposes the low-frequency ripple electric current that the active control technology of prime DC/DC converter using suppresses direct current distributed electrical source output terminal.The inverter input side voltage fluctuation of capacitor of this method is large, changes with the voltage fluctuation of inverter input side for preventing direct current distributed power source output current, the bandwidth of DC/DC converter current ring need to be controlled at below the 100Hz.Although establishment the low-frequency ripple electric current of direct current distributed power source output, but inverter input side voltage fluctuation conference increases the control difficult point of rear class inverter output voltage harmonic wave, in case load is undergone mutation, just can reach stable through several power frequency periods, dynamic performance is poor.
The utility model content
The technical problems to be solved in the utility model is: a kind of inverter that prolongs direct current distributed electrical source service life is provided.
The utility model is to solve the problems of the technologies described above the technical scheme of taking to be: a kind of inverter that prolongs direct current distributed electrical source service life, comprise direct current distributed power source, the first converter and the second converter, wherein the direct current distributed power source respectively with the first converter be connected converter and be connected, the first converter comprises the first differential capacitance C1, the first inductance L 1 and switching tube, the second converter comprises the second differential capacitance C2, the second inductance L 2 and switching tube, the symmetrical configuration of first, second converter; The output of this inverter is by first, second differential capacitance C1, C2 series connection, and output voltage is the difference of the voltage of two differential capacitances; It is characterized in that:
It also comprises control circuit, and control circuit comprises controller, the first converter control module, the second converter control module and anti-DC-bias module; The input of controller is inputted the capacitance of output voltage, output current and first, second differential capacitance C1, the C2 of this inverter, and the output of controller is exported the capacitance voltage reference value V of the one the second differential capacitance C1, C2
C1ref, V
C2refWith output current direct current component reference value; Input input and output current DC partial reference value and the output current of anti-DC-bias module; The input of the first converter control module is inputted the capacitance voltage reference value V of the first differential capacitance C1
C1ref, the capacitance voltage of the first differential capacitance C1, the inductive current of the first inductance L 1 and the output signal of anti-DC-bias module, the output of the first converter control module is connected with the switch tube driving circuit of described the first converter; The input of the second converter control module is inputted the capacitance voltage reference value V of the second differential capacitance C2
C2ref, the capacitance voltage of the second differential capacitance C2, the inductive current of the second inductance L 2 and the output signal of anti-DC-bias module, the output of the second converter control module is connected with the switch tube driving circuit of described the second converter.
Press such scheme, described the first converter and the second converter are booster converter, and symmetrical configuration; Wherein the first converter comprises the first differential capacitance C1, the first inductance L 1, the first switch transistor T 1 and second switch pipe T2, one end of the first inductance L 1 is connected with described direct current distributed power source is anodal, the other end of the first inductance L 1 is connected input with the output of the first switch transistor T 1 respectively and is connected with second switch pipe T2, connect the first differential capacitance C1 between the output of the input of the first switch transistor T 1 and second switch pipe T2, and the input of the first switching tube connects with the anodal negative pole that is connected of described direct current distributed power source; The control end of the first switch transistor T 1 and second switch pipe T2 is controlled by switch tube driving circuit by the output of the first converter control module respectively.
Press such scheme, described the first converter control module comprise in turn connect with V
C1refWith I
dThe adder of addition, with v
C1Carry out first error amplifier, the first proportional and integral controller of error computing with adder output signal, with i
L1Carry out second error amplifier, the second proportional and integral controller of error computing and the comparator that the second proportional and integral controller and sawtooth waveforms are compared with the first proportional and integral controller output signal; Described the first proportional and integral controller be connected the output of proportional and integral controller and connect respectively two diodes.
Press such scheme, described the second converter control module comprise in turn connect with V
C2refAnd I
dSubtract each other subtracter, with v
C2Carry out the 3rd error amplifier, the 3rd proportional and integral controller of error computing with the subtracter output signal, with i
L2Carry out the 4th error amplifier, the 4th proportional and integral controller of error computing and the comparator that the 4th proportional and integral controller and sawtooth waveforms are compared with the 3rd proportional and integral controller output signal; The output of described the 3rd proportional and integral controller and the 4th proportional and integral controller connects respectively two diodes.
Press such scheme, described anti-DC-bias module comprise in turn connect with output current I
oThe 5th error amplifier and the 5th proportional and integral controller that obtain the low pass filter of direct current, output current direct current component reference value and low-pass filter output signal are carried out the error computing through filtering; The output of the 5th proportional and integral controller connects two diodes that the output regulated quantity carried out amplitude limit.
The beneficial effects of the utility model are: compared with prior art, technical characteristics of the present utility model is, adopt the difference inverter, utilize simultaneously the ripple control scheme, when dwindling direct current distributed power source inversion system volume, reached again the inhibition of good low-frequency current ripple.The control method of carrying is to allow the electric capacity of boost inverter output end that pulsating power is provided, the direct current average power then has dc output end to provide, the low-frequency ripple impact of direct current distributed power source can be minimized like this, thus the life-span of improving the direct current distributed power source; When adopting the difference inverter, also removed short electrochemical capacitor in useful life.
Description of drawings
Fig. 1 is structured flowchart of the present utility model.
Fig. 2 is main circuit topological structure figure and the control block diagram of the utility model one embodiment.
Fig. 3 is the circuit diagram of the first converter control module among Fig. 2.
Fig. 4 is the circuit diagram of the second converter control module among Fig. 2.
Fig. 5 is the circuit diagram of D.C. magnetic biasing module among Fig. 2.
Fig. 6 is in the experiment of pure resistive load, does not adopt the difference boosting inverter capacitance voltage V of the utility model structure
C1, V
C2And output voltage v
0With load current i
0Waveform.
Fig. 7 is in the experiment of pure resistive load, does not adopt the difference boosting inverter inductive current i of the utility model structure
L1, i
L2And input current i
InWaveform.
Fig. 8 is in the experiment of pure resistive load, adopts the difference boosting inverter capacitance voltage V of the utility model structure
C1, V
C2And output voltage v
0With load current i
0Waveform.
Fig. 9 is in the experiment of pure resistive load, adopts the difference boosting inverter inductive current i of the utility model structure
L1, i
L2, and the waveform i of input current
In
Embodiment
Below in conjunction with the drawings and specific embodiments, further illustrate the present invention, should understand that these embodiment only are used for explanation the present invention and need not with limit the scope of the invention, after having read the present invention, those skilled in the art all fall within the application's claims limited range to the modification of the various equivalent form of values of the present invention.
Fig. 1 is structured flowchart of the present utility model, and the difference inverter refers to output by two capacitor C 1, C2 series connection, and output voltage is two capacitance voltage V
C1, V
C2The inverter of difference, the difference inverter of arbitrary form all can be used for realizing the utility model effect.
In the present embodiment, what select is the difference boosting inverter, as shown in Figure 2, comprises direct current distributed power source 1, the first converter 2 and the second converter 3.The first converter 2 comprises the first differential capacitance C1, the first inductance L 1, the first switch transistor T 1 and second switch pipe T2, one end of the first inductance L 1 is connected with described direct current distributed power source is anodal, the other end of the first inductance L 1 is connected input with the output of the first switch transistor T 1 respectively and is connected with second switch pipe T2, connect the first differential capacitance C1 between the output of the input of the first switch transistor T 1 and second switch pipe T2, and the input of the first switching tube connects with the anodal negative pole that is connected of described direct current distributed power source; The control end of the first switch transistor T 1 and second switch pipe T2 is controlled by switch tube driving circuit by the output of the first converter control module respectively.The second converter 3 and the first transformer configuration are symmetrical, corresponding the second differential capacitance C2, the second inductance L 2, the 3rd switch transistor T 3 and the 4th switch transistor T 4 of comprising.
It also comprises control circuit 4, and control circuit 4 comprises controller, the first converter control module, the second converter control module and anti-DC-bias module; The input of controller is inputted the output voltage V of this inverter
0, output current I
0With the capacitance C of first, second differential capacitance C1, C2, the output of controller is exported the capacitance voltage reference value V of first, second differential capacitance C1, C2
C1ref, V
C2refWith output current direct current component reference value, output current direct current component reference value is 0; Input input and output current DC partial reference value and the output current I of anti-DC-bias module
0The input of the first converter control module is inputted the capacitance voltage reference value V of the first differential capacitance C1
C1ref, the first differential capacitance C1 capacitance voltage V
C1, the first inductance L 1 inductive current I
L1With the output signal of anti-DC-bias module, the output of the first converter control module is exported driving signal d1, the d2 of the first switch transistor T 1 and second switch pipe T2; The input of the second converter control module is inputted the capacitance voltage reference value V of the second differential capacitance C2
C2ref, the second differential capacitance C2 capacitance voltage V
C2, the second inductance L 2 inductive current I
L2With the output signal of anti-DC-bias module, the output of the second converter control module is exported driving signal d3, the d4 of the 3rd switch transistor T 3 and the 4th switch transistor T 4.
The physical circuit of the first converter control module consists of adder by R1, R2, R3, R4, R5 and the first operational amplifier U1, as shown in Figure 3 with V
C1refAnd I
dAddition passes to rear one-level amplifier; Consist of the first error amplifier by R6, R7, R8, R9 and the second operational amplifier U2, with v
C1Carry out the error computing with the output of previous stage amplifier, pass to rear one-level amplifier; Consist of the first proportional and integral controller by R10, R11, R12, C3 and the 3rd operational amplifier U3, its output connects two diodes, and its output regulated quantity is carried out amplitude limit; Consist of the second error amplifier by R13, R14, R15, R16 and four-operational amplifier U4, with i
L1Carry out the error computing with the output of previous stage amplifier, pass to rear one-level amplifier; Consist of the second proportional and integral controller by R17, R18, R19, C4 and the 5th operational amplifier U5, its output connects two diodes, and its output regulated quantity is carried out amplitude limit; Compare by the first comparator U6 and sawtooth waveforms afterwards, produce PWM ripple d1 and control the first switch transistor T 1, produce PWM ripple d2 control second switch pipe T2 by inverter.
The physical circuit of the second converter control module consists of subtracter by R20, R21, R22, R23 and the 7th operational amplifier U7, as shown in Figure 4 with V
C2refAnd I
dSubtract each other and pass to rear one-level amplifier; Consist of the 3rd error amplifier by R24, R25, R26, R27 and the 8th operational amplifier U8, with v
C2Carry out the error computing with the output of previous stage amplifier, pass to rear one-level amplifier; Consist of the 3rd proportional and integral controller by R28, R29, R30, C5 and the 9th operational amplifier U9, its output connects two diodes, and its output regulated quantity is carried out amplitude limit; Consist of the 4th error amplifier by R31, R32, R33, R34 and the tenth operational amplifier U10, with i
L2Carry out the error computing with the output of previous stage amplifier, pass to rear one-level amplifier; Consist of the 4th proportional and integral controller by R35, R36, R137, C6 and the 11 operational amplifier U11, its output connects two diodes, and its output regulated quantity is carried out amplitude limit; Compare by the second comparator U12 and sawtooth waveforms afterwards, produce PWM ripple d3 and control the 3rd switch transistor T 3, produce PWM ripple d4 by inverter and control the 4th switch transistor T 4.
The physical circuit of D.C. magnetic biasing module as shown in Figure 5, consist of the 5th error amplifier by R39, R40, R41 and the 13 operational amplifier U13, with 0(output current direct current component reference value) carry out the error computing with the output of previous stage amplifier, pass to rear one-level amplifier; Consist of the 5th proportional and integral controller by R42, R43, R44, C8 and the tenth four-operational amplifier U14, its output connects two diodes, and its output regulated quantity is carried out amplitude limit.
Operation principle of the present utility model is: detect inverter output voltage, electric current v
o, i
oBe v in order to satisfy inversion outputting standard sine wave voltage at first
o=v
C1-v
C2=V
MaxSin (ω t), v
C1, v
C2Be respectively the capacitance voltage of first, second differential capacitance, V
MaxSin (ω t) is v
oExpression formula, V
MaxBe v
oAmplitude;
Making up the differential capacitance voltage waveform is:
The dc offset voltage V on the differential capacitance wherein
dMust satisfy:
V
InBe system's DC input voitage, B and
Be secondary ripple voltage amplitude and phase place;
Calculate direct current input current i
InFor:
Wherein, I
MaxBe the output current i of system
oAmplitude, contain flip-flop in the direct current input current waveform
The quadruple composition
And two frequency multiplication composition
When two frequency multiplication component i
In (2 ω)=0The time, then no longer contain two frequency multiplication compositions in the direct current input current;
Namely
With B and
Substitution formula (1) and (2) just can obtain the differential voltage waveform that can realize that low-frequency ripple suppresses.
Concrete experimental verification
The below is to carrying out experimental verification based on differential type inversion system of the present invention, and wherein the direct current distributed power source is fuel cell.
The specific design parameter is as shown in table 1
Table 1
| Input voltage V in | 90V |
| Output voltage (effective value) | 110V |
| Rated power P e | 150W |
| Fundamental frequency f | 50HZ |
| Switching frequency f s | 20kHZ |
| Inductance (L1, L2) | 300μH，10A |
| Electric capacity (C1, C2) | 15μF，800V |
| Switching tube (T1, T2, T3, T4) | Infineon IGBT BSM50GB120DN2 module |
As known from Table 1, two inductance L 1 and L2 type selecting are 300 μ H 10A inductance.Capacitor C 1 and C2 select behavior 15 μ H, 800V.Rated power P
eBe 150W, input voltage V
InBe 90V, the effective value of output voltage is 110V, switching frequency f
sFor 20kHZ and fundamental frequency f are 50HZ.
Reference voltage v
C1=201+77.75sin (ω t)+33sin (2 ω t+0.2801), v
C2=201-77.75 sin (ω t)+33sin (2 ω t+0.2801), boosting inverter (being the boost inverter) uses two Infineon IGBT modules.What drive that chip adopts is M57962L chip with light-coupled isolation.
Fig. 6 is in the experiment of pure resistive load, does not adopt the difference boosting inverter capacitance voltage V of the utility model structure
C1, V
C2And output voltage v
0With load current i
0Waveform.Trace1 represents v
C1, Trace2 represents v
C2, Trace3 represents V
oIt has proved can obtain required output voltage, and it is to be made of different capacitance voltages, and its capacitance voltage comprises sinusoidal waveform and the identical direct current biasing amount of two groups of phase phasic difference pi.
Fig. 7 is in the experiment of pure resistive load, does not adopt the difference boosting inverter inductive current i of the utility model structure
L1, i
L2And input current i
InWaveform.Trace1 represents i
L1, Trace2 represents i
L2, Trace3 represents i
InIts proof input current is the direct current biasing with the 100Hz ripple.
Fig. 8 is in the experiment of pure resistive load, adopts the difference boosting inverter capacitance voltage V of the utility model structure
C1, V
C2And output voltage v
0With load current i
0Waveform.Trace1 represents v
C1, Trace2 represents v
C2, Trace3 represents v
0, Trace4 represents i
0Its proof can obtain the required output voltage with power factor, and its capacitance voltage comprises sinusoidal waveform and the identical direct current biasing amount of two groups of phase phasic difference pi.
Fig. 9 is in the experiment of pure resistive load, adopts the difference boosting inverter inductive current i of the utility model structure
L1, i
L2And input current i
InWaveform.Trace1 represents i
L1, Trace2 represents i
L2, Trace3 represents i
InIts proved adopt the utility model structure can be with the amplitude limitation of 100Hz input ripple current DC component 10% in, can improve systematic function like this.
Claims (5)
1. inverter that prolongs direct current distributed electrical source service life, comprise direct current distributed power source, the first converter and the second converter, wherein the direct current distributed power source respectively with the first converter be connected converter and be connected, the first converter comprises the first differential capacitance C1, the first inductance L 1 and switching tube, the second converter comprises the second differential capacitance C2, the second inductance L 2 and switching tube, the symmetrical configuration of first, second converter; The output of this inverter is by first, second differential capacitance C1, C2 series connection, and output voltage is the difference of the voltage of two differential capacitances; It is characterized in that:
It also comprises control circuit, and control circuit comprises controller, the first converter control module, the second converter control module and anti-DC-bias module; The input of controller is inputted the capacitance of output voltage, output current and first, second differential capacitance C1, the C2 of this inverter, and the output of controller is exported the capacitance voltage reference value V of first, second differential capacitance C1, C2
C1ref, V
C2refWith output current direct current component reference value; Input input and output current DC partial reference value and the output current of anti-DC-bias module; The input of the first converter control module is inputted the capacitance voltage reference value V of the first differential capacitance C1
C1ref, the capacitance voltage of the first differential capacitance C1, the inductive current of the first inductance L 1 and the output signal of anti-DC-bias module, the output of the first converter control module is connected with the switch tube driving circuit of described the first converter; The input of the second converter control module is inputted the capacitance voltage reference value V of the second differential capacitance C2
C2ref, the capacitance voltage of the second differential capacitance C2, the inductive current of the second inductance L 2 and the output signal of anti-DC-bias module, the output of the second converter control module is connected with the switch tube driving circuit of described the second converter.
2. the inverter of prolongation direct current distributed electrical source service life according to claim 1, it is characterized in that: described the first converter and the second converter are booster converter, and symmetrical configuration; Wherein the first converter comprises the first differential capacitance C1, the first inductance L 1, the first switch transistor T 1 and second switch pipe T2, one end of the first inductance L 1 is connected with described direct current distributed power source is anodal, the other end of the first inductance L 1 is connected input with the output of the first switch transistor T 1 respectively and is connected with second switch pipe T2, connect the first differential capacitance C1 between the output of the input of the first switch transistor T 1 and second switch pipe T2, and the input of the first switching tube connects with the anodal negative pole that is connected of described direct current distributed power source; The control end of the first switch transistor T 1 and second switch pipe T2 is controlled by switch tube driving circuit by the output of the first converter control module respectively.
3. the inverter of prolongation direct current distributed electrical source service life according to claim 1 and 2 is characterized in that: described the first converter control module comprise connect in turn with V
C1refWith I
dThe adder of addition, with v
C1Carry out first error amplifier, the first proportional and integral controller of error computing with adder output signal, with i
L1Carry out second error amplifier, the second proportional and integral controller of error computing and the comparator that the second proportional and integral controller and sawtooth waveforms are compared with the first proportional and integral controller output signal; Described the first proportional and integral controller be connected the output of proportional and integral controller and connect respectively two diodes.
4. the inverter of prolongation direct current distributed electrical source service life according to claim 1 and 2 is characterized in that: described the second converter control module comprise connect in turn with V
C2refAnd I
dSubtract each other subtracter, with v
C2Carry out the 3rd error amplifier, the 3rd proportional and integral controller of error computing with the subtracter output signal, with i
L2Carry out the 4th error amplifier, the 4th proportional and integral controller of error computing and the comparator that the 4th proportional and integral controller and sawtooth waveforms are compared with the 3rd proportional and integral controller output signal; The output of described the 3rd proportional and integral controller and the 4th proportional and integral controller connects respectively two diodes.
5. the inverter of prolongation direct current distributed electrical source service life according to claim 1 and 2 is characterized in that: described anti-DC-bias module comprise connect in turn with output current I
oThe 5th error amplifier and the 5th proportional and integral controller that obtain the low pass filter of direct current, output current direct current component reference value and low-pass filter output signal are carried out the error computing through filtering; The output of the 5th proportional and integral controller connects two diodes that the output regulated quantity carried out amplitude limit.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 201220403033 CN202818138U (en) | 2012-08-15 | 2012-08-15 | Inverter device for prolonging service life of DC distributed power supply |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 201220403033 CN202818138U (en) | 2012-08-15 | 2012-08-15 | Inverter device for prolonging service life of DC distributed power supply |
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| Publication Number | Publication Date |
|---|---|
| CN202818138U true CN202818138U (en) | 2013-03-20 |
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN 201220403033 Expired - Lifetime CN202818138U (en) | 2012-08-15 | 2012-08-15 | Inverter device for prolonging service life of DC distributed power supply |
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109842317A (en) * | 2017-11-24 | 2019-06-04 | 国网山东省电力公司济宁供电公司 | A kind of differential converter and its application based on Boost and Buck-Boost circuit |
| CN110806522A (en) * | 2019-11-12 | 2020-02-18 | 天津津航计算技术研究所 | Arc signal detection conditioning circuit |
| TWI696343B (en) * | 2017-12-20 | 2020-06-11 | 美商格芯（美國）集成電路科技有限公司 | Methods, apparatus, and system for a frequency doubler for a millimeter wave device |
-
2012
- 2012-08-15 CN CN 201220403033 patent/CN202818138U/en not_active Expired - Lifetime
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109842317A (en) * | 2017-11-24 | 2019-06-04 | 国网山东省电力公司济宁供电公司 | A kind of differential converter and its application based on Boost and Buck-Boost circuit |
| TWI696343B (en) * | 2017-12-20 | 2020-06-11 | 美商格芯（美國）集成電路科技有限公司 | Methods, apparatus, and system for a frequency doubler for a millimeter wave device |
| CN110806522A (en) * | 2019-11-12 | 2020-02-18 | 天津津航计算技术研究所 | Arc signal detection conditioning circuit |
| CN110806522B (en) * | 2019-11-12 | 2022-02-22 | 天津津航计算技术研究所 | Arc signal detection conditioning circuit |
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