CN201418040Y - Driving circuit of synchronous rectifying tube - Google Patents
Driving circuit of synchronous rectifying tube Download PDFInfo
- Publication number
- CN201418040Y CN201418040Y CN2009201356200U CN200920135620U CN201418040Y CN 201418040 Y CN201418040 Y CN 201418040Y CN 2009201356200 U CN2009201356200 U CN 2009201356200U CN 200920135620 U CN200920135620 U CN 200920135620U CN 201418040 Y CN201418040 Y CN 201418040Y
- Authority
- CN
- China
- Prior art keywords
- synchronous rectifier
- shutoff
- output
- circuit
- signal
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Fee Related
Links
Images
Landscapes
- Rectifiers (AREA)
Abstract
The utility model provides a driving circuit of a synchronous rectifying tube, which comprises the following components: a shutoff pretreatment circuit which is used for obtaining a detecting signal from a drain of the synchronous rectifying tube and comparing the signal with the first standard voltage for generating a pre-shutoff signal; and a zero-crossing comparing amplifying circuit which is connected with the output end of the shutoff pretreatment circuit for collecting a source signal of the synchronous rectifying tube and comparing the signal with the second standard voltage. When the source signal is larger than the summation of the standard voltage and the voltage between the drains, a conducting driving electric signal of the synchronous rectifying tube is output so that the synchronous rectifying tube is in a saturated state; When the source signal is smaller than the summation of the standard voltage and the voltage between the drains, and the pre-shutoff signal is receivedthrough the control end, the pre-shutoff driving electric signal of the pre-shutoff of the synchronous rectifying tube is output so that the synchronous rectifying tube is in an unsaturated state. The driving circuit of a synchronous rectifying tube provided by the utility model can provides a pre-shutoff processing process thereby shortening the shutoff time of the synchronous tube.
Description
Technical field
The utility model relates to a kind of control circuit of power supply, specifically, relates to a kind of drive circuit of synchronous rectifier.
Background technology
At present, the main synchronous rectification that has been extensive use of replaces traditional diode rectifier in the power supply of the big stream output of low pressure, to improve power-efficient, energy savings.What but traditional synchronous rectification had will use the process auxiliary drive winding, and what have will make current transformer, the use that has integrated circuit, integrated numerous element, the cost height, control is complicated, and in using limitation is arranged, can't realize synchronous rectification all topological structures.
The utility model content
The utility model provides a kind of drive circuit of synchronous rectifier, and it can provide pre-shutoff processing procedure, thereby has shortened the turn-off time of synchronous rectifier.
To achieve these goals, the utility model adopts following technical scheme:
The utility model provides a kind of drive circuit of synchronous rectifier, and it comprises: turn-off pre-process circuit, be used for obtaining detection signal from the drain electrode of synchronous rectifier, and this signal is compared with first normal voltage, result from pre-cut-off signals; The zero balancing amplifying circuit excessively that links to each other with described shutoff pre-process circuit output, be used to gather the source signal of described synchronous rectifier, and this signal compared with second normal voltage, during the voltage sum, the conducting of exporting described synchronous rectifier drives the signal of telecommunication makes described synchronous rectifier be in saturation condition between described source signal is greater than described normal voltage and drain-source; Between described source signal is less than described normal voltage and drain-source during the voltage sum, and when receiving described pre-cut-off signals, exports the pre-pre-shutoff of turn-offing of described synchronous rectifier and drive the signal of telecommunication and makes described synchronous rectifier be in unsaturated state by control end.
The utility model effect: the utility model adopts exclusive shutoff preliminary treatment circuit, the turn-off time of prediction synchronous rectifier, before turn-offing, synchronous rectifier earlier the control voltage of synchronous rectifier is reduced to a reduced levels, prepare for turn-offing synchronous rectifier, when the current over-zero of synchronous rectifier, can rapidly synchronous rectifier be turn-offed, shortened the turn-off time greatly, reverse current is little.Exclusive zero-crossing switching circuit just turn-offs synchronous rectifier when the synchronous rectification tube current reaches zero point, and the shutoff sequential is accurate, does not have diode current flow problem in the synchronous rectification body, need not extra Schottky in parallel.The utility model is applied widely, is not only applicable to the synchronous rectification of continuous current mode, also can be used for the synchronous rectification of the critical and electric current non-continuous mode of electric current.
Description of drawings
Fig. 1 is the utility model electrical block diagram;
Fig. 2 is the utility model one embodiment electrical block diagram;
Fig. 3 is the another embodiment electrical block diagram of the utility model;
Fig. 4 is a circuit each several part operating voltage oscillogram of the present utility model.
Embodiment
Describe specific implementation of the present utility model in detail below with reference to accompanying drawing.
As shown in Figure 1, the drive circuit of a kind of synchronous rectifier that the utility model provides, it mainly comprises following two parts:
1, turn-offs pre-process circuit 300, be used for obtaining detection signal, and this signal is compared with the first normal voltage V1, result from pre-cut-off signals from the drain electrode of synchronous rectifier T1;
2, cross zero balancing amplifying circuit 100, it links to each other with the output that turn-offs pre-process circuit 300, be used to gather the source signal of described synchronous rectifier T1, and this signal compared with the second normal voltage V2, during the voltage sum, the conducting of output synchronous rectifier T1 drives the signal of telecommunication makes synchronous rectifier T1 be in saturation condition between described source signal is greater than described normal voltage V2 and drain-source; Between described source signal is less than described normal voltage V2 and drain-source during the voltage sum, and when receiving described pre-cut-off signals by control end, the pre-pre-shutoff of turn-offing of output synchronous rectifier T1 drives the signal of telecommunication makes described synchronous rectifier T1 be in unsaturated state, comprises off state or magnifying state.
Compared with prior art, the utility model was by realizing collection to the source signal of synchronous rectifier T1 from increasing zero balancing amplifying circuit 100, and acquisition corresponding driving signal, in order to guarantee that circuit can be stably turn-offs rapidly when the current over-zero, then also increase by one and turn-offed pre-process circuit 300, be used to produce pre-cut-off signals, the controlling and driving signal makes synchronous rectifier T1 be in unsaturated state, comprises off state or magnifying state.
As shown in Figure 1, the shutoff pre-process circuit 300 here comprises: comparator A2, integrating capacitor C2, and integrating resistor R1, the end of integrating resistor R1 is used to connect the drain electrode of synchronous rectifier T1, the other end of integrating resistor R1 connects the end of integrating capacitor C2 and the input of comparator A2, another termination signal ground of integrating capacitor C2, another input of comparator A2 connects signal ground by the second normal voltage V2, and the output of comparator A2 is used to export described pre-cut-off signals.
For the stability of circuit, in described shutoff pre-process circuit 300, also comprise: be connected on the drain electrode of synchronous rectifier T1 and the capacitance C1 between the integrating resistor R1.
In order to limit the size of current of described pre-cut-off signals, in described shutoff pre-process circuit 300, also comprise: the output and the described current-limiting resistance R2 that crosses between the zero balancing amplifying circuit 100 that are connected on described comparator A2.
In view of shutoff pre-process circuit 100 structures shown in Figure 1, for integrating capacitor C2 is resetted, described drive circuit also comprises: the integrating capacitor reset circuit 400 that links to each other with described shutoff pre-process circuit 300 outputs, be used for when the described pre-cut-off signals of described shutoff pre-process circuit 300 outputs, described integrating capacitor C2 being resetted.Shown in Figure 1, integrating capacitor reset circuit 400 comprises: inverter ic 1, with door IC2 and switch element IC3, the output of described comparator A2 connects an input described and door IC2 by inverter ic 1, the output of described comparator A2 connects another input described and door IC2, described output with door IC2 is connected the control end of described switch element IC3, described switch element IC3 is connected in parallel on the two ends of described integrating capacitor, when described comparator A2 exported described pre-cut-off signals, described switch element IC3 closure made described integrating capacitor C2 discharge reduction.Here the switch element IC3 that is carried can be triode T31, a diode D31 in parallel between its collector and emitter, as shown in Figures 2 and 3.
As shown in Figure 1, the above-mentioned zero balancing amplifying circuit 100 of crossing comprises: controlled relatively amplifying unit A1, and the first normal voltage V1, the control end of described controlled amplifying unit A1 connects the output of described shutoff pre-process circuit 300, the described controlled relatively input of amplifying unit A1 is used for connecting by the first normal voltage V1 drain electrode of described synchronous rectifier T1, and described controlled relatively another input of amplifying unit A1 is used to connect the source electrode of described synchronous rectifier T1.In addition, if controlled amplifying unit A1 adopts operational amplifier, then increase impedance Z and realize negative feedback.
As shown in Figure 1, the first normal voltage V1 can adopt DC power supply, but Fig. 3 gives the realization circuit of the another kind of first normal voltage V1, it comprises: resistance R 12, diode D12, diode D13, triode T12, resistance R 11, DC power supply VCC, the negative electrode of diode D12 connects the base stage of triode T12, the emitter of triode T12 connects the source electrode of described synchronous rectifier T1 by resistance R 11, the anode of diode D12 and diode D13 is connected the output of DC power supply VCC by resistance R 12, and the negative electrode of diode D13 connects the described controlled relatively input of amplifying unit A1.In addition, as shown in Figure 1, controlled relatively amplifying unit A1 adopts controlled high speed operation amplifier, and as shown in Figures 2 and 3, controlled relatively amplifying unit A1 comprises triode T11, capacitor C 11, and capacitor C 11 is connected in parallel between the collector and emitter of triode T11, and the base stage of triode T11 links to each other with the negative electrode of diode D13, the emitter of triode T11 connects the source electrode of described synchronous rectifier T1, and the collector electrode of triode T11 connects the output of described shutoff pre-process circuit 300.In order to overcome the error that element device parameter matching causes, in Fig. 3, increased element D12 and D13, element D12 and element D13, elements T 12 is consistent with the T13 parameter, thereby complementary, has overcome the conforming problem that component parameters error and variations in temperature cause.
In order to increase driving force, described drive circuit also comprises: be connected on the power amplification circuit 200 between the described grid of crossing zero balancing amplifying circuit 100 outputs and synchronous rectifier T1.Its complementary output level that can adopt triode to constitute realizes 200 parts as shown in Figures 2 and 3.As shown in Figure 2, power amplifying part is made of compound transistor T21, T22 and triode T23, and its input links to each other with the collector electrode of triode T11, and output is connected with the control grid of synchronous rectifier T1, it is an electric current driving amplifier, and output voltage equates with input voltage.
With Fig. 2 and two given specific embodiments of Fig. 3, operation principle of the present utility model is described below.
As shown in Figure 1, illustrate that with the continuous current mode circuit of reversed excitation its basic principle is as follows:
1. turn-off the preliminary treatment circuit in advance: establish circuit and reached stable state, institute's charging voltage is last negative just down on the capacitance C1, and its voltage equals electric power output voltage, and it is zero that the voltage on the integrating capacitor C2 has been put.It is disconnected that the transformer secondary output coil is in the beginning rank that reset, at this moment, because of the appearance value of capacitance C1 appearance value much larger than integrating capacitor C2, can think that the voltage of capacitor C 1 is constant substantially, the resetting voltage of coil 1 charges to integrating capacitor C2 by resistance, after reseting procedure was finished, the electric capacity of capacitor C 2 was charged to certain value.At this moment, coil voltage overturns, coil begins discharge through synchronous rectifier to capacitor C 3, simultaneously, integrating capacitor is also discharged to coil L by integrating resistor R1, since inductance to discharge and recharge weber value equal, also equate and be worth the ampere-second of capacitor charge and discharge, obviously, when coil discharge finishes when entering next switch periods, voltage on the integrating capacitor C2 is also put and is 0V, has inserted a reference voltage V 2 on comparator A2, by the comparison of voltage on the integrating capacitor C2 and reference voltage V 2, thereby drawn pre-cut-off signals, this signal is reflected in the output of comparator A2 and is: when the voltage on the integrating capacitor C2 is lower than the voltage of reference voltage source V2, be output as low level, electric current flows into common ports from controlled output voltage amplifier through resistance R 2, then controlled operational amplifier A 1 is output as a low voltage, synchronous rectifier T1 breaks away from the saturation region and enters the amplification region, prepares for next step shutoff, has finished pre-shutoff.
2. current over-zero compares amplifying circuit: the negative terminal at the controlled output voltage high speed operation amplifier of element A1 connects the drain electrode that is connected to synchronous rectifier T1 through a reference voltage source V1, the source electrode that just is connected to synchronous rectifier T1 of element A1.
(1) opens the stage, when transformer time limit winding L begins to discharge, its polarity is last negative just down, diode current flow in the synchronous rectification body, its drain voltage hangs down about 0.7V approximately than source voltage, because the voltage of reference voltage source V1 is far below 0.7V, at this moment, operational amplifier A 1 is output as high level, and output also is high level after power discharge device 200 amplifies, and homogeneous tube T1 is open-minded synchronously.
(2) open the maintenance stage, after synchronous rectifier T1 opens, because the voltage Vsd on the synchronous rectifier still is higher than the voltage of joining voltage source V 1, operational amplifier A 1 is output as high level, and this process lasts till that always comparator A2 provides till the pre-cut-off signals.
(3) pre-turn off process, when transformer secondary output coil L discharge process closes to an end, comparator A2 output low level, the Control current of operational amplifier A 1 flows back to common port through resistance R 2, operational amplifier A 1 controlled signal, output voltage is reduced to about 4V, after power amplifier 200 amplified, synchronous rectifier T1 voltage reduced, and broke away from saturation condition, enter magnifying state, because the threshold values shutoff voltage of synchronous rectifier T1 is about 3V, that is to say that the control pole tension of synchronous rectifier T1 only need reduce 1V more just can enter off state, obviously, reducing to 3V with respect to traditional control pole tension from about the 10V just turn-offs then and can shorten the turn-off time greatly.
(4) the dynamic conducting resistance adjustment of synchronous rectifier rank are disconnected, when power source loads is light, because the discharging current of secondary coil L is less, synchronous rectifier T1 after opening soon its tube voltage drop Vsd just less than the voltage of reference voltage source V1, the output voltage of operational amplifier A 1 reduces, force the Vgs voltage of synchronous rectifier T1 to descend, the on state resistance of synchronous rectifier T1 increases, make its Vsd voltage rise, because the negative feedback of impedance network Z, make the output voltage of operational amplifier A 1 finally reach stable state at the voltage Vsd of synchronous rectifier T1 when equaling the voltage of reference voltage source V1, this process is a lasting adjustment process.When power source loads is heavier, this adjustment process is then very of short duration, because this moment, the discharging current of secondary coil L was bigger, voltage drop Vsd on the synchronous rectifier T1 is always greater than the voltage of reference voltage source V1, open up to the primary switch pipe, secondary coil L electric current descends rapidly, and as the pressure drop Vsd of synchronous rectifier T1 during less than the voltage of reference voltage source V1, adjustment process begins.
(5) synchronous rectifier current over-zero turn off process, when secondary coil L discharge stream constantly is reduced to zero, the dynamic conducting resistance of synchronous rectifier T1 is adjusted the disconnected end in rank, output capacitance C3 begins to discharge to secondary coil L through synchronous rectifier T1, because counter-rotating has taken place in electric current, under the effect of impedance network Z, the course of work of comparator A2 is a strong positive feedback process, promptly the voltage drop Vds owing to synchronous rectifier T1 constantly raises, the output voltage of operational amplifier A 1 then constantly reduces, corresponding with it synchronous rectifier T1 control pole tension Vgs also constantly reduces, the conducting resistance of synchronous rectifier T1 also constantly increases, the then corresponding rising of its pressure drop Vds, so process is a positive feedback process, synchronous rectifier T1 turn-offs rapidly.Secondary coil L enters reseting procedure, enters next switch periods.Need to prove at this, when the electric current of synchronous rectifier T1 arrives zero, corresponding with it synchronous rectifier T1 control pole tension should corresponding effect through operational amplifier A 1 adjust to zero, promptly reach shutoff, because in the process of big electric current continuous operation, di/dt is bigger, electric current is very of short duration to zero this process from big electric current, and the regular hour is wanted in the shutoff of synchronous rectifier T1, so just turn-off this process after zero passage is arranged, and because pre-effect of turn-offing the preliminary treatment circuit, it is also very of short duration to turn-off this process after the synchronous rectifier T1 zero passage, reverse current is less, and only for using the reverse recovery current level of Schottky as rectification circuit, detailed process can be referring to oscillogram shown in Figure 4 in actual measurement.From the whole process of circuit, there is not synchronous rectifier to close this process of diode current flow in the synchronous rectifier body of having no progeny, shown in Fig. 4 (b), therefore do not need to solve the recovery problem that diode current flow brought in the synchronous rectification body for synchronous rectifier Schottky in parallel.
3. integrating capacitor reset circuit: when dynamic load is worked, can accurately provide pre-cut-off signals in order to ensure this circuit, therefore will guarantee to start from scratch, discharge into zero and finish in each switch periods integrating capacitor charging voltage.When secondary coil L discharge process will finish, voltage on the integrating capacitor C2 progressively reduces and approaches zero, and less than reference voltage V 2, comparator A2 is output as low level, behind reverser IC1, be output as high level send into the door IC2 an input, at the voltage identical with synchronous rectifier Vgs with the voltage that another input inserted of door IC2, because secondary discharge also end this moment, the Vgs of synchronous rectifier is a high level signal, so IC2 exports a high level signal at this moment with door, the electronic switch IC3 that resets opens after the secondary coil discharge process finishes, synchronous rectifier T1 turn-offs, its Vgs voltage is zero, be low level promptly with door IC2 one input terminal voltage, with the output voltage of door IC2 be low level also, the electronic switch IC3 that resets turn-offs, finished the resetting of integrating capacitor C2, integrating capacitor enters next switch periods integral process.
As shown in Figure 2, relatively amplifying circuit 100 can also be by resistance R 11 for the synchronous rectifier current over-zero, resistance R 12, resistance R 13, capacitor C 11, diode D11 and triode T11 constitute, wherein resistance R 12 provides a reference current, this electric current R11 that flows through produces a reference voltage, the junction voltage of diode D11 equates with the BE junction voltage of triode T11, when big electric current is flowed through synchronous rectifier, its Vsd is far above the voltage of R11, the reference current that provides through resistance R 11 is all through diode D11, resistance R 12 flows into the drain electrode of synchronous rectifier, no current flows through in the BE knot of triode T11, triode ends, so the Vgs of synchronous rectifier T1 obtains a high voltage, synchronous rectifier T1 conducting.When the current over-zero of the synchronous rectifier T1 that flows through, its pressure drop Vsd also is 0V, so 1/2 BE that flows through triode T11 of the reference current that R12 produced ties triode T11 saturation conduction, thereby the Vgs voltage of synchronous rectifier T1 is pulled to end level, and synchronous rectifier T1 ends.When the electric current that flows through synchronous rectifier T1 hour, the voltage drop that produces on synchronous rectifier T1 is less, be Vsd less than the pressure drop of resistance R 11 but greater than zero, then the reference current of resistance R 12 generations has small part to flow through the BE knot of triode T11, triode T11 is in magnifying state, thereby the Vgs voltage of adjusting synchronous rectifier T1 reduces, the corresponding increase of its conducting resistance, make Vsd increase, maintain the voltage levvl of resistance R 11, this process is a lasting adjustment process, and capacitor C 11 is used to eliminate the vibration that is in course of adjustment and produces.The pre-preliminary treatment circuit that turn-offs is made of capacitance C1, integrating resistor R1, integrating capacitor C2, reference voltage V 2, OC door output comparator A2 and resistance R 2.When comparator A2 obtained pre-cut-off signals and is output as a low level, resistance R 13 constituted the dividing potential drops relation with resistance R 2, thereby had dragged down the output voltage of power amplifier.
Illustrating of above-mentioned each concrete steps is comparatively concrete; can not therefore think restriction to scope of patent protection of the present utility model; above-mentioned pre-shutoff preliminary treatment circuit, integrating capacitor reset circuit, current over-zero comparison amplifying circuit, power amplification drive circuit all can adopt above-mentioned each circuit; perhaps its variant, scope of patent protection of the present utility model should be as the criterion with claims.
Claims (10)
1, a kind of drive circuit of synchronous rectifier is characterized in that, comprising:
Turn-off pre-process circuit, be used for obtaining detection signal, and this signal is compared with first normal voltage, result from pre-cut-off signals from the drain electrode of synchronous rectifier;
The zero balancing amplifying circuit excessively that links to each other with described shutoff pre-process circuit output, be used to gather the source signal of described synchronous rectifier, and this signal compared with second normal voltage, the conducting of exporting described synchronous rectifier drives the signal of telecommunication makes described synchronous rectifier be in saturation condition; Perhaps, exporting the pre-pre-shutoff driving signal of telecommunication that turn-offs of described synchronous rectifier makes described synchronous rectifier be in unsaturated state.
2, drive circuit according to claim 1 is characterized in that, described drive circuit also comprises: be connected on the power amplification circuit between the described grid of crossing zero balancing amplification circuit output end and synchronous rectifier.
3, drive circuit according to claim 1, it is characterized in that, described shutoff pre-process circuit comprises: comparator, integrating capacitor, and integrating resistor, one end of described integrating resistor is used to connect the drain electrode of described synchronous rectifier, the other end of described integrating resistor connects an end of described integrating capacitor and an input of described comparator, another termination signal ground of described integrating capacitor, another input of described comparator is by the described second standard electric crimping signal ground, and the output of described comparator is used to export described pre-cut-off signals.
4, drive circuit according to claim 3 is characterized in that, described shutoff pre-process circuit also comprises: be connected on the drain electrode of described synchronous rectifier and the capacitance between the described integrating resistor.
5, drive circuit according to claim 3 is characterized in that, described shutoff pre-process circuit also comprises: the output and the described current-limiting resistance of crossing between the zero balancing amplifying circuit that are connected on described comparator.
6, drive circuit according to claim 3, it is characterized in that, described drive circuit also comprises: the integrating capacitor reset circuit that links to each other with described shutoff pre-process circuit output, be used for when described shutoff pre-process circuit is exported described pre-cut-off signals, described integrating capacitor being resetted.
7, drive circuit according to claim 6, it is characterized in that, described integrating capacitor reset circuit comprises: inverter, with the door and switch element, the output of described comparator connects an input described and door by inverter, the output of described comparator connects another input described and door, described output with door is connected the control end of described switch element, described switch element is connected in parallel on the two ends of described integrating capacitor, when described comparator was exported described pre-cut-off signals, described switch element closure made described integrating capacitor discharge reduction.
8, drive circuit according to claim 1, it is characterized in that, the described zero balancing amplifying circuit of crossing comprises: controlled relatively amplifying unit, and first normal voltage, the control end of described controlled amplifying unit connects the output of described shutoff pre-process circuit, a described controlled relatively input of amplifying unit is used for connecting by first normal voltage drain electrode of described synchronous rectifier, and described controlled relatively another input of amplifying unit is used to connect the source electrode of described synchronous rectifier.
9, drive circuit according to claim 8, it is characterized in that, provide the circuit of described first normal voltage to comprise: resistance R 12, diode D12, diode D13, triode T12, resistance R 11, DC power supply VCC, the negative electrode of diode D12 connects the base stage of triode T12, the emitter of triode T12 connects the source electrode of described synchronous rectifier by resistance R 11, the anode of diode D12 and diode D13 is connected the output of DC power supply VCC by resistance R 12, and the negative electrode of diode D13 connects a described controlled relatively input of amplifying unit.
10, according to Claim 8 or 9 described drive circuits, it is characterized in that described controlled relatively amplifying unit adopts controlled high speed operation amplifier.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN2009201356200U CN201418040Y (en) | 2009-03-07 | 2009-03-07 | Driving circuit of synchronous rectifying tube |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN2009201356200U CN201418040Y (en) | 2009-03-07 | 2009-03-07 | Driving circuit of synchronous rectifying tube |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN201418040Y true CN201418040Y (en) | 2010-03-03 |
Family
ID=41794471
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN2009201356200U Expired - Fee Related CN201418040Y (en) | 2009-03-07 | 2009-03-07 | Driving circuit of synchronous rectifying tube |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN201418040Y (en) |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102195492A (en) * | 2011-05-24 | 2011-09-21 | 成都芯源系统有限公司 | Synchronous rectification switching power supply and control circuit and control method thereof |
| CN102735914A (en) * | 2012-05-10 | 2012-10-17 | 成都芯源系统有限公司 | Synchronous rectification circuit and zero-crossing detection method |
| CN105305844A (en) * | 2015-10-21 | 2016-02-03 | 无锡市芯茂微电子有限公司 | Isolated type synchronous rectification control circuit, device and method |
| CN115224914A (en) * | 2022-08-08 | 2022-10-21 | 绍兴光大芯业微电子有限公司 | Synchronous rectification chip pre-turn-off circuit structure for realizing flyback topology |
-
2009
- 2009-03-07 CN CN2009201356200U patent/CN201418040Y/en not_active Expired - Fee Related
Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102195492A (en) * | 2011-05-24 | 2011-09-21 | 成都芯源系统有限公司 | Synchronous rectification switching power supply and control circuit and control method thereof |
| CN102735914A (en) * | 2012-05-10 | 2012-10-17 | 成都芯源系统有限公司 | Synchronous rectification circuit and zero-crossing detection method |
| CN102735914B (en) * | 2012-05-10 | 2014-12-31 | 成都芯源系统有限公司 | synchronous rectification circuit and zero-crossing detection method |
| CN105305844A (en) * | 2015-10-21 | 2016-02-03 | 无锡市芯茂微电子有限公司 | Isolated type synchronous rectification control circuit, device and method |
| CN105305844B (en) * | 2015-10-21 | 2017-11-21 | 深圳市芯茂微电子有限公司 | A kind of isolated form synchronous commutating control circuit and its device and control method |
| CN115224914A (en) * | 2022-08-08 | 2022-10-21 | 绍兴光大芯业微电子有限公司 | Synchronous rectification chip pre-turn-off circuit structure for realizing flyback topology |
| CN115224914B (en) * | 2022-08-08 | 2024-03-22 | 绍兴光大芯业微电子有限公司 | Synchronous rectification chip pre-turn-off circuit structure for realizing flyback topology |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN105356727B (en) | Switching tube drive control method and control circuit for Switching Power Supply | |
| US9214850B2 (en) | Source-electrode driving control circuit and control method thereof | |
| CN102195492B (en) | Synchronous rectification switching power supply and control circuit and control method thereof | |
| CN101592965B (en) | Multi-mode control circuit and method and AC-DC conversion circuit | |
| CN101552560B (en) | Switch voltage stabilizing circuit and control method thereof | |
| CN108155799A (en) | For the control method and control device of flyback converter circuit | |
| CN107425728B (en) | A kind of digital optimal control method and its system of the synchronous rectification of LLC full-bridge converter | |
| CN103997295B (en) | Photovoltaic battery charge controller | |
| CN102231605A (en) | Synchronous rectification control circuit of switch power supply secondary and flyback switch power supply | |
| CN103280963B (en) | A kind of PFC control circuit reducing power tube conducting power consumption | |
| CN107147302B (en) | A kind of numerical control system and its control method of synchronous rectification LLC converter | |
| CN106487207B (en) | A kind of control method and device of power conversion circuit | |
| CN102957304A (en) | Driving circuit of triode and driving method thereof | |
| CN105244848A (en) | Overvoltage protection method and circuit | |
| CN107147296A (en) | A kind of band pulls down the isolated form DC DC booster converters of active clamp branch road | |
| CN103178712A (en) | Device and method for suppressing low-frequency fluctuation of pulse-cycle skip modulation switching converter | |
| CN201418040Y (en) | Driving circuit of synchronous rectifying tube | |
| CN102684462A (en) | Novel low end metal oxide semiconductor field effect transistor (MOSFET)/ insulated gate bipolar transistor (IGBT) negative pressure clamping driving circuit and control method thereof | |
| CN107834857A (en) | Power control and insulated switch power supply apparatus | |
| CN103281829B (en) | A kind of LED drive circuit | |
| CN107017779A (en) | A kind of band pulls down the isolated form DC DC booster converter control methods of active clamp branch road | |
| CN104411035B (en) | A kind of LED drive circuit powered without assists winding | |
| CN104185345B (en) | A kind of control device for constant current driver circuit for LED | |
| CN203722474U (en) | Quasi-Z-source DC-DC boost converter circuit | |
| CN103796389B (en) | High-high brightness hoisting module, controllable silicon light modulation LED drive circuit and system |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant | ||
| C17 | Cessation of patent right | ||
| CF01 | Termination of patent right due to non-payment of annual fee |
Granted publication date: 20100303 Termination date: 20130307 |