CN1897440A - Circuit for controlling switch power supply - Google Patents
Circuit for controlling switch power supply Download PDFInfo
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- CN1897440A CN1897440A CN 200610089519 CN200610089519A CN1897440A CN 1897440 A CN1897440 A CN 1897440A CN 200610089519 CN200610089519 CN 200610089519 CN 200610089519 A CN200610089519 A CN 200610089519A CN 1897440 A CN1897440 A CN 1897440A
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Abstract
Being difference with the currently-used technology, the invention adds a high-pass filter in the current feedback circuit in order to filter the low frequency portion in the current feedback signals, to improve the load capacity of the circuit at low voltage and to shorten the time of load variation.
Description
Technical field
The present invention relates to a kind of control switching control circuit, particularly a kind of DC control switch power control circuit of peak-current mode control.
Technical background
The DC control switch power control circuit mainly comprises pulse width modulation (Pulse-width Modulation, hereinafter to be referred as pulse-width modulation or PWM) comparator, control switch and output lc circuit, described PWM comparator is used for the square-wave signal of the input signal generation different duty of its input of comparison, the square-wave signal that these PWM comparators produce is used for the closure and the shutoff of drive controlling switch, therefore, these PWM square-wave signals also can be called pwm pulse and turn-off constantly, described control switch is used for when it is closed input voltage being inserted lc circuit, when it turn-offs, cut off the energy that is connected and discharges lc circuit of input voltage and lc circuit, described lc circuit comprises inductance that is connected with control switch and the electric capacity of connecting with described inductance, and the node voltage of the connected node of described inductance and electric capacity is used as output voltage.
The basic functional principle of described DC control switch power control circuit is exactly under the situation that input voltage changes, inner parameter changes or external load changes, control circuit carries out closed loop feedback by the difference of controlled signal and reference signal, the conducting pulse duration of regulation control switch makes controlled signals such as the output voltage of control switching control circuit or electric current stable.Because the key of DC control switch power control circuit is the control of the conducting pulse duration of control switch, so this control circuit also is called pulse-width modulation (PWM) control circuit.
Exist the various feedback control model to control PWM in the prior art, a kind of peak-current mode control (Peak Current Mode Control) PWM that is is wherein just arranged.Fig. 1 and 2 shows the control circuit of a kind of existing peak-current mode control pulse-width modulation (PWM) respectively.Show its a kind of embodiment as Fig. 1, described pulse-width modulation (PWM) control circuit comprises error amplifier (Error Amplifier) 10, triangular-wave generator (Ramp Generator) 20, PWM comparator 30, logical drive unit 40, control switch 50, the outputting inductance 60 of connecting and output capacitance 70, feedback amplifier 80, bleeder circuit 90.
The positive input of described error amplifier (Error Amplifier) 10 is imported a reference voltage V
Ref, also can be called reference voltage, reverse input end is imported output voltage V
OutThe feedback voltage V that dividing potential drop obtains
FB, described error amplifier 10 is with feedback voltage V
FBAnd reference voltage V
RefRelatively and with comparative result suitably amplify with output voltage V
EADescribed triangular-wave generator 20 is used to produce stable triangular signal.The positive input of described PWM comparator is imported described triangular signal, and its reverse input end is imported described output voltage V
EAWith feedback current voltage V
IFBSynthetic resultant voltage V
∑, described feedback current voltage V
IFBThe variation of reflection outputting inductance 60 current peaks, described PWM comparator is used for triangular wave and resultant voltage V
∑Compare to export the square-wave signal of certain duty ratio, the shutoff of just described control switch 50 constantly.The operation principle of described PWM comparator specifically please refer to Fig. 4, when the triangular signal current potential is higher than resultant voltage V
∑High level signal of output in the time of current potential, the resultant voltage V that is lower than when the triangular signal current potential
∑Low level signal of output in the time of current potential.By adjusting resultant voltage V
∑Current potential height just can adjust the duty ratio of output square wave, the shutoff of just having adjusted control switch 50 and then is controlled the output voltage V of pwm control circuit constantly
Out
Described control switch 50 by a PMOS manage, NMOS pipe forms, described PMOS manages and links to each other the source electrode of described PMOS pipe and input voltage V respectively with logical drive unit 40 with the grid of NMOS pipe
InConnect, the source electrode of described NMOS pipe is connected with ground, described PMOS pipe is connected with the drain electrode of NMOS pipe and links to each other with outputting inductance 60 as the output of control switch 50, the other end ground connection of the output capacitance 70 of connecting with outputting inductance 60, outputting inductance 60 is drawn the output voltage V of making pwm control circuit with the voltage of the connected node of output capacitance 70
Out, described output voltage V
OutObtain aforementioned feedback voltage V through bleeder circuit 90
FBDescribed bleeder circuit 90 is by being connected on output voltage V
OutAnd first divider resistance between the ground and second divider resistance composition, the intermediate node voltage of described first divider resistance and second divider resistance is as feedback voltage V
FB
Described logical drive unit 40 receives the square-wave signal of described PWM comparator and it is divided into two-way, and one tunnel grid of giving the PMOS pipe is as switching signal, and the grid of NMOS pipe is given as switching signal through certain time-delay in another road.Aforementioned feedback current voltage V
IFBBe with input voltage V
InDeduct after the intermediate node voltage of control switch 50 and outputting inductance 60 again through suitably amplifying through amplifier 80 again after the switch collection by the control pmos system of control switch 50 and obtain.Aforementioned feedback current voltage V
IFBComputing formula be:
V
IFB＝α*(V
in-(V
in-i*R
PMOS))＝α*i*R
PMOS
Wherein: α is the amplification coefficient of amplifier 80, and i is outputting inductance 60 electric currents, R
PMOSEquivalent resistance for the PMOS pipe.By formula feedback current voltage V as can be seen
IFBReflected the variation of outputting inductance current peak.
As input voltage V
InUnder the situation that variation or external load change, described feedback voltage V
FBMay produce fluctuation, error amplifier 10 is with the feedback voltage V of fluctuation
FBWith reference voltage V
RefRelatively and with comparative result suitably amplify to adjust output voltage V
EAThereby, adjust resultant voltage V
∑Current potential height with the duty ratio of control output square wave, the shutoff of having adjusted control switch 50 constantly, and then the output voltage V of control pwm control circuit
OutConverge on a fiducial value, at this moment feedback voltage V
FBWith reference voltage V
RefBetween difference be zero, therefore, this output voltage V
OutFiducial value and reference voltage V
RefDirectly related.
In the duty ratio of the square wave of pwm control circuit shown in Figure 1 output voltage V by error amplifier 10
EAFeedback current voltage V with the variation of reflection outputting inductance 60 current peaks
IFBResultant voltage V
∑Decision.Therefore, peak-current mode control pwm control circuit is a double closed-loop control system, ring in the outer voltage Control current.Current inner loop is instantaneous fast according to pulsed operation one by one.Power stage is the current source by current inner loop control, and this power output stage current source of outer voltage control.In the control of this dicyclo, current inner loop only is responsible for the dynamic change of input inductance, thereby outer voltage only need control output capacitance, needn't control the LC accumulator.
The another one embodiment of peak-current mode shown in Figure 2 control pwm control circuit, the difference of itself and pwm control circuit shown in Figure 1 is the feedback current voltage V that reflection outputting inductance 60 current peaks change
IFBIt or not output voltage V with error amplifier 10
EAForm resultant voltage V '
∑But and the triangular signal that produces of triangular-wave generator 20 consist of triangular shape waveform or the trapezoidal tip-angled shape synthesized waveform signal that its peak value is represented the outputting inductance current peak, and synthesized waveform signal imported the positive input of PWM comparator, and the output voltage V of error amplifier 10
EADirectly import the reverse input end of PWM comparator.The operation principle of pwm control circuit shown in Figure 2 with shown in Figure 1 is identical, and this appearance is not given unnecessary details again.
Peak-current mode control makes pwm control circuit become a single pole system, and also having a benefit is exactly conveniently to compensate.But directly quote electric current can cause following two aspects as feedback signal influence:
1. on load capacity.Under continuous current pattern (Continue Current Mode), the duty ratio of the drive signal of control switch 50 (D=Vout/Vin) is a constant value in theory, in order to obtain a constant D value, the output voltage V of error amplifier 10
EAMust change along with the variation of the electric current that flows through outputting inductance 60.And when loading a big load, the electric current that flows through outputting inductance 60 can increase, and the output voltage V of error amplifier 10
EAAlso just need to increase thereupon, however the output voltage V of error amplifier 10
EAValue be subjected to input voltage V
InRestriction must limit within the specific limits, therefore, when load during greater than certain limit, the output voltage V of the error amplifier 10 that needs
EAValue just may exceed its span.Like this, the load capacity of the pwm control circuit under the peak-current mode will be very limited.
2. aspect load response speed.As in 1, discussing, the output voltage V of error amplifier
EANeed adapt with the load current that flows through outputting inductance 60.When load changes fast, that is to say when load current changes the output voltage V of error amplifier
EAResponse time will be because of output voltage V
EAThe value amplitude of variation increases and increases, again output voltage V
EAIt can produce strong upwards overshoot and overshoot downwards during response.
Therefore, demand occurring the DC control switch power control circuit that a kind of load capacity is strong and response speed is fast urgently.
Summary of the invention
In view of this, the object of the present invention is to provide the DC control switch power control circuit that a kind of load capacity is strong and response speed is fast.
In order to achieve the above object, a kind of control switching control circuit is described according to the present invention, and it comprises:
The output lc circuit, it comprises the outputting inductance and the electric capacity of series connection, the other end ground connection of output capacitance, the node voltage of the connected node of described outputting inductance and electric capacity is used as output voltage V
Out
Control switch, it has and input voltage V
InPower connector end, the ground connection link that is connected with ground, the output that is connected with outputting inductance that connects and be used to control the control end of described control switch unlatching or shutoff, described control switch is used for when it is opened input voltage V
InFlow to the output lc circuit to give the charging of output lc circuit, described control switch also is used for cutting off input voltage V when it turn-offs
InWith output lc circuit be connected and to its discharge;
Error amplifier, one input end input reference voltage V
Ref, another input input is with output voltage V
OutThe feedback voltage V that dividing potential drop obtains
FB, described error amplifier is used for described feedback voltage V
FBWith described reference voltage V
RefSubtract each other and difference is amplified, with output error voltage V
EA
Triangular-wave generator is used to produce stable triangular signal;
Pulse-width modulation comparator, one input end are imported described triangular signal, and its another input input is by error voltage V
EAFeedback current voltage V with the variation of reflection outputting inductance electric current
IFBSynthetic resultant voltage V
∑, perhaps one input end is imported described triangular signal and the feedback current voltage V that reflects that the outputting inductance electric current changes
IFBResultant voltage V '
∑, its another input input error voltage V
EA, the pulse-width modulation comparator is used for triangular wave and resultant voltage V
∑Compare or be used for error voltage V
EAWith resultant voltage V '
∑Compare the control end of giving described control switch with the switch controlling signal of the unlatching of exporting described control switch and shutoff; Its characteristics are,
Described control circuit also includes high pass filter, and it is used to filter out feedback current voltage V
IFBLow frequency component part in the middle reflection outputting inductance electric current makes feedback current voltage V
IFBThe high fdrequency component that only reflects the outputting inductance electric current.
A kind of control switching control circuit of the present invention is described owing to adopted high pass filter, and the high fdrequency component in the filtering feedback current voltage makes output voltage V
EAAmplitude of variation significantly dwindle, the response speed of control circuit significantly improves.In addition, under the same load current situation, owing to introduced high pass filter, and make output voltage V
EAThe operating voltage that needs is from reducing, because the output voltage V of error amplifier
EAThe upper limit be subjected to input voltage V
InRestriction, therefore, in the output voltage V of error amplifier
EAPrescribe a time limit for last, introduced the load of the control circuit of high pass filter and wanted obviously greater than the situation that does not have to introduce.
Description of drawings
Fig. 1 is the structured flowchart of first kind of embodiment of the DC control switch power control circuit under the peak-current mode in the prior art;
Fig. 2 is the structured flowchart of second kind of embodiment of the DC control switch power control circuit under the peak-current mode in the prior art;
Fig. 3 is the structured flowchart of first kind of execution mode of the DC control switch power control circuit under the peak-current mode of the present invention;
Fig. 4 is the schematic diagram that the PWM comparator produces certain duty ratio square wave;
Fig. 5 is the simulation waveform figure of existing DC control switch power control circuit;
Fig. 6 be DC control switch power control circuit of the present invention simulation waveform figure;
Fig. 7 is the structured flowchart of second kind of execution mode of the DC control switch power control circuit under the peak-current mode of the present invention;
Fig. 8 is that high pass filter is realized block diagram among the present invention; With
Fig. 9 is the physical circuit figure that high pass filter is realized among the present invention.
Embodiment
The invention provides a kind of DC control switch power control circuit of peak-current mode control, also can be called the pwm control circuit 101 of peak-current mode control, Fig. 3 shows first execution mode of pwm control circuit 101 of the present invention.
Please referring to Fig. 3, pwm control circuit 101 provided by the invention comprises error amplifier 10, triangular-wave generator 20, PWM comparator 30, logical drive unit 40, control switch 50, the outputting inductance 60 of connecting and output capacitance 70, feedback amplifier 80, bleeder circuit 90.
The positive input of described error amplifier (Error Amplifier) 10 is imported a reference voltage V
Ref, also can be called reference voltage, reverse input end is imported output voltage V
OutThe feedback voltage V that dividing potential drop obtains
FB, described error amplifier 10 is used for described feedback voltage V
FBWith described reference voltage V
RefRelatively and with comparative result suitably amplify in order to output, this output voltage is called as V
EADescribed triangular-wave generator 20 is used to produce stable triangular signal.
The positive input of described PWM comparator is imported described triangular signal, and its reverse input end is imported the output voltage V of described error amplifier 10
EAFeedback current voltage V with the variation of reflection outputting inductance 60 current peaks
IFBSynthetic resultant voltage V
∑, described PWM comparator is used for triangular wave and resultant voltage V
∑Compare to export the square-wave signal of certain duty ratio.The operation principle of described PWM comparator specifically please refer to Fig. 4, when the triangular signal current potential is higher than resultant voltage V
∑High level signal of output in the time of current potential, the resultant voltage V that is lower than when the triangular signal current potential
∑Low level signal of output in the time of current potential.
Described control switch 50 by a PMOS manage, NMOS pipe forms, described PMOS manages and links to each other the source electrode of described PMOS pipe and input voltage V respectively with logical drive unit 40 with the grid of NMOS pipe
InConnect, the emitter-base bandgap grading of described NMOS pipe is connected with ground, the emitter-base bandgap grading of described PMOS pipe is connected with the source electrode of NMOS pipe and links to each other with outputting inductance 60 as the output of control switch 50, the other end ground connection of the output capacitance 70 of connecting with outputting inductance 60, outputting inductance 60 is drawn the output voltage V of making pwm control circuit with the voltage of the connected node of output capacitance 70
Out, described output voltage V
OutObtain aforementioned feedback voltage V through bleeder circuit 90
FBDescribed bleeder circuit 90 is by being connected on output voltage V
OutAnd first divider resistance between the ground and second divider resistance composition, the intermediate node voltage of described first divider resistance and second divider resistance is as feedback voltage V
FB
Described logical drive unit 40 receives the square-wave signal of described PWM comparator and it is divided into two-way, and one tunnel grid of giving the PMOS pipe is as switching signal, and the grid of NMOS pipe is given as switching signal through certain time-delay in another road.When square-wave signal is high level, open NMOS and manage shutoff PMOS pipe, release energy for outputting inductance 60, output capacitance 70, be called as the shutoff moment of control switch 50 this moment; And when square wave when being low level, open the PMOS pipe and turn-off NMOS pipe, input voltage V
InManage to outputting inductance, electric capacity charging by PMOS, be called as the unlatching moment of control switch this moment.From this angle, aforementioned square-wave signal also can be called the switching time of described control switch 50.Described logical drive unit 40 is used for guaranteeing can not producing the state that two pipes all open or all turn-off and produces.Therefore, by adjusting resultant voltage V
∑Current potential height just can adjust the duty ratio of output square wave, the shutoff of just having adjusted control switch 50 and then is controlled the output voltage V of pwm control circuit constantly
Out
The feedback current voltage V that aforementioned reflection outputting inductance 60 current peaks change
IFBBe with input voltage V
InDeduct after the intermediate node voltage of control switch 50 and outputting inductance 60 again through suitably amplifying through amplifier 80 again after the switch collection by the control pmos system of control switch 50 and obtain.Aforementioned feedback current voltage V
IFBComputing formula be:
V
IFB＝α*(V
in-(V
in-i*R
PMOS))＝α*i*R
PMOS
Wherein: α is the amplification coefficient of amplifier 80, and i is outputting inductance 60 electric currents, R
PMOSResistance value for the PMOS pipe.By formula feedback current voltage V as can be seen
IFBReflected the variation of outputting inductance current peak.
The concrete control procedure of pwm control circuit 100 provided by the invention once is described below.
As input voltage V
InUnder the situation that variation or external load change, described output voltage V
OutThe fluctuation that may will produce increases or reduce below is that example is introduced control procedure: described feedback voltage V with the increase
FBIncrease feedback voltage V
FBWith reference voltage V
RefBetween difference increase output voltage V
EAIncrease resultant voltage V thereupon
∑Current potential draw high, the high level of square-wave signal increases constantly, the shutoff of control switch 50 increases promptly charging constantly and reduces constantly, output voltage V
OutReduce up to converging on a fiducial value, at this moment, feedback voltage V
FBConverge on reference voltage V
RefTherefore, reference voltage V
RefBe used to determine output voltage V
OutSize.On the contrary, output voltage V
OutWhen diminishing, feedback voltage V
FBWith reference voltage V
RefBetween difference reduce output voltage V
EAReduce resultant voltage V thereupon
∑Current potential drag down, the high level of square-wave signal reduces constantly, the unlatching of control switch 50 increases promptly charging constantly and increases constantly, output voltage V
OutIncrease is up to converging on a fiducial value.That is to say, adjust resultant voltage V by voltage or current feedback
∑Current potential height, just can adjust the duty ratio of output square wave, just adjusted the switching time of control switch 50, and then controlled the output voltage V of pwm control circuit
Out
In the duty ratio of the square wave of pwm control circuit shown in Figure 3 output voltage V by error amplifier 10
EAFeedback current voltage V with the variation of reflection outputting inductance 60 current peaks
IFBResultant voltage V
∑Decision.Therefore, peak-current mode control pwm control circuit is a double closed-loop control system, ring in the outer voltage Control current.Current inner loop is instantaneous fast according to pulsed operation one by one.Power stage is the current source by current inner loop control, and this power output stage current source of outer voltage control.In the control of this dicyclo, current inner loop only is responsible for the dynamic change of input inductance, thereby outer voltage only need control output capacitance, needn't control the LC accumulator.
Can find that to the load capacity of the pwm control circuit of peak-current mode of the prior art control and the analysis of load corresponding speed the weak and slow basic reason of load corresponding speed of the load capacity of pwm control circuit of the prior art is the output voltage V of error amplifier 10
EAMust change along with the variation of the electric current that flows through outputting inductance 60, and the most important thing is output voltage V
EAMust change along with the variation of the low frequency component in the electric current that flows through outputting inductance 60.Yet, what really the stability of pwm control circuit is brought benefit in current feedback is the high fdrequency component that flows through in the electric current of outputting inductance 60, and what benefit the low frequency component that flows through in the electric current of outputting inductance 60 does not bring to the stability of pwm control circuit.Based on this kind consideration, please once more referring to shown in Figure 3, pwm control circuit 101 also comprises the high pass filter 100 that is arranged in current feedback loop, and described high pass filter 100 is used to filter out feedback current voltage V
IFBThe part of the low frequency component in the middle reflection outputting inductance electric current makes feedback current voltage V
IFBOnly reflect that outputting inductance 60 electric current high fdrequency components change.Therefore, the output voltage V of error amplifier 10
EADo not contain the low frequency component of the electric current that flows through outputting inductance 60, thus make pwm control circuit 101 provided by the invention guarantee the same with control circuit shown in Figure 1 stable in, increased load capacity and accelerated response speed.
Please contrast referring to Fig. 5 and shown in Figure 6, Fig. 5 is the simulation waveform figure of existing DC control switch power control circuit, Fig. 6 is the simulation waveform figure of DC control switch power control circuit of the present invention, and each simulation waveform figure is by the time dependent oscillogram of a plurality of parameters.First oscillogram all is an output voltage V in two picture groups (Fig. 5 and Fig. 6)
OutTime domain waveform figure; Second oscillogram is input voltage V
InTime domain waveform figure; The 3rd oscillogram is the time domain waveform figure that flows through the current i of outputting inductance; The 4th oscillogram is the electric current time domain waveform figure that flows through load; The 5th oscillogram is the output voltage V of error amplifier 10
EATime domain waveform figure.
Please contrast referring to Fig. 5,6 the 4th figure, the DC control switch power control circuit all is to be to jump to 300mA about 60mA at load current, and then returns 60mA from the saltus step of the 300mA left and right sides.
Please control reference Fig. 5,6 the 1st figure, under the situation of identical load variations, the output voltage V of the power output stage of existing control circuit and control circuit of the present invention
OutWaveform has all produced downward overshoot (B) to a certain degree when load current jumps to about 300mA from about 60mA, all produced upwards overshoot (A) to a certain degree at load current when the saltus step of the 300mA left and right sides is returned about 60mA.In the control circuit of not introducing high pass filter, the output voltage V of power output stage
OutUpwards the difference between the valley of peak overshoot and overshoot downwards is about 403mV, and has introduced in the control circuit of high pass filter the output voltage V of power output stage
OutUpwards the difference between the valley of peak overshoot and overshoot downwards is about 105mV, and overshoot has reduced greatly, and like this, the response speed of control circuit has also improved greatly.
Same, please control reference Fig. 5,6 the 5th figure, in the control circuit of not introducing high pass filter, the output voltage V of error amplifier 10
EAWaveform becomes 1.4V by 900mV when load current jumps to about 300mA from about 60mA, amplitude of fluctuation is 500mV; And introduce in the control circuit of high pass filter the output voltage V of error amplifier 10
EAWaveform becomes 900mV by 600mV when load current jumps to about 300mA from about 60mA, amplitude of fluctuation is 300mV.Under same load current changes, owing to introduced high pass filter, and make output voltage V
EAAmplitude of variation reduce to 300mV from 500mV, amplitude of variation is significantly dwindled, this also as can be seen, the response speed of control circuit significantly improves.In addition, under the same load current situation, owing to introduced high pass filter, and make output voltage V
EAThe operating voltage that needs is reduced to 900mV from 1.4V, because the output voltage V of error amplifier 10
EAThe upper limit be subjected to input voltage V
InRestriction, therefore, in the output voltage V of error amplifier 10
EAPrescribe a time limit for last, introduced the load of the control circuit of high pass filter and wanted obviously greater than the situation that does not have to introduce.
From contrast we as can be seen, tributary of the present invention control switching control circuit has been owing to introduced high pass filter 100, and improved the speed of response when having strengthened its load capacity.
Please referring to shown in Figure 7, second kind of execution mode of the present invention compared with first kind of execution mode, described do not have not to be connected to as negative feedback the output of error amplifier 10 through the high pass filter 70 and the current signal that flows through power output stage of amplifier 80, but be connected and deliver to the positive input of comparator 30 as the triangular signal of positive feedback and triangular-wave generator 10 generations.Its effect is not given unnecessary details at this with first embodiment.
Please referring to shown in Figure 8, the mentality of designing among the figure has been adopted in described high pass filter design.Because low pass filter easier realization on circuit, thereby the present invention produces the two-way signal identical with described current feedback signal with a current mirroring circuit earlier, fall the wherein high fdrequency component of one road signal with a low pass filter filters out, and deduct the current feedback signal that this road filters out high fdrequency component with another road signal, the current feedback signal of high fdrequency component is only arranged.Because the value of the current feedback signal of input is bigger, adopt low pass filter will adopt big resistance to cooperate, and big electric capacity can take very big chip area with big electric capacity, the present invention then adopts the Miller capacitance design, has saved very big chip area.
Please contrast referring to Fig. 8, shown in Figure 9, described high pass filter comprises 7 metal-oxide-semiconductors and a resistance R 20,7 metal-oxide-semiconductors are respectively M0, M5, M6, M8, M27 and M28, the current feedback signal that contains high fdrequency component and low frequency component of filter is advanced in I_in representative input, and the I_out representative is through the current signal of high pass filter filters.As shown in Figure 9, M0 and M5, M8 have constituted two current mirrors, M27 and M29 have constituted an equivalent capacity, M6, unite with M27, M29 and to constitute a Miller capacitance, R20 and M6, M27, M29 have constituted a low pass filter, the current signal that is drained by M5 again after the high fdrequency component of input signal I_in leached subtracts each other, and will obtain the only current signal of reserved high-frequency component at output at last.
The Miller capacitance design that the present invention has preferably adopted M6, M27 and M29 to constitute, so just the equivalent capacity that M27 and M29 can be constituted amplify M6 gain doubly, so just utilize two triode equivalences to go out a bigger electric capacity, saved very big chip area.
Above-mentioned connection about current mirror and Miller capacitance can easily obtain correlation technique with, function and electrology characteristic those of ordinary skills, does not give unnecessary details for this reason at this.
The power output stage of current peak modulating device of the present invention can adopt buck, boost and buck-boost circuit.
Current peak modulating device of the present invention can also be used in the circuit of driving LED light and shade.
The above only is preferred embodiment of the present invention, and is in order to restriction the present invention, within the spirit and principles in the present invention not all, any modification of being done, is equal to replacement etc., all should be included within protection scope of the present invention.
Claims (7)
1. control switching control circuit, it comprises:
The output lc circuit, it comprises the outputting inductance and the electric capacity of series connection, the other end ground connection of output capacitance, the node voltage of the connected node of described outputting inductance and electric capacity is used as output voltage V
Out
Control switch, it has and input voltage V
InPower connector end, the ground connection link that is connected with ground, the output that is connected with outputting inductance that connects and be used to control the control end of described control switch unlatching or shutoff, described control switch is used for when it is opened input voltage V
InFlow to the output lc circuit to give the charging of output lc circuit, described control switch also is used for cutting off input voltage V when it turn-offs
InWith output lc circuit be connected and to its discharge;
Error amplifier, one input end input reference voltage V
Ref, another input input is with output voltage V
OutThe feedback voltage V that dividing potential drop obtains
FB, described error amplifier is used for described feedback voltage V
FBWith described reference voltage V
RefSubtract each other and difference is amplified, with output error voltage V
EA
Triangular-wave generator is used to produce stable triangular signal;
Pulse-width modulation comparator, one input end are imported described triangular signal, and its another input input is by error voltage V
EAFeedback current voltage V with the variation of reflection outputting inductance electric current
IFBSynthetic resultant voltage V
∑, perhaps one input end is imported described triangular signal and the feedback current voltage V that reflects that the outputting inductance electric current changes
IFBResultant voltage V '
∑, its another input input error voltage V
EA, the pulse-width modulation comparator is used for triangular wave and resultant voltage V
∑Compare or be used for error voltage V
EAWith resultant voltage V '
∑Compare the control end of giving described control switch with the switch controlling signal of the unlatching of exporting described control switch and shutoff; It is characterized in that,
Described control circuit also includes high pass filter, and it is used to filter out feedback current voltage V
IFBLow frequency component part in the middle reflection outputting inductance electric current makes feedback current voltage V
IFBThe high fdrequency component that only reflects the outputting inductance electric current.
2. control switching control circuit according to claim 1, it is characterized by: described control switch comprises a PMOS pipe and a NMOS pipe, the source electrode of described PMOS pipe and PMOS pipe all is connected an end of described inductance, and the drain electrode of described PMOS pipe is connected to described input voltage V as power connector end
InOn, the drain electrode of described NMOS pipe is connected to ground as the ground connection link, the grid of described PMOS and NMOS is as the control end of described control switch, its purpose be when switch controlling signal when being low level PMOS open NMOS closure, input voltage V
InBe described lc circuit charging, and NMOS opens the PMOS closure when switch controlling signal is high level, described lc circuit is by the earth terminal discharge of NMOS.
3. control switching control circuit according to claim 2, it is characterized by: described control circuit also includes the logical drive unit, comprise an input and two outputs, its input is imported the switch controlling signal that described control switch is opened and turn-offed, an one output is directly exported the grid that described switch controlling signal is given described PMOS pipe, its another output is exported the grid that same switch controlling signal is given described NMOS pipe through a specific time-delay, and its purpose is to guarantee that PMOS manages and the NMOS pipe can not be opened or close simultaneously.
4. control switching control circuit according to claim 2 is characterized by: aforementioned feedback current voltage V
IFBBe with input voltage V
InDeduct suitably to amplify through amplifier 80 again after the intermediate node voltage of control switch and outputting inductance and obtain aforementioned feedback current voltage V
IFBComputing formula be:
V
IFB＝α*(V
in-(V
in-i*R
PMOS))＝α*i*R
PMOS
α is the amplification coefficient of amplifier, and i is the outputting inductance electric current, R
PMOSResistance value for the PMOS pipe.
5. control switching control circuit according to claim 1 is characterized by: described high pass filter is made of a current mirroring circuit low-pass filter circuit, and at first described current mirroring circuit produces two-way and described feedback current voltage V
IFBIdentical signal, described low pass filter filters out fall the wherein high fdrequency component of one road signal, and deduct the feedback current voltage signal that this road filters out high fdrequency component with another road signal, and the feedback current voltage signal of high fdrequency component is only arranged.
6. control switching control circuit according to claim 5 is characterized by: described low pass filter adopts the capacitance resistance filter design, and described electric capacity adopts the Miller capacitance design.
7. control switching control circuit according to claim 1 is characterized by: with output voltage V
OutThe feedback voltage V that dividing potential drop obtains
FBBe to obtain aforementioned feedback voltage V through bleeder circuit
FB, described bleeder circuit is by being connected on output voltage V
OutAnd first divider resistance between the ground and second divider resistance composition, the intermediate node voltage of described first divider resistance and second divider resistance is as feedback voltage V
FB
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